EP0111929B1 - Arrangement for switching off an inverter - Google Patents
Arrangement for switching off an inverter Download PDFInfo
- Publication number
- EP0111929B1 EP0111929B1 EP83112842A EP83112842A EP0111929B1 EP 0111929 B1 EP0111929 B1 EP 0111929B1 EP 83112842 A EP83112842 A EP 83112842A EP 83112842 A EP83112842 A EP 83112842A EP 0111929 B1 EP0111929 B1 EP 0111929B1
- Authority
- EP
- European Patent Office
- Prior art keywords
- circuit
- disconnect
- current
- monitoring
- arrangement
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Images
Classifications
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
- H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
- H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
- H05B41/2985—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal lamp operating conditions
Definitions
- the invention relates to an arrangement for switching off an inverter according to the preamble of claim 1.
- Such an arrangement as described in the international patent application PCT / DE 82/00155 has the advantage that the shutdown of the inverter triggered by a malfunction is canceled when the defective lamp is removed, that is to say no separate mains shutdown is required.
- the monitoring circuit must be dimensioned such that the required minimum holding current can flow through it at the lowest supply voltage under consideration, which is above the tilt-back limit at which the switch-off device tilts back into the normal state.
- This holding current now causes additional losses during normal operation, which are of particular importance if a resistance of the monitoring circuit is parallel to the oscillating capacitor of the inverter.
- the object of the invention is therefore to reduce these additional losses. This is achieved according to the invention in the case of an arrangement having the features of claim 1.
- the monitoring circuit can therefore be dimensioned with a higher resistance, the greater the sensitivity of the controllable resistance in the holding circuit.
- the invention makes this possible to dimension the monitoring circuit and the holding circuit independently of one another such that the switch-off device remains securely in this state after a switch-off even at the lowest supply voltage, even if an electrode in the monitoring circuit is broken.
- the previously observed intermittent switching off and restarting of the inverter can then be avoided by appropriate dimensioning. The reason for this was found to be that the current flowing in the monitoring circuit when the electrode was broken was not sufficient to maintain the switch-off state at all supply voltages under consideration, but was sufficiently large to charge the starting capacitor to the response value of the inverter.
- the inverter denoted by W is supplied via terminals w1 with a supply voltage source from a step-up converter H, which in turn is connected to an AC voltage network N.
- the transistors V1, V2 are connected in series between the terminals w1, w2 and are controlled alternately by a control set S.
- the latter contains secondary windings t2, t3 of a saturation transformer T, the primary winding t1 of which is arranged in series with a switching capacitor C1 and an intermediate load circuit in parallel with the transistor V1;
- the load circuit itself consists of two parallel, identical lamp circuits, each of which has a series resonance circuit C01, L01; C02, L02 and the heated electrodes e11, e12; contains e21, e22 of a discharge lamp E1, E2, the capacitor of the series resonant circuit being arranged in each case between the electrodes of a lamp.
- the operating frequency of the inverter is essentially determined by the saturation transformer T and is somewhat higher than the resonance frequency of the series resonance circuits located in the lamp circuits.
- a bistable shutdown device A ensures a permanent shutdown of the inverter W when the time integral of the current in one of the lamp circuits exceeds a predetermined limit value.
- the bistable switching device contains a thyristor V3, the control path of which is connected via a switching diode D2 to a capacitor C5 which is connected in parallel with the resistor R4 and diode D3 of the switching path of the thyristor V3 via a discharge branch.
- each voltage divider lies parallel to a choke L01 or L02 of the series resonant circuits when the transistor V2 of the inverter is turned on.
- the associated choke and the voltage divider connected to it generate such a high voltage that the thyristor V3 of the shutdown device A is turned on after a certain time.
- V3 then short-circuits a secondary winding t4 of the saturation transformer T via diode D5, so that the inverter can no longer oscillate.
- the load circuit of the thyristor is connected to w1, w2 via a holding circuit this holding circuit contains a diode D6, a resistor R7 and a transistor V4 in series.
- the thyristor V3 is connected via a resistor R10 in the discharge circuit of a starting capacitor C3, the voltage of which is fed to the control unit S via a switching diode D4: when the voltage across this starting capacitor reaches a limit value determined by this switching diode, the inverter begins to oscillate.
- This starting capacitor is connected to a resistor R5 which, together with the resistor R10 and the monitoring circuit, is connected to the DC supply voltage; the monitoring circuit contains a resistor R6, the electrodes e11, e21, a diode D7 and a resistor R9.
- the control path of the transistor V4 is connected in parallel with the resistor R9 via a resistor R8.
- the holding current no longer needs to flow through the monitoring circuit, it and the voltage divider for C3 enclosing it can be dimensioned with a correspondingly high resistance, so that it causes only negligible losses in normal operation (when the shutdown device is in the normal state).
- the voltage divider then only needs to be dimensioned in such a way that the start-up limit of the voltage is reached at C3 with the smallest supply voltage under consideration and with intact electrodes, provided the shutdown device is in the normal state.
- the sensitivity of the transistor V4 and its control circuit are then to be dimensioned such that the essentially constant current flowing when the electrode is broken is sufficient to control the transistor into saturation, provided that the switch-off device A is in the switch-off state and the then current flowing through the holding circuit is above the tilt-back limit value I H1 of the disconnection device A, that is to say the required minimum holding current IH2 flows at the lowest supply voltage that is possible.
- the first line shows the position of the tilt-back range which ends with the tilt-back limit value I H1 .
- Line 2 shows the range of the permissible holding currents I H , the minimum holding current IH2 of which is at a safety distance from the tilt-back limit value I H1 .
- the third line shows the range of the monitoring currents I B possible when A is switched off, which projects into the tilt-back range.
- transistor V4 ensures that at least the minimum holding current IH2 flows in the holding circuit even with the lowest supply voltage and broken electrode (monitoring current I B2 ).
- Line 4 finally shows the range of the monitoring currents I B flowing through the voltage divider of the starting capacitor C3 in normal operation.
- This voltage divider is dimensioned such that the maximum value I B1 of the monitoring current is below the minimum response value I B2 , ie V4 practically blocks in normal operation.
Abstract
Description
Die Erfindung betrifft eine Anordnung zur Abschaltung eines Wechselrichters gemäss Oberbegriff von Anspruch 1.The invention relates to an arrangement for switching off an inverter according to the preamble of
Eine solche in der internationalen Patentanmeldung PCT/DE 82/00155 beschriebene Anordnung hat den Vorteil, dass die durch einen Störungsfall ausgelöste Abschaltung des Wechselrichters beim Entfernen der schadhaften Lampe aufgehoben wird, also keine gesonderte Netzabschaltung erforderlich ist. Hierbei muss jedoch der Überwachungsstromkreis so bemessen sein, dass über ihn bei der niedrigsten in Betracht kommenden Speisespannung der erforderliche Mindesthaltestrom fliessen kann, der über dem Rückkippgrenzwert liegt, bei dem die Abschalteinrichtung wieder in den Normalzustand zurückkippt.Such an arrangement as described in the international patent application PCT / DE 82/00155 has the advantage that the shutdown of the inverter triggered by a malfunction is canceled when the defective lamp is removed, that is to say no separate mains shutdown is required. Here, however, the monitoring circuit must be dimensioned such that the required minimum holding current can flow through it at the lowest supply voltage under consideration, which is above the tilt-back limit at which the switch-off device tilts back into the normal state.
Dieser Haltestrom verursacht nun im Normalbetrieb Zusatzverluste, die vor allem ins Gewicht fallen, wenn ein Widerstand des Überwachungskreises zu dem Umschwingkondensator des Wechselrichters parallel liegt. Der Erfindung liegt daher die Aufgabe zugrunde, diese Zusatzverluste zu reduzieren. Dies gelingt erfindungsgemäss bei einer Anordnung mit den Merkmalen nach Anspruch 1. Der Überwachungskreis kann somit um so hochohmiger bemessen werden, je grösser die Empfindlichkeit des steuerbaren Widerstandes in dem Haltestromkreis ist.This holding current now causes additional losses during normal operation, which are of particular importance if a resistance of the monitoring circuit is parallel to the oscillating capacitor of the inverter. The object of the invention is therefore to reduce these additional losses. This is achieved according to the invention in the case of an arrangement having the features of
Besonders vorteilhaft ist die Anwendung der Erfindung bei einem Wechselrichter, dessen Anschwingen von der Spannung an einem Startkondensator abhängt, der seinerseits an einem über den Überwachungskreis geführten Spannungsteiler liegt und dessen Entladekreis geschlossen ist, wenn sich die Abschalteinrichtung im Abschaltzustand befindet: Die Erfindung ermöglicht es hierbei, den Überwachungsstromkreis und den Haltestromkreis unabhängig voneinander so zu bemessen, dass die Abschalteinrichtung nach einer Abschaltung auch bei der niedrigsten Speisespannung sicher in diesem Zustand bleibt, selbst wenn eine Elektrode in dem Überwachungsstromkreis gebrochen ist. Durch eine entsprechende Dimensionierung lässt sich dann das früher beobachtete intermittierende Abschalten und Neustarten des Wechselrichters vermeiden. Als Ursache dafür wurde nämlich ermittelt, dass der bei gebrochener Elektrode im Überwachungskreis fliessende Strom zwar nicht bei allen in Betracht kommenden Speisespannungen zum Aufrechterhalten des Abschaltzustandes ausreichte, jedoch genügend gross war, um den Startkondensator auf den Ansprechwert des Wechselrichters aufzuladen.It is particularly advantageous to use the invention in an inverter whose oscillation depends on the voltage at a starting capacitor, which in turn is connected to a voltage divider that is routed through the monitoring circuit and whose discharge circuit is closed when the switch-off device is in the switch-off state: the invention makes this possible to dimension the monitoring circuit and the holding circuit independently of one another such that the switch-off device remains securely in this state after a switch-off even at the lowest supply voltage, even if an electrode in the monitoring circuit is broken. The previously observed intermittent switching off and restarting of the inverter can then be avoided by appropriate dimensioning. The reason for this was found to be that the current flowing in the monitoring circuit when the electrode was broken was not sufficient to maintain the switch-off state at all supply voltages under consideration, but was sufficiently large to charge the starting capacitor to the response value of the inverter.
Vorzugsweise ist der steuerbare Widerstand im Haltestromkreis ein Transistor, dessen Steuerkreis einem Widerstand im Überwachungsstromkreis parallel geschaltet ist. Ein derartiges Ausführungsbeispiel der Erfindung wird anhand der Figuren näher erläutert; es zeigen:
- Fig. 1 ein Schaltbild der erfindungsgemässen Anordnung und
- Fig. 2 die Relation verschiedener Grenzwerte.
- Fig. 1 is a circuit diagram of the arrangement according to the invention and
- Fig. 2 shows the relation of different limit values.
Der mit W bezeichnete Wechselrichter wird über die Klemmen w1 mit einer Speisespannungsquelle von einem Hochsetzsteller H versorgt, der seinerseits an einem Wechselspannungsnetz N liegt. Zwischen den Klemmen w1, w2 liegen in Reihenschaltung die Transistoren V1, V2, die von einem Steuersatz S abwechselnd durchgesteuert werden. Letzterer enthält hierzu Sekundärwicklungen t2, t3 eines Sättigungstransformators T, dessen Primärwicklung t1 in Reihe mit einem Umschwingkondensator C1 und einem dazwischenliegenden Lastkreis parallel zu dem Transistor V1 angeordnet ist; der Lastkreis selbst besteht aus zwei parallel geschalteten, gleichartig aufgebauten Lampenstromkreisen, von denen jeder einen Serienresonanzkreis C01, L01; C02, L02 und die heizbaren Elektroden e11, e12; e21, e22 einer Entladungslampe E1, E2 enthält, wobei jeweils der Kondensator des Serienresonanzkreises zwischen den Elektroden einer Lampe angeordnet ist.The inverter denoted by W is supplied via terminals w1 with a supply voltage source from a step-up converter H, which in turn is connected to an AC voltage network N. The transistors V1, V2 are connected in series between the terminals w1, w2 and are controlled alternately by a control set S. For this purpose, the latter contains secondary windings t2, t3 of a saturation transformer T, the primary winding t1 of which is arranged in series with a switching capacitor C1 and an intermediate load circuit in parallel with the transistor V1; the load circuit itself consists of two parallel, identical lamp circuits, each of which has a series resonance circuit C01, L01; C02, L02 and the heated electrodes e11, e12; contains e21, e22 of a discharge lamp E1, E2, the capacitor of the series resonant circuit being arranged in each case between the electrodes of a lamp.
Die Betriebsfrequenz des Wechselrichters ist im wesentlichen durch den Sättigungstransformator T bestimmt und liegt etwas höher als die Resonanzfrequenz der in den Lampenstromkreisen liegenden Serienresonanzkreise.The operating frequency of the inverter is essentially determined by the saturation transformer T and is somewhat higher than the resonance frequency of the series resonance circuits located in the lamp circuits.
Eine bistabile Abschalteinrichtung A sorgt für eine dauernde Abschaltung des Wechselrichters W, wenn das Zeitintegral des Stromes in einem der Lampenstromkreise einen vorgegebenen Grenzwert übersteigt. Hierzu enthält die bistabile Schalteinrichtung einen Thyristor V3, dessen Steuerstrecke über eine Schaltdiode D2 an einem Kondensator C5 liegt, der über einen Entladezweig mit dem Widerstand R4 und Diode D3 der Schaltstrecke des Thyristors V3 parallel geschaltet ist. C5 ist einem Widerstand R3 parallel geschaltet, der mit einem weiteren Widerstand R2 einen Spannungsteiler bildet, der über zwei Entkopplungsdioden D11, D12 an zwei Kondensatoren C41, C42.angeschlossen ist; diese Kondensatoren bilden jeweils mit einem Widerstand R11, R12 einen Spannungsteiler, an dem eine vom Strom in den Lampenstromkreisen abhängige Spannung auftritt; jeder Spannungsteiler liegt hierzu bei durchgesteuertem Transistor V2 des Wechselrichters parallel zu einer Drossel L01 bzw. L02 der Serienresonanzkreise. Wenn daher eine der Lampen nicht zündet, ihre Lampenstromkreise dann voraussetzungsgemäss im Resonanzbetrieb arbeiten, tritt an der zugehörigen Drossel und dem daran angeschlossenen Spannungsteiler eine so hohe Spannung auf, dass der Thyristor V3 der Abschalteinrichtung A nach einer gewissen Zeit durchgesteuert wird. V3 schliesst dann über Diode D5 eine Sekundärwicklung t4 des Sättigungstransformators T kurz, so dass der Wechselrichter nicht mehr schwingen kann. Der Lastkreis des Thyristors ist über einen Haltestromkreis an w1, w2 angeschlossen, wobei dieser Haltestromkreis in Reihenschaltung eine Diode D6, einen Widerstand R7 und einen Transistor V4 enthält. Ferner liegt der Thyristor V3 über einen Widerstand R10 im Entladekreis eines Startkondensators C3, dessen Spannung über eine Schaltdiode D4 dem Steuersatz S zugeführt ist: Wenn die Spannung an diesem Startkondensator einen durch diese Schaltdiode bestimmten Grenzwert erreicht, beginnt der Wechselrichter zu schwingen. Dieser Startkondensator liegt an einem Widerstand R5, der zusammen mit dem Widerstand R10 und dem Überwachungskreis an der Speisegleichspannung liegt; der Überwachungskreis enthält hierbei einen Widerstand R6, die Elektroden e11, e21, eine Diode D7 und einen Widerstand R9. Dem Widerstand R9 ist über einen Widerstand R8 die Steuerstrecke des Transistors V4 parallel geschaltet.A bistable shutdown device A ensures a permanent shutdown of the inverter W when the time integral of the current in one of the lamp circuits exceeds a predetermined limit value. For this purpose, the bistable switching device contains a thyristor V3, the control path of which is connected via a switching diode D2 to a capacitor C5 which is connected in parallel with the resistor R4 and diode D3 of the switching path of the thyristor V3 via a discharge branch. C5 is connected in parallel with a resistor R3, which forms a voltage divider with a further resistor R2, which is connected to two capacitors C41, C42 via two decoupling diodes D11, D12; these capacitors each form a voltage divider with a resistor R11, R12, at which a voltage that depends on the current in the lamp circuits occurs; For this purpose, each voltage divider lies parallel to a choke L01 or L02 of the series resonant circuits when the transistor V2 of the inverter is turned on. Therefore, if one of the lamps does not ignite and its lamp circuits operate in resonance mode as required, the associated choke and the voltage divider connected to it generate such a high voltage that the thyristor V3 of the shutdown device A is turned on after a certain time. V3 then short-circuits a secondary winding t4 of the saturation transformer T via diode D5, so that the inverter can no longer oscillate. The load circuit of the thyristor is connected to w1, w2 via a holding circuit this holding circuit contains a diode D6, a resistor R7 and a transistor V4 in series. Furthermore, the thyristor V3 is connected via a resistor R10 in the discharge circuit of a starting capacitor C3, the voltage of which is fed to the control unit S via a switching diode D4: when the voltage across this starting capacitor reaches a limit value determined by this switching diode, the inverter begins to oscillate. This starting capacitor is connected to a resistor R5 which, together with the resistor R10 and the monitoring circuit, is connected to the DC supply voltage; the monitoring circuit contains a resistor R6, the electrodes e11, e21, a diode D7 and a resistor R9. The control path of the transistor V4 is connected in parallel with the resistor R9 via a resistor R8.
Da über den Überwachungskreis nicht mehr der Haltestrom zu fliessen braucht, kann er und somit der ihn einschliessende Spannungsteiler für C3 entsprechend hochohmig bemessen werden, so dass er im Normalbetrieb (wenn sich die Abschalteinrichtung im Normalzustand befindet) nur vernachlässigbar geringe Verluste verursacht. Der Spannungsteiler braucht dann lediglich so bemessen zu werden, dass an C3 bei der kleinsten in Betracht kommenden Speisespannung sowie bei intakten Elektroden der Anschwinggrenzwert der Spannung erreicht wird, vorausgesetzt, die Abschalteinrichtung befindet sich im Normalzustand. Die Empfindlichkeit des Transistors V4 und sein Steuerkreis sind dann so zu bemessen, dass der bei gebrochener Elektrode fliessende, im wesentlichen konstante Strom ausreicht, um den Transistor in die Sättigung zu steuern, wobei vorausgesetzt ist, dass sich die Abschalteinrichtung A im Abschaltzustand befindet und der dann über den Haltestromkreis fliessende Strom über dem Rückkippgrenzwert IH1 der Abschalteinrichtung A liegt, also bei der niedrigsten in Betracht kommenden Speisespannung der erforderliche Mindesthaltestrom IH2 fliesst.Since the holding current no longer needs to flow through the monitoring circuit, it and the voltage divider for C3 enclosing it can be dimensioned with a correspondingly high resistance, so that it causes only negligible losses in normal operation (when the shutdown device is in the normal state). The voltage divider then only needs to be dimensioned in such a way that the start-up limit of the voltage is reached at C3 with the smallest supply voltage under consideration and with intact electrodes, provided the shutdown device is in the normal state. The sensitivity of the transistor V4 and its control circuit are then to be dimensioned such that the essentially constant current flowing when the electrode is broken is sufficient to control the transistor into saturation, provided that the switch-off device A is in the switch-off state and the then current flowing through the holding circuit is above the tilt-back limit value I H1 of the disconnection device A, that is to say the required minimum holding current IH2 flows at the lowest supply voltage that is possible.
In Fig. 2 ist die Relation dieser Ströme und Strombereiche dargestellt: Die erste Zeile zeigt die Lage des Rückkippbereiches, der mit dem Rückkippgrenzwert IH1 endet. Zeile 2 zeigt den Bereich der zulässigen Halteströme IH, dessen Mindesthaltestrom IH2 einen Sicherheitsabstand von dem Rückkippgrenzwert IH1 hat.The relationship of these currents and current ranges is shown in FIG. 2: The first line shows the position of the tilt-back range which ends with the tilt-back limit value I H1 . Line 2 shows the range of the permissible holding currents I H , the minimum holding current IH2 of which is at a safety distance from the tilt-back limit value I H1 .
Die dritte Zeile zeigt den Bereich der im Abschaltzustand von A möglichen Überwachungsströme IB, der in den Rückkippbereich ragt. Transistor V4 sorgt jedoch dafür, dass selbst bei niedrigster Speisespannung und gebrochener Elektrode (Überwachungsstrom IB2) im Haltestromkreis wenigstens der Mindesthaltestrom IH2 fliesst.The third line shows the range of the monitoring currents I B possible when A is switched off, which projects into the tilt-back range. However, transistor V4 ensures that at least the minimum holding current IH2 flows in the holding circuit even with the lowest supply voltage and broken electrode (monitoring current I B2 ).
Zeile 4 zeigt schliesslich den Bereich der im Normalbetrieb über den Spannungsteiler von Startkondensator C3 fliessenden Überwachungsströme IB. Dieser Spannungsteiler ist so bemessen, dass der Maximalwert IB1 des Überwachungsstromes unter dem Mindestansprechwert IB2 liegt, V4 also im Normalbetrieb praktisch sperrt.Line 4 finally shows the range of the monitoring currents I B flowing through the voltage divider of the starting capacitor C3 in normal operation. This voltage divider is dimensioned such that the maximum value I B1 of the monitoring current is below the minimum response value I B2 , ie V4 practically blocks in normal operation.
Claims (5)
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| AT83112842T ATE26376T1 (en) | 1982-12-23 | 1983-12-20 | INVERTER SHUTDOWN ARRANGEMENT. |
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE3247863 | 1982-12-23 | ||
| DE19823247863 DE3247863A1 (en) | 1982-12-23 | 1982-12-23 | ARRANGEMENT FOR SWITCHING OFF A INVERTER |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| EP0111929A1 EP0111929A1 (en) | 1984-06-27 |
| EP0111929B1 true EP0111929B1 (en) | 1987-04-01 |
Family
ID=6181649
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| EP83112842A Expired EP0111929B1 (en) | 1982-12-23 | 1983-12-20 | Arrangement for switching off an inverter |
Country Status (6)
| Country | Link |
|---|---|
| US (1) | US4616158A (en) |
| EP (1) | EP0111929B1 (en) |
| JP (1) | JPS59123199A (en) |
| AT (1) | ATE26376T1 (en) |
| DE (2) | DE3247863A1 (en) |
| FI (1) | FI77349C (en) |
Families Citing this family (29)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE3412942C2 (en) * | 1984-04-06 | 1986-02-20 | Trilux-Lenze Gmbh + Co Kg, 5760 Arnsberg | Electronic ballast for several fluorescent lamps |
| DE3503778C2 (en) * | 1985-02-05 | 1986-11-20 | Trilux-Lenze Gmbh + Co Kg, 5760 Arnsberg | Fluorescent lamp ballast |
| JP2754531B2 (en) * | 1986-09-30 | 1998-05-20 | 東芝ライテック株式会社 | Directly connected discharge lamp lighting device |
| US4980611A (en) * | 1988-04-05 | 1990-12-25 | Neon Dynamics Corporation | Overvoltage shutdown circuit for excitation supply for gas discharge tubes |
| JPH0658831B2 (en) * | 1988-12-15 | 1994-08-03 | 松下電工株式会社 | Discharge lamp lighting device |
| US5089753A (en) * | 1990-07-09 | 1992-02-18 | North American Philips Corporation | Arrangement for predicting failure in fluorescent lamp systems |
| US5130611A (en) * | 1991-01-16 | 1992-07-14 | Intent Patents A.G. | Universal electronic ballast system |
| US5111114A (en) * | 1991-06-18 | 1992-05-05 | L.P.S. Technology Co., Ltd. | Fluorescent lamp light ballast system |
| US5179509A (en) * | 1991-10-21 | 1993-01-12 | Jackson Ling | High-frequency and high-voltage power supply unit with internal protecting circuit |
| ATE143208T1 (en) * | 1992-03-02 | 1996-10-15 | Siemens Ag | CIRCUIT ARRANGEMENT FOR OPERATING SEVERAL FLUORESCENT LAMPS WITH ONE BALLAST |
| US5436529A (en) * | 1993-02-01 | 1995-07-25 | Bobel; Andrzej A. | Control and protection circuit for electronic ballast |
| US5420779A (en) * | 1993-03-04 | 1995-05-30 | Dell Usa, L.P. | Inverter current load detection and disable circuit |
| FR2707051B1 (en) * | 1993-06-10 | 1996-03-08 | Matsushita Electric Works Ltd | |
| US5493181A (en) * | 1994-03-22 | 1996-02-20 | Energy Savings, Inc. | Capacitive lamp out detector |
| US5686799A (en) * | 1994-03-25 | 1997-11-11 | Pacific Scientific Company | Ballast circuit for compact fluorescent lamp |
| TW266383B (en) * | 1994-07-19 | 1995-12-21 | Siemens Ag | Method of starting at least one fluorescent lamp by an electronic ballast and the electronic ballast used therefor |
| US5691606A (en) * | 1994-09-30 | 1997-11-25 | Pacific Scientific Company | Ballast circuit for fluorescent lamp |
| US5821699A (en) * | 1994-09-30 | 1998-10-13 | Pacific Scientific | Ballast circuit for fluorescent lamps |
| US6037722A (en) * | 1994-09-30 | 2000-03-14 | Pacific Scientific | Dimmable ballast apparatus and method for controlling power delivered to a fluorescent lamp |
| US5596247A (en) * | 1994-10-03 | 1997-01-21 | Pacific Scientific Company | Compact dimmable fluorescent lamps with central dimming ring |
| WO1997024016A1 (en) * | 1995-12-26 | 1997-07-03 | General Electric Company | Control and protection of dimmable electronic fluorescent lamp ballast with wide input voltage range and wide dimming range |
| US5925986A (en) * | 1996-05-09 | 1999-07-20 | Pacific Scientific Company | Method and apparatus for controlling power delivered to a fluorescent lamp |
| GB9622768D0 (en) * | 1996-11-01 | 1997-01-08 | Lab Craft Limited | Fluorescent lamp failure warning device |
| US5866993A (en) * | 1996-11-14 | 1999-02-02 | Pacific Scientific Company | Three-way dimming ballast circuit with passive power factor correction |
| US5798617A (en) * | 1996-12-18 | 1998-08-25 | Pacific Scientific Company | Magnetic feedback ballast circuit for fluorescent lamp |
| US6111368A (en) * | 1997-09-26 | 2000-08-29 | Lutron Electronics Co., Inc. | System for preventing oscillations in a fluorescent lamp ballast |
| AU732605B1 (en) * | 2000-06-14 | 2001-04-26 | Brenex Electrics Pty Limited | Control circuits for fluorescent tubes |
| DE10046443A1 (en) * | 2000-09-18 | 2002-03-28 | Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh | Electronic circuit for the detection of the change in gas discharge lamps |
| CN101060737A (en) * | 2006-04-19 | 2007-10-24 | 皇家飞利浦电子股份有限公司 | A circuit of displaying the functional status of detecting lamp and ballast |
Family Cites Families (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4168453A (en) * | 1977-12-28 | 1979-09-18 | Datapower, Inc. | Variable intensity control apparatus for operating a gas discharge lamp |
| JPS5535272A (en) * | 1978-09-04 | 1980-03-12 | Japan Storage Battery Co Ltd | Detector for overvoltage of inverter output |
| JPS55144780A (en) * | 1979-04-24 | 1980-11-11 | Nippon Denso Co Ltd | Converter |
| JPS5635838U (en) * | 1979-08-28 | 1981-04-07 | ||
| SU877696A1 (en) * | 1980-02-25 | 1981-10-30 | Московский Ордена Трудового Красного Знамени Инженерно-Строительный Институт Им.В.В.Куйбышева | Inverter protection device |
| US4471422A (en) * | 1981-01-09 | 1984-09-11 | Wide-Lite International Corporation | Dc-to-ac Inverter |
| DE3112577A1 (en) * | 1981-03-30 | 1982-10-14 | Patra Patent Treuhand | Ballast arrangement for operating low-pressure discharge lamps |
| SU970554A1 (en) * | 1981-05-08 | 1982-10-30 | Новочеркасский Ордена Трудового Красного Знамени Политехнический Институт Им.Серго Орджоникидзе | Device for thermal protection of converter gates |
| DE3273928D1 (en) * | 1981-07-31 | 1986-11-27 | Siemens Ag | Converter |
| US4455509A (en) * | 1983-05-16 | 1984-06-19 | Crum Stephen T | Intrinsically safe lighting system |
-
1982
- 1982-12-23 DE DE19823247863 patent/DE3247863A1/en not_active Withdrawn
-
1983
- 1983-12-01 FI FI834398A patent/FI77349C/en not_active IP Right Cessation
- 1983-12-19 JP JP58240785A patent/JPS59123199A/en active Pending
- 1983-12-19 US US06/563,170 patent/US4616158A/en not_active Expired - Fee Related
- 1983-12-20 EP EP83112842A patent/EP0111929B1/en not_active Expired
- 1983-12-20 DE DE8383112842T patent/DE3370744D1/en not_active Expired
- 1983-12-20 AT AT83112842T patent/ATE26376T1/en active
Also Published As
| Publication number | Publication date |
|---|---|
| FI834398A (en) | 1984-06-24 |
| ATE26376T1 (en) | 1987-04-15 |
| JPS59123199A (en) | 1984-07-16 |
| EP0111929A1 (en) | 1984-06-27 |
| FI77349C (en) | 1989-02-10 |
| DE3247863A1 (en) | 1984-06-28 |
| FI834398A0 (en) | 1983-12-01 |
| US4616158A (en) | 1986-10-07 |
| FI77349B (en) | 1988-10-31 |
| DE3370744D1 (en) | 1987-05-07 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| EP0111929B1 (en) | Arrangement for switching off an inverter | |
| DE2903224C2 (en) | Circuit arrangement for igniting and feeding a metal vapor discharge lamp provided with a preheatable electrode | |
| EP0800335B1 (en) | Circuit for operating electric lamps | |
| DE3805510A1 (en) | CIRCUIT ARRANGEMENT FOR OPERATING A LOW-PRESSURE DISCHARGE LAMP | |
| DE2556734A1 (en) | EMERGENCY LIGHTING SYSTEM WITH INVERTER WITH HIGH EFFICIENCY | |
| EP0146683A1 (en) | DC-AC conventer | |
| DE19622803A1 (en) | Vehicle electrical power supply circuit for gas-discharge lamps | |
| DE3301632A1 (en) | INVERTER | |
| DE2425720C3 (en) | ||
| DE3626209A1 (en) | Ballast for at least one discharge lamp | |
| DE2924069C2 (en) | Circuit arrangement for igniting and operating a gas and / or vapor discharge lamp | |
| EP0564895B1 (en) | Electronic ballast for low pressure discharge lamps | |
| DE2425720A1 (en) | Equalising ballast circuit for discharge lamps - provides protection against resonance effects in phase lines | |
| EP0519220A1 (en) | Ballast with controlled heating time | |
| EP0111956B1 (en) | Circuit arrangement for operating high-pressure discharge lamps | |
| EP0120258B1 (en) | Energy economising circuit | |
| DE3511661A1 (en) | Ballast apparatus for gas-discharge lamps | |
| DE1589215C3 (en) | Circuit arrangement for Niederspanniingsleuchtstofflampen.die are fed from a vehicle battery or a similar direct voltage source | |
| DE3503778C2 (en) | Fluorescent lamp ballast | |
| DE3029672C2 (en) | ||
| EP0552389A1 (en) | Power supply method for an electro-filter | |
| DE4242174A1 (en) | Ballast for starting and operating high pressure gas discharge lamps | |
| DE2646621A1 (en) | Gas discharge lamps ballast circuit - is for two lamps in series and has two RC voltage doublers and voltage regulating transistor | |
| DE3331780A1 (en) | CIRCUIT ARRANGEMENT FOR IGNITING AND OPERATING A DISCHARGE LAMP | |
| DE3152951C2 (en) | Ballast |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PUAI | Public reference made under article 153(3) epc to a published international application that has entered the european phase |
Free format text: ORIGINAL CODE: 0009012 |
|
| AK | Designated contracting states |
Designated state(s): AT BE CH DE FR GB LI NL SE |
|
| 17P | Request for examination filed |
Effective date: 19840524 |
|
| 17Q | First examination report despatched |
Effective date: 19860409 |
|
| GRAA | (expected) grant |
Free format text: ORIGINAL CODE: 0009210 |
|
| AK | Designated contracting states |
Kind code of ref document: B1 Designated state(s): AT BE CH DE FR GB LI NL SE |
|
| REF | Corresponds to: |
Ref document number: 26376 Country of ref document: AT Date of ref document: 19870415 Kind code of ref document: T |
|
| REF | Corresponds to: |
Ref document number: 3370744 Country of ref document: DE Date of ref document: 19870507 |
|
| ET | Fr: translation filed | ||
| PLBE | No opposition filed within time limit |
Free format text: ORIGINAL CODE: 0009261 |
|
| STAA | Information on the status of an ep patent application or granted ep patent |
Free format text: STATUS: NO OPPOSITION FILED WITHIN TIME LIMIT |
|
| 26N | No opposition filed | ||
| PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: AT Payment date: 19901128 Year of fee payment: 8 |
|
| PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: SE Payment date: 19901212 Year of fee payment: 8 |
|
| PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: FR Payment date: 19901219 Year of fee payment: 8 |
|
| PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: BE Payment date: 19901228 Year of fee payment: 8 |
|
| PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: NL Payment date: 19901231 Year of fee payment: 8 |
|
| PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: CH Payment date: 19910322 Year of fee payment: 8 |
|
| PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: AT Effective date: 19911220 |
|
| PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: SE Effective date: 19911221 |
|
| PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: LI Effective date: 19911231 Ref country code: CH Effective date: 19911231 Ref country code: BE Effective date: 19911231 |
|
| BERE | Be: lapsed |
Owner name: SIEMENS A.G. BERLIN UND MUNCHEN Effective date: 19911231 |
|
| PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: NL Effective date: 19920701 |
|
| NLV4 | Nl: lapsed or anulled due to non-payment of the annual fee | ||
| PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: FR Effective date: 19920831 |
|
| REG | Reference to a national code |
Ref country code: CH Ref legal event code: PL |
|
| REG | Reference to a national code |
Ref country code: FR Ref legal event code: ST |
|
| PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: GB Payment date: 19931122 Year of fee payment: 11 |
|
| PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: DE Payment date: 19940216 Year of fee payment: 11 |
|
| PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: GB Effective date: 19941220 |
|
| EUG | Se: european patent has lapsed |
Ref document number: 83112842.6 Effective date: 19920704 |
|
| GBPC | Gb: european patent ceased through non-payment of renewal fee |
Effective date: 19941220 |
|
| PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: DE Effective date: 19950901 |