CN1481100A - Method of time space solution for estimating wave diretion of maultiple paths signals in correlative CDMA and its device - Google Patents

Method of time space solution for estimating wave diretion of maultiple paths signals in correlative CDMA and its device Download PDF

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CN1481100A
CN1481100A CNA031496881A CN03149688A CN1481100A CN 1481100 A CN1481100 A CN 1481100A CN A031496881 A CNA031496881 A CN A031496881A CN 03149688 A CN03149688 A CN 03149688A CN 1481100 A CN1481100 A CN 1481100A
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decorrelation
multipaths
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CN1207859C (en
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维 杨
杨维
陈俊仕
谈振辉
程时昕
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Beijing Jiaotong University
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Abstract

First, separation of user multipaths signals is carried out and the output of matched filter group under asynchronous multipaths channels is calculated by using connected matched filter group behind array antenna. Next, correlation process of time space united solution is carried out for output of matched filter group. Then, covariance matrix of user multipaths signals is estimated by using user decoupled multipaths signals. Calculation of covariance matrix eigenvalue decomposion is carried out. Finally, based on main eigenvector, estimating wave destination direction of user multipaths signals is realized. The device includes time space solution associative processor of user multipaths signals estimator of wave destination direction of user multipaths signals. The invented method and device is suitable for fine estimating wave destination direction of user multipaths signals by using time space solution associative detection technique in array antenna of CDMA system.

Description

Decorrelation CDMA multipath method for estimating signal wave direction and device when empty
Technical field
The invention belongs to code division multiple access cdma cellular field of wireless communications.
Background technology
The cdma cellular communication technology is simple with its frequency planning, power system capacity is big, ability of anti-multipath is strong, good communication quality, electromagnetic interference are little etc., and characteristics demonstrate huge development potentiality, are the mainstream technologys of future mobile communications.If particularly in cdma system, use array antenna can improve capacity, spectrum efficiency, communication quality and the coverage of system significantly and high-precision wireless location service is provided.The direction of arrival of user multipaths signal estimates that the user radio location technology that wave beam to down link forms, reduces to disturb and estimates based on angle has important function in the array antenna CDMA system, is one of key technology of array antenna CDMA system.
In the past few decades, proposed many signal direction of arrival DOA algorithm for estimating, be commonly referred to traditional DOA algorithm for estimating based on aerial array.Traditional DOA algorithm for estimating such as multiple signal classification method MUSIC and require the array number of aerial array more than signal number by invariable rotary technology estimated signal parameter ESPRIT algorithm, and signal source spatially can not be overlapping, otherwise aerial array can't effectively be estimated the DOA of signal source.
The up channel of cdma system is generally asynchronous multipath channel, and user job is in identical frequency range.Tens users are arranged in the typical cellular sub-district usually, and each user's signal can produce many single sub path again, makes traditional DOA method of estimation based on aerial array can not directly apply in the array antenna CDMA system.
Summary of the invention
Technical problem solved by the invention is, proposes a kind of decorrelation CDMA multipath method for estimating signal wave direction and device when empty.This method can effectively be differentiated and the direction of arrival of estimating user multipath signal accurately.The accurate estimation of the array antenna CDMA system user multipath signal direction of arrival of decorrelation detection technique when the device based on said method that the present invention proposes is very suitable for adopting sky.
Decorrelation CDMA multipath method for estimating signal wave direction during technical scheme of the present invention-sky:
The output that at first utilizes the matched filter banks that connects after the array antenna array element to carry out the separation of user multipaths signal and calculate matched filter banks under the asynchronous multipath channel, secondly the space-time joint decorrelation being carried out in the output of matched filter banks handles, utilize the user to separate the covariance matrix of lotus root multipath output signal estimating user multipath signal then, carry out the calculating of covariance matrix feature decomposition afterwards again, realize at last estimating based on the user multipaths signal direction of arrival of covariance matrix feature decomposition principal eigenvector.
Its process is as follows:
At first user multipaths signal is separated and the output of calculating matched filter banks: utilize matched filter banks user multipaths signal effectively to be separated and utilize the output of the property calculation matched filter banks that is associated of transmission signals signature waveform under the asynchronous multipath channel based on matched filter banks.
Decorrelation was handled when next carried out sky: decorrelation was handled when the desired user multipath signal of matched filter banks output was carried out sky, eliminate the interference of other multipath signals, and the user multipaths signal decorrelation disturbed of other multipaths of being eliminated or separate lotus root output, the space-time joint decorrelation handles that be based on the space-time joint correlation matrix contrary realize.
Estimate covariance matrix then: ask Estimation of covariance matrix to eliminating the desired user decoupled multipaths signal that other multipaths disturb, obtain desired user decoupled multipaths signal Estimation of covariance matrix, the calculating utilization of user's decoupled multipaths signal covariance matrix be long process window method.
Afterwards, calculating user decoupled multipaths signal covariance matrix is carried out feature decomposition, obtain the principal eigenvector of corresponding eigenvalue of maximum.
At last, realize the estimation of user multipaths signal direction of arrival: after obtaining principal eigenvector, utilize multiple signal classification method estimating user multipath signal direction of arrival based on principal eigenvector.
Decorrelation CDMA multipath signal direction of arrival estimation unit when empty.This device comprises: decorrelation processor A and user multipaths signal direction of arrival estimator B two parts during user multipaths signal empty, the input of the input termination array antenna baseband sampling signal of decorrelation processor A when empty, the input of the output termination user multipaths signal direction of arrival estimator B of decorrelation processor A when empty.
Below to the invention in each composition discussed respectively.
1. decorrelation is handled when empty
A. the user multipaths signal based on matched filter banks separates and calculating
1) received signal of array
Investigate one and go up line asynchronous multipath channel array antenna CDMA system, suppose that mobile channel is the frequency selectivity slow fading channel, the correlation time of channel is much larger than symbol period.Certain cellular cell has K user launching bpsk signal by multipath channel separately in the supposing the system.Like this, k the N bit signal that the user launched can be expressed as: x k ( t ) = A k Σ n = 0 N - 1 b k ( n ) c k ( t - nT b ) , k = 1 , . . . , K In [formula 1] formula, A kThe amplitude of representing k subscriber signal, b k(n) { 1 ,+1} represents the n bit signal of general transmission such as k user, c to ∈ k(t) k user's of expression frequency spreading wave has c k ( t ) = Σ g = 0 G - 1 c kg p ( t - gT c ) In [formula 2] formula, c Kg∈ 1, and+1} (g=0 ..., G-1) be its spreading code, p (t) is that width is T cCut general pulse, T bBe the bit interval time, G is defined as G=T b/ T cSpreading gain, its frequency spreading wave has normalized energy, promptly ∫ 0 T b | c k ( t ) | 2 = 1 . Equally, suppose that the information bit that each user launches is independently, the information bit of different user also is independently.
Suppose that base station array antenna has M array element, customer mobile terminal adopts single antenna.Like this, the baseband multi-path channel between k user transmitter and base station receiver can represent that its impulse response vector is with the many output of single input SIMO channels h k ( t ) = Σ l = 1 L α k , l ( t ) a k , l ( θ k , l ( t ) ) δ ( t - τ k , l ) [formula 3] wherein, L is each user's a multipath number, α K, lAnd τ K, lBe respectively the multiple decay and the time delay of k user l footpath signal, a k , l ( θ k , l ( t ) ) = [ a k , l , 1 ( θ k , l ( t ) ) , . . . , a k , l , M ( θ k , l ( t ) ) ] T / M Be that corresponding k user l footpath signal direction of arrival is θ K, l(t) array vector.
Like this, base station array antenna receives total signal and is r ( t ) = Σ k = 0 K x k ( t ) * h k ( t ) + w ( t ) = Σ n = 0 N - 1 Σ k = 1 K A k b k ( n ) Σ l = 1 L α k , l a k , l , m s k ( t - nT b - τ k , 1 ) + w ( t ) [formula 4] wherein, * represents convolution, μ K, l=A kα K, lBe the complex magnitude of k user l footpath signal of being received, w (t) is that average is 0, and covariance matrix is σ 2I MThe additive white Gaussian noise vector, I MIt is the unit matrix of M * M.
2) calculating of matched filter banks output
Use r m(t) signal of m array element reception of expression array antenna.The signal phasor that receives from formula 4, the m array elements can be expressed as r m ( t ) = Σ n = 0 N - 1 Σ k = 1 K A k b k ( n ) Σ l = 1 L c k , l , m s k ( t - nT b - τ k , l ) + w m ( t ) , m = 1 , . . . M [formula 5] wherein, c K, l, mJ, lα K, l, mIt is the complex gain that comprises multiple decay and direction of arrival.
All users and multipath composition thereof can provide sufficient statistical information in the output of all array element matched filter banks of array antenna to detecting numerical chracter.At t ∈ [nT b, (n+1) T b) time interval sampling that is matched with last k the user of array element m the 1st footpath frequency spreading wave is output as y k , l , m ( n ) = ∫ nT b + τ k , l ( n + 1 ) T b + τ k , l r m ( t ) s k ( t - nT b - τ k , l ) dt [formula 6]
The time delay expansion maximum of supposing Any user is no more than P mark space, and P is a positive integer, has
τ K, l≤ PTs, 1≤k≤K; 1≤l≤L [formula 7]
The received signal of this expression array antenna will be handled in length is the processing window of N=2P+1.Be the k user's of demodulation the n symbol, the user's matched filter output in corresponding each footpath of each bay is that formula 6 can be written as again y k , l , m ( n ) = Σ i = - P P Σ k ′ = 1 K A k ′ b k ′ ( n + i ) Σ l ′ = 1 L c k ′ , l ′ , m R ( k , l ) , ( k ′ , l ′ ) , m ( i ) + w k , l , m ( n ) , l = 1 , · · · , L ; m = 1 , · · · · , M
[formula 8] wherein, R (k, l), (k ', l '), m(i) be the cross-correlation that array element m goes up user's inhibit signal waveform, it is defined as R ( k , l ) , ( k ′ , l ′ ) , m ( i ) = ∫ - ∞ + ∞ s k ( t - nT b - τ k , l , m ) s k ′ ( t - nT b + iT b - τ k ′ , l ′ , m ) dt [formula 9] w K, l, m(n) expression array element m goes up the k user the 1st footpath in symbol n sampling noiset matched filtering output therebetween w k , l , m ( n ) = ∫ nT b + τ k , l ( n + 1 ) T b + τ k , l w m ( t ) s k ( t - nT b - τ k , l ) dt [formula 10] { w K, l, m(n) } for average be 0 multiple Gaussian random process, its covariance is
Figure A0314968800061
[formula 11]
Define t ∈ [nT now b, (n+1) T b] between symbolic vector b ( n ) = def ( b 1 ( n ) , b 2 ( n ) , · · · b K ( n ) ) T ∈ Ξ K Therefore, handling window scope preface received signal even at one can be expressed as = def ( ( b ( n - p ) ) T , · · · , ( b ( n ) ) T , · · · ( b ( n + p ) ) T ) T ∈ Ξ NK Similarly, the last sampling matched filtering output vector between symbol n of definition array element m is y k , m ( n ) = ( y k , 1 , m ( n ) , y k , 2 , m ( n ) · · · y k , L , m ( n ) ) T ∈ C L [formula 12] y m ( n ) = ( ( y 1 , m ( n ) ) T , ( y 2 , m ( n ) ) T , · · · · · · , ( y K , m ( n ) ) T ) T ∈ C KL They are linked as [formula 13] a preface of handling the window scope y m = ( ( y m ( n - p ) ) T , · · · ( y m ( n ) ) T , · · · ( y m ( n + p ) ) T ) T ∈ C NKL [formula 14] like this, array element m goes up the symbolic representation that total matched filtering sampling output can matrix and is
y m=R mC mA mB+w m[formula 15] wherein, cross-correlation matrix R mCan be expressed as R m = R m ( 0 ) R m ( - 1 ) R m ( - 2 ) . . . 0 k R m ( 1 ) R m ( 0 ) R m ( - 1 ) . . . 0 k . . . . . . . . . . . . . . . 0 k 0 k 0 k . . . R m ( 0 ) ∈ C NKL × NKL R m ( i ) = R 1,1 , m ( i ) R 1,2 , m ( i ) . . . R 1 , K , m ( i ) R 2,1 , m ( i ) R 2,2 , m ( i ) . . . R 2 , K , m ( i ) . . . . . . . . . . . . R K , 1 , m ( i ) R K , 2 , m ( i ) . . . R K , K , m ( i ) ∈ C KL × KL Wherein, matrix R K, k ', m (i)∈ R L * LBe cross-correlation matrix, its element R (k, l), (k ', l '), m(i) definition is identical with formula 9.Because τ K, l≤ PT bWith at [O, T b] outer s k(t) be 0, so have
R m(i)=0,|i|>P R m ( - i ) = R m T ( i )
Channel matrix C mCan be expressed from the next C m = diag ( C m ( n - p ) , C m ( n - p + 1 ) , · · · , C m ( n + p ) ) T ∈ C NKL × NK C m ( n ) = diag ( c 1 , m ( n ) , c 2 , m ( n ) , · · · , c K , m ( n ) ) ∈ C KL × K c k , m ( n ) = ( c k , 1 ( n ) , c k , 2 ( n ) , · · · , c k , L ( n ) ) T ∈ C L .
The signal amplitude matrix can be expressed as
A m=diag(A m,A m,…,A m)∈C NK×NK
A m=diag (A 1, A 2..., A K) ∈ CK * KUse w mExpression array element m goes up the noise vector of matched filter output, and then the preface of all sensing array elements of array antenna connects the matched filtering output vector and is
Wherein, y is defined as y=RCAB+W [formula 16] y = ( y 1 T , y 2 T , · · · , y m T ) T ∈ C MNKL And R=diag (R 1, R 2..., R M) ∈ C MNKL * MNKL, C=diag (C 1, C 2..., C M) ∈ CMNKL * MNKL, A=diag (A 1, A 2..., A M) ∈ CMNK * MNK, B=(b T, b T..., b T) ∈ Ξ MNK, W = ( w 1 T , w 2 T , · · · , w M T ) ∈ C MNKL .
The calculating of decorrelator output when B. empty
For the contrary output that is added on matched filter of lotus root user data information decorrelation detector with correlation matrix is conciliate in the interference of eliminating multipath signal.Because correlation matrix R is positive definite always in practice, its Linear Mapping has the character of Hermitian and positive definite, and therefore, they contrary always exists.Multiply by inverse matrix R at the two ends of formula 16 -1Decorrelation is output as when obtaining sky
Z=CAb+R -1W [formula 17] wherein, Z = ( Z 1 T , Z 2 T , · · · , Z M T ) ∈ C MNKL Z m = ( ( Z m ( n - p ) ) T , · · · , ( Z m ( n ) ) T , · · · ( Z m ( n + p ) ) T ) T ∈ C NKL [formula 18] Z m ( n ) = ( ( Z 1 , m ( n ) ) T , ( Z 2 , m ( n ) ) T , · · · ( Z K , m ( n ) ) T ) T ∈ C KL [formula 19] Z k , m ( n ) = ( Z k , 1 , m ( n ) , Z k , 2 , m ( n ) , · · · , Z k , L , m ( n ) ) T ∈ C L [formula 20] is obvious, Z K, m (n)Each element contain that array element m goes up single decoupled multipaths signal of user k and array element m goes up other the multipath interference signal that can separate lotus root and has been eliminated.Therefore, each multipath signal that can separate lotus root can be detected independently.2, the user multipaths signal direction of arrival is estimated
A. the calculating of covariance matrix
For estimating the direction of arrival θ of k user l footpath signal K, lNeed at first estimate its pairing covariance matrix of separating the output of lotus root array.In practice, the exact value of covariance matrix is unavailable, must estimate by the data that receive.Typical in the case processing mode is exactly the employing estimation that forms true covariance matrix by Q continuous observation or sampling.For obtaining continuous Q observation or sampling, need be that Q the continuous processing window of N=2P+1 is handled to length, the adjacent processing window symbol that slides over each other.Can only open a long processing window when concrete the processing, be called the long process window, be Q observation of equidistant intercepting or sampling about reference point to handle window center then.Adopt this method can obtain the better estimation of covariance matrix.
Can estimate on m the array element that from formula 20 k user l footpath signal separate lotus root signal Z when q mark space empty K, l, m (q)K user l footpath signal is separated the signal of lotus root signal on all array elements of array antenna when q mark space empty pile up, can obtain M * 1 vector Z k , l ( q ) = ( Z k , l , 1 ( q ) , Z k , l , 2 ( q ) · · · , Z k , l , M ( q ) ) T [formula 21] therefore separates being estimated as of lotus root signal covariance matrix when adopting directly empty of corresponding k the user the 1st of long process window processing method R ^ k , l = 1 Q { Z k , l ( r - Q - 1 2 ) ( Z k , l ( r - Q - 1 2 ) ) H + · · · + Z k , l ( r ) ( Z k , l ( r ) ) H + · · · + Z k , l ( r + Q - 1 2 ) ( Z k , l ( r + Q - 1 2 ) ) H } [formula 22] wherein, Q is assumed to be odd number, and r is a reference point.
B. the feature decomposition of covariance matrix
To resulting sampling Estimation of covariance matrix
Figure A0314968800083
Carry out feature decomposition, obtain covariance matrix R K, lPrincipal eigenvector e 1, k, lEstimation
C. the user multipaths signal direction of arrival is estimated
At last, realize the estimation of user multipaths signal direction of arrival.In the estimation that obtains k user l footpath covariance matrix feature decomposition principal eigenvector of de-correlated signals when empty After, can realize k user l footpath signal direction of arrival θ K, lEstimation Concrete steps are:
At first, structure spatial spectrum function, P MU ( θ k , l ) = [ 1 - | | a k , l H ( θ i , l ) e ^ 1 , k , l | | 2 ] - 1 [formula 23] wherein, reciprocity pitch arrays antenna has a k , l H ( θ k , l ) = [ 1 , e - j 2 πd λ sin ( θ k , l ) , . . . , e - j 2 πd λ ( M - 1 ) sin ( θ k , l ) ] / M
Then, search volume spectral function R MUThe spectrum peak direction of arrival that just can obtain corresponding k user l footpath signal estimate.The direction of arrival θ of corresponding k user l footpath signal K, lBe estimated as θ ^ k , l = arg max θ k , l { [ 1 - | | a k , l H ( θ k , l ) e ^ 1 , k , l | | 2 ] - 1 } [formula 24]
Beneficial effect of the present invention: at first since the estimation of user multipaths signal direction of arrival be based on user multipaths signal separate that lotus root output realizes, eliminated the interference of other multipath signals, therefore, the advantage of this method is exactly that estimation performance is good.Secondly, this method does not require the number of signals of the array number of array antenna more than user and multipath thereof; Simultaneously, this method does not need to detect the signal source number of user and multipath thereof, and these are that traditional multiple signal classification method is necessary.In addition, owing to only need the single spatial spectrum peak of search, therefore, corresponding estimated result is very reliable.These all make the present invention be very suitable for the demanding situation of user's multipath direction of arrival estimated accuracy, particularly when the array antenna CDMA system adopts the multiuser detection that decorrelation is handled when empty.
Description of drawings
Fig. 1 is the device general diagram.
Fig. 2 is a matched filter banks schematic diagram after each array element.
Fig. 3-the 6th, the performance legend of Wave arrival direction estimating method that the present invention carries.
Embodiment
The present invention is described in further detail below in conjunction with accompanying drawing.
The method according to this invention is applicable to the CDMA mobile communication system of any employing array antenna.
Fig. 1 has provided this method and has been applied to the device detailed structure schematic diagram that the array antenna direct sequence spread spectrum codes is divided multiple access DS-CDMA mobile communication system.
This device comprises: decorrelation processor A and user multipaths signal direction of arrival estimator B two parts are formed during user multipaths signal empty, the input of the input termination baseband sampling signal of decorrelation processor A when empty, the input of the output termination user multipaths signal direction of arrival estimator B of decorrelation processor A when empty.
The decorrelation processor A comprises that user multipaths signal based on matched filter banks separates and decorrelation processing module A102 when computing module A101 and sky when empty, and user multipaths signal direction of arrival estimator B comprises user's decoupled multipaths signal correlation matrix computing module B101, covariance matrix feature decomposition module B102, user multipaths signal direction of arrival estimation module B103.Wherein separate and computing module A101, decorrelation processing module A102, user's decoupled multipaths signal correlation matrix computing module B101, covariance matrix feature decomposition module B102, user multipaths signal direction of arrival estimation module B103 are connected in series successively in proper order when empty based on the user multipaths signal of matched filter banks.
Concrete signal processing is as follows: at first, the base-band analog signal that each array element of array antenna is received into becomes digital signal after modulus A/D conversion, the user multipaths signal that enters then based on matched filter banks separates and calculator modules A101, this module realizes the separation of user multipaths signal by matched filter banks according to the different delay of user multipaths signal, while connects matched filtering output vector y, decorrelation processing module A102 when its result offers sky according to the preface that formula 16 calculates all sensing array elements of array antenna.When sky, in the decorrelation processing module preface is connected matched filtering output vector y and carry out space-time joint decorrelation processing, eliminate the interference of other multipath signals, and the lotus root of separating of the desired user multipath signal of other multipaths interference that are eliminated is exported Z K, l (q)In user multipaths signal correlator block B101, export Z according to the lotus root of separating of 22 pairs of desired user multipath signals of formula K, l (q)Carry out correlation computations, obtain the desired user multipath signal and separate lotus root and export true covariance matrix R K, lEmploying estimate Covariance matrix feature decomposition module B102 receives the output of user multipaths signal correlator block B101 and the employing of desired user decoupled multipaths signal covariance matrix is estimated
Figure A0314968800102
Matrix carries out feature decomposition, obtains principal eigenvector e 1, k, lEstimation
Figure A0314968800103
And will Be input to user multipaths signal direction of arrival estimator module B103.User multipaths signal direction of arrival estimator module B103 receives After, obtain desired user multipath signal direction of arrival θ K, lEstimation
Figure A0314968800106
Fig. 3-6 has provided based on array antenna DS-CDMA system user multipath signal direction of arrival estimation under the asynchronous multipath channel of space-time joint decorrelation output the result of signal to noise ratio snr.Number of users, spread processing gain and array structure have been provided respectively to estimated Effect on Performance.For estimate estimation performance to 50 times independently simulation result carried out on average, and adopted standard error SD as evaluation index, it is defined as SD = 1 U Σ u = 1 U ( θ ^ k , l - θ k , l ) 2 [formula 25] wherein, U is the number of times of independent experiment.
Concrete simulated conditions is as follows: the employing array element distance is that the evenly equally spaced 5 array element linear array antennas in half wavelength lambda/2 receive the BPSK multipath signal.Be without loss of generality, suppose that channel is two footpath rayleigh fading channels, each directly has identical energy, and the relative delay of multipath signal is in a mark space.Spreading code is that the gain of picked at random is 16 frequency expansion sequence, obtains Estimation of covariance matrix with 20 times observations or sampling length
Figure A0314968800108
Might as well suppose to have respectively 3 and 6 users to be randomly dispersed in the sub-district, user's footpath direction of arrival that expectation is estimated is 27 °.
As seen from Figure 3, method proposed by the invention is estimated very effective, accurate to the direction of arrival of user multipaths signal.And along with the increase estimation performance of number of users almost is identical.This is can eliminate multiple access interference MAI because decorrelation is handled on principle.
Decorrelation output and direct DOA estimated performance when Fig. 4 has compared based on sky based on matched filter banks output.Decorrelation output estimation performance is much more accurate than directly exporting estimation performance based on matched filter banks when Fig. 4 can be clear that based on sky, this also is can eliminate multiple access interference MAI because decorrelation is handled on principle, is inevitable and the algorithm multiple access that directly output is estimated based on matched filter banks is disturbed MAI.When signal to noise ratio increased, decorrelation output estimation performance can also be further improved during based on sky, directly but can not get improving owing to multiple access disturbs the corresponding increase of MAI based on matched filter banks output estimation performance on the contrary.
Fig. 5 has shown the influence of spread processing gain to estimated performance.Even the result of Fig. 5 shows that estimation performance is very accurate under the gain of low spread processing, therefore, along with the improvement of the increase estimated performance of spread processing gain will can be not clearly.
Fig. 6 has shown the influence of array structure to estimated performance.Can observe from Fig. 6, when strengthen between array element apart from the time, estimation performance can obtain improving more significantly.This be since in this case the resolving power of array antenna be enhanced.
It is worthy of note, even when two of different user or many strips directly arrive the direction of arrival of aerial array when identical, because it is that each CDMA user has been assigned with unique spreading code that method has been utilized the intrinsic characteristic of CDMA signal, therefore the direction of arrival in each son footpath still can effectively be estimated in this case.

Claims (7)

1. the CDMA multipath of decorrelation when empty method for estimating signal wave direction, the output that it is characterized in that at first utilizing the matched filter banks that connects after the array antenna array element to carry out the separation of user multipaths signal and calculate matched filter banks under the asynchronous multipath channel, secondly the space-time joint decorrelation being carried out in the output of matched filter banks handles, utilize the covariance matrix of user's decoupled multipaths signal estimating user multipath signal then, carry out the calculating of covariance matrix feature decomposition afterwards again, realize at last estimating based on the user multipaths signal direction of arrival of covariance matrix feature decomposition principal eigenvector.
2. decorrelation CDMA multipath method for estimating signal wave direction when empty according to claim 1, the calculating that it is characterized in that matched filter banks output are to utilize that the characteristic that is associated of transmission signals signature waveform realizes under the asynchronous multipath channel.
3. decorrelation CDMA multipath method for estimating signal wave direction when empty according to claim 1 is characterized in that the space-time joint decorrelation handles that be based on the space-time joint correlation matrix contrary realize.
4. according to described decorrelation CDMA multipath method for estimating signal wave direction when empty of claim 1, it is characterized in that user's decoupled multipaths signal Estimation of covariance matrix utilizes long process window method to realize.
5. decorrelation CDMA multipath method for estimating signal wave direction is characterized in that utilizing the multiple signal classification method estimating user multipath signal direction of arrival based on principal eigenvector during according to the described sky of claim 1.
6. the CDMA multipath of decorrelation when empty signal direction of arrival estimation unit, decorrelation processor (A) and user multipaths signal direction of arrival estimator (B) two parts are formed when it is characterized in that this device by user multipaths signal empty, the input of the input termination array antenna baseband sampling signal of decorrelation processor (A) when empty, the input of the output termination user multipaths signal direction of arrival estimator (B) of decorrelation processor (A) when empty.
7. decorrelation CDMA multipath signal direction of arrival estimation unit during according to the described sky of claim 6, decorrelation processor (A) comprises based on the user multipaths signal of matched filter banks and separating and decorrelation processing module (A102) when computing module (A101) and sky when it is characterized in that sky, user multipaths signal direction of arrival estimator (B) comprises user multipaths signal correlation matrix computing module (B101), covariance matrix feature decomposition module (B102), user multipaths signal direction of arrival estimation module (B103), wherein the user multipaths signal based on matched filter banks separates and computing module (A101), decorrelation processing module (A102) when empty, user multipaths signal correlation matrix computing module (B101), covariance matrix feature decomposition module (B102), user multipaths signal direction of arrival estimation module (B103) order successively is connected in series.
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CN100345402C (en) * 2004-07-06 2007-10-24 中兴通讯股份有限公司 High resolution estimation method for incoming wave direction of mobile communication system
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CN101521536B (en) * 2004-03-12 2012-09-05 北京交通大学 Mobile station receiving circuit for CDMA system sparetime spread spectrum method
CN100345402C (en) * 2004-07-06 2007-10-24 中兴通讯股份有限公司 High resolution estimation method for incoming wave direction of mobile communication system
CN100369390C (en) * 2004-07-22 2008-02-13 中兴通讯股份有限公司 Method of receiving radio transmission by multiple antenna array
CN100431386C (en) * 2005-05-12 2008-11-05 上海原动力通信科技有限公司 Method for estimating arrival direction of common frequency multi-cell terminal
US8054785B2 (en) 2005-05-12 2011-11-08 Shanghai Ultimate Power Communications Technology Co., Ltd. Method for estimating direction-of-arrival of terminal in multiple co-frequency cells
CN101199125B (en) * 2005-05-25 2011-12-28 捷讯研究有限公司 Joint space-time optimum filters (JSTOF) for interference cancellation
CN101297564B (en) * 2005-08-15 2011-11-02 捷讯研究有限公司 Joint space-time optimum filters (JSTOF) for interference cancellation
CN101283513B (en) * 2005-08-15 2011-08-17 捷讯研究有限公司 Joint space-time optimum filters (ISTOF) using singular value decompositions (SVD)
CN101283610B (en) * 2005-08-15 2012-12-05 捷讯研究有限公司 Mobile wireless communication device and method for reducing co-channel interference
WO2007137484A1 (en) * 2006-05-11 2007-12-06 Shanghai Jiao Tong University A channel estimation method and the device thereof
WO2008052481A1 (en) * 2006-10-31 2008-05-08 Huawei Technologies Co., Ltd. Signal detection method and receiver in a multi-antennae digital communication system
CN103593509A (en) * 2013-10-24 2014-02-19 西安理工大学 Method for analyzing plasma-sheath-caused multipath interference on aircraft surfaces
CN103593509B (en) * 2013-10-24 2017-01-11 西安理工大学 Method for analyzing plasma-sheath-caused multipath interference on aircraft surfaces
CN105007096A (en) * 2015-07-02 2015-10-28 北京理工大学 Method for separating multiple co-frequency beams of non-orthogonal code words based on DS-CDMA (Direct Sequence-Code Division Multiple Access) system

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