CN115792916A - Microwave photon wind measuring radar device - Google Patents
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Abstract
The invention discloses a microwave photon wind measuring radar device, which takes a photoelectric oscillator as a frequency source, generates a radio frequency signal with low phase noise, realizes the sharing of a receiving antenna and a transmitting antenna by means of a circulator and a four-beam antenna, reduces the size of the antenna and simultaneously realizes the accurate measurement of small-scale atmospheric turbulence; the high-isolation switch module is controlled through the comprehensive processing module, the conduction time sequence of the control switch is received, radial wind speed measurement in four directions is achieved by combining the four-beam antenna, and then wind direction information is calculated. The device has smaller antenna size, the radio frequency signal with low phase noise wave band has stronger penetrating power in severe weather, and the problem that the laser radar cannot work in severe weather can be effectively solved.
Description
Technical Field
The invention relates to the technical field of microwave signal detection and meteorological radar, in particular to a microwave photon radar wind measuring device for short-distance atmospheric turbulence electromagnetic wave scattering detection.
Background
As a non-spherical high altitude meteorological detection device, the wind profile radar is an important supplement of the current conventional sounding, and can continuously provide the height-dependent distribution of meteorological elements such as atmospheric speed, temperature, refractive index structural constants and the like. The detection data provided by the wind profile radar has high space-time resolution and good continuity and real-time performance. Wind profile radars generally emit electromagnetic beams vertically to the high altitude through phased array antennas, and detect changes of electromagnetic wave scattering signals caused by refractive index fluctuation due to atmospheric turbulence activity, so as to estimate information such as wind speed and wind direction of the position of an echo signal.
The wind profile radar has irreplaceable functions in the fields of atmospheric science research, meteorological service application, social meteorological service and the like. In particular, the wind profile radar can be used for researching the atmospheric turbulence and the atmospheric boundary layer, deducing the turbulence structure of atmospheric motion, detecting the change of the atmospheric boundary layer, and determining the wind shear position, height and the like.
In recent years, the requirements of wind field resource measurement and wind field measurement in the forward direction of a fan cabin are urgent. Compared with the traditional meteorological service, the wind field resource measurement and the wind field measurement in the forward direction of the fan cabin aim at the small-scale meteorological measurement within the range of hundreds of meters. At present, most of wind profile radars detect atmospheric scattering of a boundary layer and a stratosphere, detect meteorology with larger scale, detect meteorology with small scale, and have overlarge volume and overhigh manufacturing cost. The small-scale turbulence measurement usually uses a laser radar, but the laser radar is easily influenced by severe weather to cause incapability of working, and in recent years, a 24GHz microwave radar is also used for near-field turbulence measurement, but the traditional microwave oscillator frequency source hardly considers the characteristics of high oscillation frequency and high Q value of a resonant cavity at the same time, so that the directly generated high-frequency microwave signal noise performance is poor, and the measurement precision is easily influenced by the phase noise of the frequency source.
Disclosure of Invention
The invention mainly aims to provide a microwave photon wind measuring radar device which utilizes a photoelectric oscillator to generate a microwave signal to realize accurate measurement of all-weather near-field small-scale atmospheric turbulence.
The technical scheme adopted by the invention is as follows:
a microwave photon wind radar device is provided, which comprises
The photoelectric oscillator is used for generating a low-phase-noise continuous radio frequency signal and outputting the low-phase-noise continuous radio frequency signal to the three-terminal circulator;
the four-beam antenna is used for realizing radio frequency signal transmission and reflected signal reception in four directions of the south, the east, the west and the north under the control of the comprehensive processing module;
the three-terminal circulator comprises three ports, receives continuous radio frequency signals through a port a, sends the continuous radio frequency signals to the four-beam antenna through a port b, receives signals of the four-beam antenna from the port b, and outputs received signals through a port c;
the high-isolation switch module adopts two single-pole single-throw switches connected in series, synchronously acts under the control of the comprehensive processing module, and realizes the pulse of continuous signals with high isolation;
the receiving control switch adopts a single-pole single-throw switch and realizes the time-sharing controlled receiving of the four-beam antenna signals under the control of the comprehensive processing module;
and the comprehensive processing module is used for realizing controlled transmission of radio frequency signals, controlled reception of antenna signals and data processing.
According to the technical scheme, the photoelectric oscillator comprises a laser, a Mach-Zehnder modulator, a photoelectric detector, an amplifier, a band-pass filter and a microwave coupler which are connected in sequence; one output end of the microwave coupler is also connected with one input end of the Mach-Zehnder modulator;
continuous laser emitted by the laser enters the Mach-Zehnder modulator for modulation, then enters the photoelectric detector through the long optical fiber to convert optical signals into electric signals, the electric signals enter the microwave coupler through the amplifier and the band-pass filter to generate continuous radio-frequency signals with low phase noise, and meanwhile the microwave coupler generates feedback signals to the Mach-Zehnder modulator to modulate the continuous laser emitted by the laser.
The four-beam antenna comprises a single-pole four-throw switch, four sets of feed sources and a parabolic reflecting surface, wherein the four sets of feed sources are respectively connected with the output of the single-pole four-throw switch, and the centers of the four sets of feed sources generate beam deflection at the intersection points of the parabolic reflecting surface, so that the four beams are respectively deflected to four directions of south, east, west and north relative to the normal direction by theta, and theta is more than or equal to 10 degrees and less than or equal to 45 degrees.
According to the technical scheme, the isolation degree of the three-terminal circulator is more than or equal to 20dB, and the insertion loss is less than or equal to 1dB.
According to the technical scheme, the power divider is a power divider adopting a micro-strip current structure.
According to the technical scheme, the mixer single-end-to-differential amplifying circuit and the low-pass filter circuit are connected in series to form the mixer single-end-to-differential amplifying circuit, the single-end-to-differential amplifying circuit converts a single-end input signal into a differential signal and amplifies the differential signal, and the differential signal enters the low-pass filter circuit and is subjected to noise filtering.
In connection with the above technical scheme, the output of the photoelectric oscillator has the frequency of 77.000GHz +/-1 kHz, the phase noise is less than or equal to 144dBc/Hz @10kHz, and the frequency stability is less than or equal to 10 -10 @1 s.
According to the technical scheme, the gain of the four-beam antenna is more than or equal to 28dB, and the side lobe attenuation is less than or equal to-20 dB.
According to the technical scheme, the saturation power value of the power amplifier is not less than 40dBm, and the gain is not less than 25dB.
According to the technical scheme, the noise coefficient of the front low-noise amplifier is not more than 2.5, the gain of the rear low-noise amplifier is not less than 40dB, and the rear low-noise amplifier is composed of multiple stages of low-noise amplifiers.
The invention also provides a measuring method of the microwave photon wind measuring radar, which is based on the microwave photon wind measuring radar device of the technical scheme and comprises the following steps:
a continuous radio frequency signal generated by the photoelectric oscillator is divided into a measuring signal and a reference signal through a power divider, and the reference signal is input into a mixer;
the measurement signal enters a high-isolation switch module and forms a radio frequency pulse signal under the control of a comprehensive processing module;
a radio frequency pulse signal is input from a port a of the three-terminal circulator after passing through the power amplifier and then is output to the four-beam antenna through a port b, and a reflected signal received by the four-beam antenna is input from the port b and then is output from a port c to the receiving control switch to form a reflected receiving signal;
the reflected received signals respectively pass through a preposed low-noise amplifier, a radio frequency band-pass filter, a numerical control attenuator and a postposition low-noise amplifier and then enter a mixer to be mixed with a reference signal to form an intermediate frequency signal;
the intermediate frequency signals pass through an intermediate frequency processing circuit, then pass through an analog-to-digital converter, are digitized, then enter a comprehensive processing module for processing, and finally are resolved into wind speed and wind direction information.
The invention has the following beneficial effects: the invention provides a microwave photon wind measuring radar device, which combines a microwave photon technology and a wind measuring radar technology, utilizes an optoelectronic oscillator to generate a continuous radio frequency signal with low phase noise, and realizes the sharing of a receiving antenna and a transmitting antenna by means of a circulator and a four-beam antenna, thereby realizing the accurate measurement of all-weather near-field small-scale atmospheric turbulence.
Furthermore, the antenna of the device is smaller in size, the 77.000GHz band has stronger penetrating power in severe weather, and the problem that the laser radar cannot work in severe weather is effectively solved.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly introduced below, and it is obvious that the drawings in the following description are some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to these drawings without creative efforts.
FIG. 1 is a block diagram of a microwave photon wind radar apparatus according to an embodiment of the present invention;
FIG. 2 is a schematic timing control diagram of a high isolation switch module and a receive control switch according to an embodiment of the present invention;
FIG. 3 is a block diagram of an optoelectronic oscillator of an embodiment of the present invention;
FIG. 4 is a schematic diagram of a four-beam antenna according to an embodiment of the present invention;
fig. 5 is a four-beam antenna directional diagram of an embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
The invention utilizes the photoelectric oscillator to generate a radio frequency signal with the frequency of 77.000GHz, realizes the sharing of the receiving and transmitting antenna by means of the circulator and the four-beam antenna, realizes the accurate measurement of all-weather near-field small-scale atmospheric turbulence, and greatly reduces the volume of the whole device.
The invention provides a microwave photon wind measuring radar device, which comprises
The photoelectric oscillator 1 generates a continuous radio frequency signal with low phase noise, the frequency of the output radio frequency signal is 77.000GHz, the wavelength is shorter compared with that of a traditional microwave wind radar, the size of an antenna is smaller, the penetrating power of the wave band in severe weather is stronger, and the problem that a laser radar cannot work in severe weather is effectively solved; meanwhile, the radio frequency output signal of the photoelectric oscillator 1 has low phase noise and small time jitter, and is higher in measurement accuracy compared with the traditional microwave wind-measuring radar.
The four-beam antenna 6 realizes the radio frequency signal transmission and the reflected signal reception in four directions of the south, the east, the west and the north under the control of the comprehensive processing module, and realizes the measurement of the radial wind speed in the four directions.
And the three-terminal circulator 5 sends the radio-frequency signal at the terminal a to the four-beam antenna through the port b, receives the signal of the four-beam antenna from the port b, and outputs the received signal through the port c. In the embodiment of the invention, the receiving and transmitting link common antenna is realized through the circulator 5, the circulator 5 is provided with three ports, the signal flow direction is that the port a enters the port b and exits, and the signal entering the port b exits from the port c. The circulator isolation is not less than 20dB, and the insertion loss is not more than 1dB.
The high-isolation switch module 3 adopts two single-pole single-throw switches which are conducted at high level and are connected in series, and synchronously acts under the control of the comprehensive processing module, thereby realizing the pulse of continuous signals at high isolation.
And the receiving control switch 7 adopts a single-pole single-throw switch switched off at a high level, and realizes time-sharing controlled receiving of four-beam antenna signals under the control of the comprehensive processing module.
The comprehensive processing module 15 is used for realizing controlled transmission of radio frequency signals, controlled receiving of antenna signals and data processing, the comprehensive processing module 15 strictly controls and controls the conduction time sequences of the high-isolation switch module 3 and the receiving control switch 7, and receiving and transmitting of signals in four directions of the four-beam antenna 6 are realized, and the transmitting antenna is shared.
As shown in fig. 1, the microwave photon wind radar device works as follows:
a continuous radio frequency signal generated by the photoelectric oscillator 1 is divided into a measuring signal and a reference signal through the power divider 2, and the reference signal is input into the mixer 12; the measuring signal enters the high-isolation switch module 3, a radio-frequency pulse signal is formed under the control of the comprehensive processing module 15, the radio-frequency pulse signal is input from a port a of the three-terminal circulator 5 after passing through the power amplifier 4 and then is output to the four-beam antenna 6 through a port b, a reflection signal received by the four-beam antenna 6 is input from the port b and then is output to the receiving control switch 7 through a port c to form a reflection receiving signal; the comprehensive processing module 15 controls the four-beam antenna 6 to perform sequential beam switching every 0.25s, so that radio frequency pulses are sequentially transmitted to 4 orthogonal directions, the transmitted radio frequency pulses are scattered with atmospheric turbulence, scattered signals are received by the four-beam antenna 6, and turbulent scattered radio frequency pulses, namely reflected received signals, are formed.
The reflected received signals respectively pass through a preposed low noise amplifier 8, a radio frequency band-pass filter 9 and a numerical control attenuator 10, and under the control of a comprehensive processing module 15, turbulent scattering echoes at different distances after stray filtering are subjected to program control attenuation, so that the dynamic range of turbulent scattering echo signals is reduced. The signals subjected to program control attenuation enter a post-positioned low-noise amplifier 11 for amplification, then enter a mixer 12 and a reference signal for mixing to form intermediate-frequency signals (two paths of orthogonal IQ signals), the intermediate-frequency signals are subjected to low-frequency filtering and amplification through an intermediate-frequency processing circuit 13 to match the input range of an analog-to-digital converter 14, then are digitized through the analog-to-digital converter 14 and enter a comprehensive processing module 15 for processing and storage, the radial wind speed of the current beam pointing direction is respectively solved, and then wind speed and wind direction information are calculated according to the radial wind speed of four directions.
In the embodiment of the present invention, the intermediate frequency processing circuit 13 is composed of two stages, the first stage is a single-end to differential amplifying circuit, that is, a signal input by the mixer 12 is converted into a differential signal and amplified, and the second stage is a low-pass filtering circuit for performing noise filtering on the differential signal.
The invention strictly controls and controls the conduction time sequence of the high-isolation switch module 3 and the receiving control switch 7 through the comprehensive processing module 15, realizes the receiving and sending of signals in four directions of the four-beam antenna 6 and the sharing of transmitting and receiving antennas. The receiving control switch 7 is turned off when the high-isolation switch module 3 is turned on, so as to avoid saturation or damage of a receiving link device caused by coupling of a radio frequency signal in a transmitting link into a receiving link by a circulator.
The control timing sequences of the high-isolation switch module 3 and the receiving control switch 7 are shown in fig. 2, two single-pole single-throw switches switched on by high level in the high-isolation switch module 3 act synchronously, the switching-on period is 250kHz, and the switching-on duration is 200ns. The turn-off period of the receiving control switch 7 is 250kHz, the turn-off duration is 250ns, and the turn-off duration is 50ns longer than the turn-on duration of the high-isolation switch module 3, so that power coupling caused by switching delay of the switch is avoided.
As a preferred embodiment, as shown in fig. 3, the internal structure and principle of the optoelectronic oscillator 1 are as follows:
continuous laser light emitted by the laser 101 enters the Mach-Zehnder modulator 102 for modulation, then enters the photoelectric detector 104 through the long optical fiber 103 to convert an optical signal into an electric signal, the electric signal enters the microwave coupler 107 after passing through the amplifier 105 and the band-pass filter 106 to generate a low-phase-noise 77GHz continuous radio-frequency signal, and meanwhile the microwave coupler 107 generates a feedback signal to the Mach-Zehnder modulator 102 to modulate the continuous laser light emitted by the laser. The signal is continuously photoelectrically converted, amplified and fed back in the loop, and finally stable self-oscillation is realized and then output by the microwave coupler 107.
Through electro-optic-photoelectric conversion, a kilometer long optical fiber 103 is used as a part of a resonant cavity, and the constructed photoelectric resonant cavity has an ultra-high Q value and can generate a high-frequency microwave signal with ultra-low phase noise by relying on the advantages of low loss and large bandwidth of the optical fiber.
As a preferred embodiment, as shown in fig. 4, the four-beam antenna 6 includes a single-pole four-throw switch 601, four sets of feeds 602, and a parabolic reflecting surface 603, the four sets of feeds 602 are connected to outputs of the single-pole four-throw switch 601, respectively, and centers of the four sets of feeds 602 generate beam deflection at intersections of the parabolic reflecting surface 603, so that four beams are respectively deflected by θ in four directions of south, east, west, and north relative to a normal direction, and θ is greater than or equal to 10 ° and less than or equal to 45 °. As a preferred embodiment, the four beams are offset by 15 ° in four directions, south-east-west-north, respectively, with respect to the normal direction, as shown in fig. 5.
As a preferred embodiment, the isolation of the three-terminal circulator 5 is more than or equal to 20dB, and the insertion loss is less than or equal to 1dB.
As a preferred embodiment, the power divider 2 is a power divider adopting a microstrip current structure, and has the characteristics of simple and compact structure, low cost, stable performance and wide frequency band.
As a preferred embodiment, the mixer 12 is formed by connecting a single-ended to differential amplifier circuit and a low-pass filter circuit in series, the single-ended to differential amplifier circuit converts a single-ended input signal into a differential signal and amplifies the differential signal, and the differential signal enters the low-pass filter circuit to filter noise of the differential signal.
As a preferred embodiment, the output of the optoelectronic oscillator 1 is frequency 77.000GHz + -1 kHz, phase noise ≦ 144dBc/Hz @10kHz, frequency stability ≦ 10 -10 @1 s. The size of the antenna is smaller than that of VHF (very high frequency) radars, UHF (ultra high frequency) radars, L-band radars and 24GHz radars under the condition of generating the same antenna gain by using 77GHz radio frequency, so that the antenna is beneficial to miniaturization design.
As a preferred embodiment, the gain of the four-beam antenna 6 is more than or equal to 28dB, and the side lobe attenuation is less than or equal to-20 dB.
As a preferred embodiment, the power amplifier 4 has a saturation power value of not less than 40dBm and a gain of not less than 25dB.
As a preferred embodiment, the noise coefficient of the front low noise amplifier 8 is not more than 2.5, and the gain of the rear low noise amplifier 11 is not less than 40dB, and the front low noise amplifier is composed of a plurality of stages of low noise amplifiers.
The device of the embodiment of the invention adopts a transmitting-receiving common antenna design, thereby greatly reducing the volume of the whole system, but in order to ensure the transmitting-receiving isolation degree, a switching device is required to be added, and the insertion loss of a link is increased by introducing the switching device, so that the receiving sensitivity of the system is reduced. In order to compensate for the problem of reduced receiving sensitivity, the transmitting power needs to be increased, and the increase of the transmitting power puts higher requirements on the transmitting-receiving isolation, so that the increase range of the transmitting power and the transmitting-receiving isolation need to be comprehensively considered.
As a preferred embodiment, the transmission power is 38dBm, the three-terminal circulator 5 and the high isolation switch module 3 at the rear end of the power amplifier 4 need to work normally when the transmission power is boosted, the maximum input power of the three-terminal circulator 5 is designed to be 40dBm, and the maximum input power of the single-pole four-throw switch 601 in the four-beam antenna 6 is 39dBm, which can bear the boost of the transmission power.
When transmitting, the power amplifier 4 outputs 38dBm, the isolation of the three-terminal circulator 5 is about 20dB, and the isolation output of the three-terminal circulator 5 is about 18dBm. The receiving control switch 7 uses a single-pole single-throw switch with the isolation degree of 40dB, the power is about-22 dBm after passing through the receiving control switch 7 and is completely lower than the input saturation power of the preposed low-noise amplifier 8, and the isolation degree requirement during transmitting is ensured.
When the signal is not transmitted, the condition that the signal of the receiver is overlarge due to power leakage and the extraction of a turbulent echo weak signal is influenced needs to be prevented. When the power divider is not used for transmitting, the power output by the power divider 2 to a front-stage single-pole single-throw switch of the high-isolation switch module 3 is +15dBm, the power of a signal is attenuated to-65 dBm after passing through the two-stage single-pole single-throw switch, and the power is amplified by the power amplifier 4 by 25dB and is about-40 dBm. And the signal power is attenuated by 20dB through the three-terminal circulator 5, and the signal power after the 40dB attenuation of the receiving control switch 7 is about-100 dBm and is close to the lowest receiving power value of a receiving channel, so that the influence on the actual echo signal can be ignored.
The preferred embodiment of the present invention uses a 77GHz RF frequency, which is smaller than VHF (very high frequency) radar, UHF (ultra high frequency) radar, L-band radar and 24GHz radar under the condition of generating the same antenna gain, thereby facilitating the miniaturization design.
It should be noted that, according to the implementation requirement, each step/component described in the present application can be divided into more steps/components, and two or more steps/components or partial operations of the steps/components can be combined into new steps/components to achieve the purpose of the present invention.
It will be understood that modifications and variations can be made by persons skilled in the art in light of the above teachings and all such modifications and variations are intended to be included within the scope of the invention as defined in the appended claims.
Claims (10)
1. A microwave photonic wind radar apparatus, comprising:
the photoelectric oscillator is used for generating a low-phase-noise continuous radio frequency signal and outputting the low-phase-noise continuous radio frequency signal to the three-terminal circulator;
the four-beam antenna is used for realizing radio frequency signal transmission and reflected signal reception in four directions of the south, the east, the west and the north under the control of the comprehensive processing module;
the three-terminal circulator comprises three ports, wherein a continuous radio frequency signal is received through a port a, then is sent to the four-beam antenna through a port b, receives a signal of the four-beam antenna from the port b, and then outputs a received signal through a port c;
the high-isolation switch module adopts two single-pole single-throw switches connected in series, synchronously acts under the control of the comprehensive processing module, and realizes the pulse of continuous signals with high isolation;
the receiving control switch adopts a single-pole single-throw switch and realizes the time-sharing controlled receiving of the four-beam antenna signals under the control of the comprehensive processing module;
and the comprehensive processing module is used for realizing controlled transmission of radio frequency signals, controlled reception of antenna signals and data processing, and calculating wind speed and wind direction information.
2. The microwave photonic wind radar apparatus according to claim 1, wherein the optoelectronic oscillator comprises a laser, a mach-zehnder modulator, a photodetector, an amplifier, a band-pass filter, and a microwave coupler, which are connected in sequence; one output end of the microwave coupler is also connected with one input end of the Mach-Zehnder modulator;
continuous laser emitted by the laser enters the Mach-Zehnder modulator for modulation, then enters the photoelectric detector through the long optical fiber to convert optical signals into electric signals, the electric signals enter the microwave coupler through the amplifier and the band-pass filter to generate continuous radio-frequency signals with low phase noise, and meanwhile the microwave coupler generates feedback signals to the Mach-Zehnder modulator to modulate the continuous laser emitted by the laser.
3. The microwave photon wind radar apparatus according to claim 1, wherein the four-beam antenna comprises a single-pole four-throw switch, four sets of feed sources and a parabolic reflecting surface, the four sets of feed sources are connected with the outputs of the single-pole four-throw switch respectively, and the centers of the four sets of feed sources generate beam deflection at the intersection points of the parabolic reflecting surface, so that the four beams are respectively deflected to four directions of south, east, west and north relative to the normal direction by theta, and theta is not less than 10 degrees and not more than 45 degrees.
4. The microwave photon wind radar apparatus according to claim 1, wherein the isolation of the three-terminal circulator is not less than 20dB and the insertion loss is not more than 1dB.
5. The microwave photonic wind radar apparatus according to claim 1, wherein the power divider is a power divider using a microstrip current structure.
6. The microwave photon wind radar apparatus according to claim 1, wherein the mixer single-ended to differential amplifier circuit and the low-pass filter circuit are connected in series, the single-ended to differential amplifier circuit converts a single-ended input signal into a differential signal and amplifies the differential signal, and the differential signal enters the low-pass filter circuit to filter noise of the differential signal.
7. The microwave photonic wind radar apparatus according to claim 2, wherein the output of the optoelectronic oscillator has a frequency of 77.000GHz ± 1kHz, a phase noise of ≤ 144dBc/Hz of @10kHz, and a frequency stability of ≤ 10 -10 @1 s.
8. The microwave photon wind radar apparatus according to claim 3, wherein the gain of the four-beam antenna is not less than 28dB, and the side lobe attenuation is not more than-20 dB; the saturation power value of the power amplifier is not less than 40dBm, and the gain is not less than 25dB.
9. The microwave photonic wind radar apparatus according to claim 3, wherein the front low noise amplifier has a noise figure of not more than 2.5, and the rear low noise amplifier has a gain of not less than 40dB and is composed of a plurality of stages of low noise amplifiers.
10. A method for measuring a microwave photonic wind radar, the method being based on the microwave photonic wind radar apparatus of any one of claims 1 to 9, comprising the steps of:
a continuous radio frequency signal generated by the photoelectric oscillator is divided into a measuring signal and a reference signal through a power divider, and the reference signal is input into a mixer;
the measurement signal enters a high-isolation switch module and forms a radio frequency pulse signal under the control of a comprehensive processing module;
a radio frequency pulse signal is input from a port a of the three-terminal circulator after passing through the power amplifier and then is output to the four-beam antenna through a port b, and a reflected signal received by the four-beam antenna is input from the port b and then is output from a port c to the receiving control switch to form a reflected receiving signal;
the reflected and received signals respectively pass through a preposed low-noise amplifier, a radio frequency band-pass filter, a numerical control attenuator and a postpositional low-noise amplifier and then enter a mixer to be mixed with a reference signal to form an intermediate frequency signal;
the intermediate frequency signals pass through an intermediate frequency processing circuit, then pass through an analog-to-digital converter, are digitized, then enter a comprehensive processing module for processing, and finally are resolved into wind speed and wind direction information.
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| CN202211539743.7A CN115792916A (en) | 2022-12-02 | 2022-12-02 | Microwave photon wind measuring radar device |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN117578067A (en) * | 2024-01-12 | 2024-02-20 | 南京信息工程大学 | Multifunctional multiplexing antenna system based on near space sonde |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN117578067A (en) * | 2024-01-12 | 2024-02-20 | 南京信息工程大学 | Multifunctional multiplexing antenna system based on near space sonde |
| CN117578067B (en) * | 2024-01-12 | 2024-03-29 | 南京信息工程大学 | Multifunctional multiplexing antenna system based on near space sonde |
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