CN114614681A - Improved prediction control method for three-phase alternating current electronic load - Google Patents

Improved prediction control method for three-phase alternating current electronic load Download PDF

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CN114614681A
CN114614681A CN202210286534.XA CN202210286534A CN114614681A CN 114614681 A CN114614681 A CN 114614681A CN 202210286534 A CN202210286534 A CN 202210286534A CN 114614681 A CN114614681 A CN 114614681A
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pwm rectifier
voltage
load
power
grid
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王健
董学育
朱建忠
郭前程
刘晨曦
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Nanjing Institute of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • H02J3/381—Dispersed generators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices

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  • Power Engineering (AREA)
  • Rectifiers (AREA)

Abstract

The invention discloses an improved predictive control method of three-phase alternating current electronic load, which comprises a first PWM control method and a second PWM control method, wherein the first PWM control method comprises sampling voltage and current of power supply at load analog side, obtaining input current reference value, calculating conversion prediction variable by formula, obtaining reference value of input voltage, all possible voltage vectors in the model are divided into sectors, the most possible voltage vectors of the next stage are obtained by judging the sector where the reference input voltage is positioned and the position in the sector, further obtaining the on-off state of the next sampling interval, the control method of the invention realizes further optimization to the prior predictive control algorithm, greatly reduces the calculated amount of the predictive control algorithm, and the control effect of the predictive control algorithm is not influenced, so that the application of the predictive control algorithm is more universal.

Description

Improved prediction control method for three-phase alternating current electronic load
Technical Field
The invention relates to the technical field of electronics, in particular to an improved predictive control method for a three-phase alternating current electronic load.
Background
Because of various AC power supply devices, such as an Uninterruptible Power Supply (UPS), a battery, an AC/DC power supply, a vehicle-mounted power supply, a communication power supply, a variable frequency power supply and the like, before the test is put into practical application, very strict detection experiments including an aging experiment, a dynamic and static test, a test of the output characteristics of the product and the like are carried out, however, the traditional load is used for testing, which causes the problems of inconvenient adjustment, poor precision, poor stability, great energy waste and the like, in order to solve the above problems, energy-fed electronic loads are generally adopted, as shown in fig. 1, the topology of the three-phase half-bridge three-phase ac electronic load is two back-to-back PWM rectifiers, the preceding-stage PWM rectifier is the load simulation side, the three-phase IGBT bridge comprises a three-phase IGBT bridge consisting of VT1-VT6, a filter inductor L1 and an equivalent resistor R1, according to the four-quadrant working characteristics of the PWM rectifier, the simulation of loads with different properties is realized; the rear-stage PWM rectifier is an energy feedback side and comprises a three-phase IGBT bridge consisting of VT7-VT12, a filter inductor L2 and an equivalent resistor R2, and the energy generated in the test process is fed back to the power grid according to the unit power factor grid-connected characteristic of the PWM rectifier; the middle of the direct current bus is connected by a direct current bus capacitor and used for decoupling of a controller and restraining voltage harmonics of a direct current side, and energy transmission between two stages is achieved.
For the traditional model prediction control, the calculation amount is large, so that the performance of the processor is high; the prior art, application number is 202110820720.2, and the name of the invention is: a predictive control method for three-phase alternating current electronic load adopts finite set model predictive control, a load simulation side adopts direct current predictive control, an energy feedback side adopts predictive power control, but the method has the following problems: the calculation amount of the algorithm is large, and the calculation load of the processor is increased.
Disclosure of Invention
Aiming at the technical problems, the invention provides an improved three-phase alternating current electronic load predictive control method capable of greatly reducing the calculated amount, the original predictive control method has overlarge calculated amount and higher performance requirement on a processor, the improved predictive control calculated amount is greatly reduced, the control performance of a predictive control algorithm is not changed, and the application of the predictive control algorithm can be realized on the processor with lower cost.
The purpose of the invention can be realized by the following technical scheme:
a three-phase alternating current electronic load prediction control method comprises a load simulator with a first PWM rectifier at the front stage and an energy feedback device with a second PWM rectifier at the rear stage; the first PWM rectifier of the load simulator is connected with the second PWM rectifier of the energy feedback device back to back through a direct current bus capacitor; the method is characterized in that: the first PWM rectifier and the second PWM rectifier adopt respective independent control methods; the first PWM rectifier control method comprises the following steps:
step 1: the three-phase alternating current electronic load is connected with a power supply to be tested, and the power supply voltage U to be tested and the input current i are sampled;
step 2: the tested power supply voltage U and the input current i are converted by an abc/alpha beta conversion module to obtain the actual power supply voltage U of the load simulation side under an alpha-beta coordinate systemα、UβAnd the actual input current i of the load simulation sideα、iβ(ii) a According to the load characteristics preset by a user, calculating the expected input current of the load simulation side under the alpha-beta coordinate system by utilizing the complex form of ohm's law
Figure BDA0003558473090000031
And
Figure BDA0003558473090000032
the negativeThe load characteristics comprise resistive load, resistance-inductance load and resistance-capacitance load;
and step 3: calculating an expected input voltage corresponding to the expected input current in the first PWM rectifier based on a mathematical model of the PWM rectifier;
and 4, step 4: carrying out sector distribution on all possible eight voltage vectors of the next sampling interval in the first PWM rectifier, and judging the sector where the expected input voltage is located; the sampling interval is a preset sampling interval;
and 5: judging the position of a sector where an expected input voltage vector is located through vector calculation, and if the expected input voltage vector is in a shadow area, selecting a switching state corresponding to a zero vector as a switching state of a first PWM rectifier at a next sampling interval; if the voltage vector is not in the shadow area, selecting the switching state corresponding to the voltage vector in the sector as the switching state of the first PWM rectifier at the next sampling interval;
the second PWM rectifier control method includes the steps of:
step 6: three-phase alternating current electronic load is merged into a power grid, and the voltage U of the power grid is sampledsAnd a grid-connected current is；
And 7: to-be-sampled grid voltage UsAnd a grid-connected current isThe power grid side actual power supply voltage U is converted into an alpha-beta coordinate system through an abc/alpha-beta conversion modulesα、UsβAnd the actual input current i on the network sidesα、isβ；
And 8: collecting the voltage of the DC bus and sampling the actual value U of the DC bus voltagedcAnd the preset direct current bus voltage expected value
Figure BDA0003558473090000041
Inputting the error signal between the two into a PI controller; the signal output by the PI controller and the actual value U of the DC bus voltagedcMultiplying to obtain the expected value p of the active powerref(ii) a The desired value q of the reactive power is calculatedrefSet to 0;
and step 9: predicting the grid-connected current value of each different voltage vector in the eight voltage vectors in the second PWM rectifier in the next sampling interval based on the mathematical model of the PWM rectifier;
step 10: the actual power supply voltage U of the power grid side in the step 7 is comparedsα、UsβSequentially substituting the grid-connected current value predicted in the step 9 into a power formula to calculate predicted active power and reactive power; and predicting the active power, the reactive power and the expected value p of the active powerrefAnd desired value q of reactive powerrefSubstituting the cost function to calculate the difference value between the predicted power and the expected power corresponding to the predicted power; and taking the switching state corresponding to the voltage vector which minimizes the cost function as the switching state of the second PWM rectifier at the next sampling interval.
Further, the cost function in step 10 is specifically:
g＝|pref-pk+1|+|qref-qk+1|；(1)
(1) in the formula, pk+1、qk+1Is the predicted active power and reactive power magnitude of the next sampling interval.
Further, the switching states of the first PWM rectifier and the second PWM rectifier are both: s ═ 000100010110001101011111.
Has the advantages that:
the control algorithm realizes further optimization of the existing predictive control algorithm, greatly reduces the calculated amount of the predictive control algorithm, does not influence the control effect of the predictive control algorithm, and ensures that the application of the predictive control algorithm has universality.
Drawings
FIG. 1 is a main circuit topology diagram of a three-phase AC electronic load in the present invention;
FIG. 2 is a block diagram of an improved predictive control algorithm employed in the present invention;
FIG. 3 is a voltage vector sector allocation diagram according to the present invention;
FIG. 4 is a predictive control block diagram of the present invention.
Detailed Description
The present invention will be described in detail with reference to the accompanying drawings.
As shown in fig. 2 to 4, a method for predictive control of a three-phase ac electronic load includes a load simulator having a front stage with a first PWM rectifier and an energy feedback device having a rear stage with a second PWM rectifier; the first PWM rectifier of the load simulator is connected with the second PWM rectifier of the energy feedback device back to back through a direct current bus capacitor; the method is characterized in that: the first PWM rectifier and the second PWM rectifier adopt respective independent control methods; the first PWM rectifier control method comprises the following steps:
step 1: the three-phase alternating current electronic load is connected with a power supply to be tested, and the power supply voltage U to be tested and the input current i are sampled;
step 2: the tested power supply voltage U and the input current i are converted by an abc/alpha beta conversion module to obtain the actual power supply voltage U of the load simulation side under an alpha-beta coordinate systemα、UβAnd the actual input current i of the load simulation sideα、iβ(ii) a According to the load characteristics preset by a user, calculating the expected input current of the load simulation side under the alpha-beta coordinate system by utilizing the complex form of ohm's law
Figure BDA0003558473090000061
And
Figure BDA0003558473090000062
the load characteristics comprise resistive load, resistance-inductance load and resistance-capacitance load;
and step 3: calculating an expected input voltage corresponding to the expected input current in the first PWM rectifier based on a mathematical model of the PWM rectifier;
and 4, step 4: carrying out sector distribution on all possible eight voltage vectors of the next sampling interval in the first PWM rectifier, and judging the sector where the expected input voltage is located; the sampling interval is a preset sampling interval;
and 5: judging the position of a sector where an expected input voltage vector is located through vector calculation, and if the expected input voltage vector is in a shadow area, selecting a switching state corresponding to a zero vector as a switching state of a first PWM rectifier at a next sampling interval; if the voltage vector is not in the shadow area, selecting the switching state corresponding to the voltage vector in the sector as the switching state of the first PWM rectifier at the next sampling interval;
the second PWM rectifier control method includes the steps of:
step 6: three-phase alternating current electronic load is merged into a power grid, and the voltage U of the power grid is sampledsAnd a grid-connected current is；
And 7: to-be-sampled grid voltage UsAnd a grid-connected current isThe power grid side actual power supply voltage U is converted into an alpha-beta coordinate system through an abc/alpha-beta conversion modulesα、UsβAnd the actual input current i on the network sidesα、isβ；
And 8: collecting the voltage of the DC bus and sampling the actual value U of the DC bus voltagedcAnd the preset direct current bus voltage expected value
Figure BDA0003558473090000071
Inputting the error signal between the two into a PI controller; actual value U of signal and direct current bus voltage that PI controller outputdcMultiplying to obtain the expected value p of the active powerref(ii) a The reactive power expected value q is calculatedrefSet to 0;
and step 9: predicting the grid-connected current value of each different voltage vector in the eight voltage vectors in the second PWM rectifier in the next sampling interval based on the mathematical model of the PWM rectifier;
step 10: the actual power supply voltage U of the power grid side in the step 7 is comparedsα、UsβSequentially substituting the grid-connected current value predicted in the step 9 into a power formula to calculate predicted active power and reactive power; and predicting the active power, the reactive power and the expected value p of the active powerrefWith desired value q of reactive powerrefSubstituting the cost function to calculate the difference value between the predicted power and the expected power corresponding to the predicted power; and taking the switching state corresponding to the voltage vector which minimizes the cost function as the switching state of the second PWM rectifier at the next sampling interval.
The cost function in step 10 is specifically: g ═ pref-pk+1|+|qref-qk+1|；(1)
(1) In the formula, pk+1、qk+1Is the predicted active power and reactive power of the next sampling interval.
The switching states of the first PWM rectifier and the second PWM rectifier are as follows: s ═ 000100010110001101011111.
As shown in fig. 1, the topology structure of the three-phase half-bridge three-phase ac electronic load is two back-to-back PWM rectifiers, the front-stage PWM rectifier is a load simulation side, and includes a three-phase IGBT bridge composed of VT1-VT6, a filter inductor L1, and an equivalent resistor R1, and the simulation of loads with different properties is realized according to the four-quadrant operating characteristics of the PWM rectifier; the rear-stage PWM rectifier is an energy feedback side and comprises a three-phase IGBT bridge consisting of VT7-VT12, a filter inductor L2 and an equivalent resistor R2, and the energy generated in the test process is fed back to the power grid according to the unit power factor grid-connected characteristic of the PWM rectifier; the middle is connected by a direct current bus capacitor and used for decoupling of a controller and restraining voltage harmonic waves at a direct current side, a control target at a load simulation side is to control input current to track a set value so as to realize simulation of loads with various characteristics, so that the load simulation side adopts direct current control, a control target at an energy feedback side comprises constant control of direct current bus voltage and subsequent unit power factor grid connection, so that the control target is to adopt power control and control input reactive power to realize the control purpose while stabilizing the direct current bus voltage, a controller at the load simulation side obtains voltage signals and phase information of a test power supply through a voltage sampling circuit and inputs the voltage signals and the phase information into an instruction signal generating unit, the instruction signal generating unit generates instruction current signals through calculation of a corresponding instruction signal generating algorithm according to a set load form, and the load simulator tracks the change of the instruction current through a current control strategy, therefore, load functions with various characteristics are simulated, the energy feedback side controller respectively controls direct current bus voltage and grid-connected current through a control strategy combining predictive control and direct power control, energy feedback with power factors close to-1 is achieved, and finally energy is fed back to a power grid.
FIG. 2 is a block diagram of an improved predictive control algorithm provided by the present invention; on the load simulation side, a voltage expected value at the next moment is calculated through a voltage value u (k), a current value i (k) and a preset current expected value input calculation module at the current moment, divided sectors are divided into a shadow area and a non-shadow area according to a vector relation, sector judgment is carried out on the voltage expected value vector to obtain the position of the voltage expected value vector, if the voltage expected value vector is in the shadow area, a switching state corresponding to a zero vector is selected as a switching state at the next moment, if the voltage expected value vector is not in the shadow area, the switching state corresponding to the voltage vector in the corresponding sector is selected as the switching state at the next moment, then switching values (S1, S2 and S3) are input to control a first PWM rectifier, on the energy feedback side, the predicted power and the expected power are substituted into a cost function to calculate the difference value between the predicted power and the expected power, and the switching state corresponding to the voltage vector with the minimum cost function (S1, A, B and B) are taken, S2, S3) as the switching state of the second PWM rectifier for the next phase.
As shown in fig. 3, the load simulation side collects actual input current, predicts and obtains expected input voltage of the next sampling interval based on a mathematical model of the PWM rectifier and a current expected value obtained by setting, and selects a switching state corresponding to an optimal solution as a control signal of the first three-phase PWM rectifier by sector judgment; and performing PI integration on the deviation value of the actual direct current bus voltage at the energy feedback side and the expected direct current bus voltage at the energy feedback side to obtain an expected grid-connected current value, designing expected active power and reactive power, comparing the expected active power and reactive power with the predicted active power and reactive power at the next sampling interval in a cost function, and selecting a switching state corresponding to the optimal solution as a control signal of a second three-phase PWM rectifier.
In the design provided by the present invention, the system parameters may be set as: the filter inductance of the load simulation side and the filter inductance of the energy feedback side are 10mH, the equivalent resistance of a line is 0.3 omega, the capacitance of a direct current bus is 3000uF, the expected value of the voltage of the direct current bus is 600V, and the sampling frequency is 20 KHZ.
Although the present invention has been described with reference to the preferred embodiments, it should be understood that various changes and modifications can be made therein by those skilled in the art without departing from the spirit and scope of the invention as defined in the appended claims.

Claims (3)

1. A three-phase AC electronic load prediction control method is applied to a three-phase AC electronic load, the three-phase AC electronic load comprises a load simulator with a front stage of a first PWM rectifier and an energy feedback device with a rear stage of a second PWM rectifier, the first PWM rectifier of the load simulator and the second PWM rectifier of the energy feedback device are connected back to back through a DC bus capacitor, and the three-phase AC electronic load prediction control method is characterized in that: the first PWM rectifier and the second PWM rectifier adopt independent control methods, wherein the control method of the first PWM rectifier comprises the following steps:
step 1: the three-phase alternating current electronic load is connected with a power supply to be tested, and the power supply voltage U to be tested and the input current i are sampled;
step 2: the tested power supply voltage U and the input current i are converted by an abc/alpha beta conversion module to obtain the actual power supply voltage U of the load simulation side under an alpha-beta coordinate systemα、UβAnd the actual input current i of the load simulation sideα、iβ(ii) a According to the load characteristics preset by a user, calculating the expected input current of the load simulation side under the alpha-beta coordinate system by utilizing the complex form of ohm's law
Figure FDA0003558473080000011
And
Figure FDA0003558473080000012
the load characteristics comprise resistive load, resistive-inductive load and resistive-capacitive load;
and step 3: calculating an expected input voltage corresponding to the expected input current in the first PWM rectifier based on a mathematical model of the PWM rectifier;
and 4, step 4: carrying out sector distribution on all possible eight voltage vectors in the next sampling interval in the first PWM rectifier, and judging the sector where the expected input voltage is located, wherein the sampling interval is a preset sampling interval;
and 5: judging the position of a sector where an expected input voltage vector is located through vector calculation, if the expected input voltage vector is in a shadow area, selecting a switching state corresponding to a zero vector as a switching state of a first PWM rectifier at a next sampling interval, and if the expected input voltage vector is not in the shadow area, selecting the switching state corresponding to the voltage vector in the sector as the switching state of the first PWM rectifier at the next sampling interval; the control method of the second PWM rectifier comprises the following steps:
step 6: three-phase alternating current electronic load is merged into a power grid, and the voltage U of the power grid is sampledsAnd a grid-connected current is；
And 7: to-be-sampled grid voltage UsAnd a grid-connected current isThe actual power supply voltage U at the side of the power grid under an alpha-beta coordinate system is converted by an abc/alpha-beta conversion modulesα、UsβAnd the actual input current i on the network sidesα、isβ；
And 8: collecting the voltage of the DC bus and sampling the actual value U of the DC bus voltagedcAnd the preset direct current bus voltage expected value
Figure FDA0003558473080000021
Inputting the error signal between the two into a PI controller; the signal output by the PI controller and the actual value U of the DC bus voltagedcMultiplying to obtain the expected value p of the active powerref(ii) a The reactive power expected value q is calculatedrefSet to 0;
and step 9: predicting the grid-connected current value of each different voltage vector in the eight voltage vectors in the second PWM rectifier in the next sampling interval based on the mathematical model of the PWM rectifier;
step 10: the actual power supply voltage U of the power grid side in the step 7sα、UsβSequentially substituting the grid-connected current value predicted in the step 9 into a power formula to calculate predicted active power and reactive power; and predicting the active power, the reactive power and the expected value p of the active powerrefWith desired value q of reactive powerrefCalculating predicted power by substituting cost functionThe difference from its corresponding desired power; and taking the switching state corresponding to the voltage vector which minimizes the cost function as the switching state of the second PWM rectifier at the next sampling interval.
2. The method of claim 1, wherein the predictive control of the three-phase ac electronic load comprises: the cost function in step 10 is specifically: g ═ pref-pk+1|+|qref-qk+1|；(1)
(1) In the formula, pk+1、qk+1Is the predicted active power and reactive power magnitude of the next sampling interval.
3. The method of claim 1, wherein the method comprises: the switching states of the first PWM rectifier and the second PWM rectifier are both as follows: s ═ 000100010110001101011111.
CN202210286534.XA 2022-03-22 2022-03-22 Improved prediction control method for three-phase alternating current electronic load Withdrawn CN114614681A (en)

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