CN114142737A - Control method of full-bridge CLLC resonant converter - Google Patents
Control method of full-bridge CLLC resonant converter Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33584—Bidirectional converters
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- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention discloses a sectional control method of a full-bridge CLLC resonant converter, which combines the traditional control method and divides the control into two sections: PFM control is adopted in a higher voltage gain section; the lower voltage gain section is controlled using EPS. The segmented control can realize the soft switching-on of the primary side switch in a larger PFM control range and a full EPS control range, and has smaller reflux power compared with the traditional phase-shift control and narrower switching frequency change range compared with the traditional frequency modulation control.
Description
Technical Field
The invention relates to the technical field of power electronic converters, in particular to a sectional control method of a bidirectional full-bridge CLLC resonant converter.
Background
With the establishment and the implementation of the national 'double-carbon' target, the distributed renewable energy becomes the propulsion energy transformation, and an important way for assisting in constructing a novel power system taking new energy as a main body is provided. The power electronic technology is a key technology of a new energy power generation system, related research subjects are widely concerned, and the bidirectional full-bridge CLLC resonant converter is applied to high-frequency, high-voltage and high-power occasions due to the characteristics that the energy can flow bidirectionally, soft switching can work and the like.
In an application scene with a large voltage regulation range, a traditional pulse width control method is adopted, such as: the bidirectional CLLC resonant converter has disadvantages of a narrow soft switching range, a large return power, a large switching Frequency variation range, and the like, such as Pulse Width Modulation (PWM), Pulse Frequency Modulation (PFM), and an Extended Phase Shift control (EPS).
Disclosure of Invention
Aiming at the defects in the prior art, the invention provides a sectional control method of a bidirectional full-bridge CLLC resonant converter, PFM control is adopted when the voltage gain is higher, EPS control is adopted when the voltage gain is lower, and primary side switch soft turn-on can be realized in a larger PFM control range and a full EPS control range through sectional control, so that the backflow power caused by adopting the traditional phase-shift control is effectively reduced, and the larger switching frequency change caused by adopting the traditional frequency modulation control is reduced.
In order to achieve the purpose, the invention can be realized by the following technical scheme:
a control method of a full-bridge CLLC resonant converter is used for a bidirectional full-bridge CLLC resonant converter circuit, the bidirectional full-bridge CLLC resonant converter circuit comprises a primary side and a secondary side which are coupled through a transformer, the primary side comprises a first H bridge, and a first bridge arm of the first H bridge is formed by a switch tube S1And a switching tube S3The second bridge arm of the first H bridge is composed of a switch tube S2And a switching tube S4The secondary side comprises a second H bridge, and a first bridge arm of the second H bridge is composed of a switch tube S5And a switching tube S7The second H bridge is composed of a switch tube S2And a switching tube S4Are connected in series, the energy flows from the primary side to the secondary side,
the method comprises a first working mode and a second working mode, wherein the critical voltage gain of the converter is determined by the transformation ratio of the transformer, the voltage input by the converter and the voltage output by the converter, the first working mode is determined when the voltage gain of the actual working of the converter circuit is not higher than the critical voltage gain compared with the critical voltage gain, and the second working mode is determined when the voltage gain of the actual working is lower than the critical voltage gain;
the first operating mode includes:
the control waveforms of the switching tubes of the converter circuit are all square wave signals with the duty ratio of 50% under the control of PFM, the rising edge of each square wave signal controls the switching tube to be switched on, and the falling edge of each square wave signal controls the switching tube to be switched off, wherein the switching tube S1Switch tube S4Switch tube S5And a switching tube S8The same control signal flows in, the switch tube S2Switch tube S3Switch tube S6And a switching tube S7The inflowing control signals are the same, and the phase difference of the two control signals is pi;
voltage gain G for practical operation in this mode1：
Where k is the ratio of the exciting inductance to the resonant inductance of the transformer, and k is equal to Lm/Lr1(ii) a Q is the quality factor of the CLLC resonant converter, Q ═ Lr1/Cr1)0.5/Req；ReqConverting the equivalent impedance of the secondary side to the primary side for the CLLC resonant converter; f. ofnTo normalize frequency, fn＝fs/fr；fsIs the switching frequency; f. ofrIs the resonant frequency;
the second operating mode includes:
the EPS control is adopted, the control waveforms of all the switching tubes of the converter circuit are square wave signals with the duty ratio of 50%, the rising edge of each wave signal controls the switching tube to be switched on, the falling edge of each wave signal controls the switching tube to be switched off, and the switching tube S1And a switching tube S3Control signal complementation of (S), switching tube S2And a switching tube S4Control signal complementation, switchPipe S5And a switching tube S8Are the same, switch tube S6And a switching tube S7Are the same, switch tube S5And a switching tube S6Control signal complementation of (S), switching tube S1And a switching tube S3Control signal phase difference of D1/fsSwitching tube S1And a switching tube S5Control signal phase difference of D2/fsWherein: d1＝2D2；D1Is the phase-shift duty ratio of the primary full bridge; d2The phase-shift duty ratio of the secondary side full bridge;
voltage gain G for practical operation in this mode2：
In the formula, ZmTo the excitation impedance, Zm＝jωLm(ii) a j is an imaginary factor; omega is power frequency angular frequency; z1Is the primary side resonant impedance, Z1＝jωLr1+1/jωCr1；Z2Is secondary side resonance impedance, Z2＝jωL’r2+1/jωC’r2；ZeqIs the equivalent impedance of the secondary side,
Req＝8n2Ro/π2。
the control method of the full-bridge CLLC resonant converter further comprises the step of controlling the full-bridge CLLC resonant converter when the switching frequency f is lower than the preset switching frequency fsEqual to the resonant frequency frThen, the critical voltage gain G of the two working modes is obtained0。
The control method of the full-bridge CLLC resonant converter further comprises the step of controlling the bidirectional full-bridge CLLC resonant converterThe primary side of the CLLC resonant converter circuit further comprises: a voltage U of the converter input in parallel with the first H-bridgeiD.C. capacitor Ci。
The method for controlling the full-bridge CLLC resonant converter further includes: voltage U output by the converter connected in parallel with the second H-bridgeoD.C. capacitor CoVoltage equalizing resistor Ro。
In the method for controlling the full-bridge CLLC resonant converter, the output end of the first arm of the first H-bridge is connected in series with Cr1And Lr1And the resonant circuit is connected to one end of the primary side of the transformer, and the other end of the primary side of the transformer is connected to the output end of the second bridge arm of the first H bridge.
In the control method of the full-bridge CLLC resonant converter, the primary side of the transformer is further connected in parallel with the excitation inductor Lm。
In the method for controlling the full-bridge CLLC resonant converter, the output end of the first arm of the second H-bridge is connected in series with Cr2And Lr2And the resonant circuit is connected to one end of the secondary side of the transformer, and the other end of the secondary side of the transformer is connected to the output end of the second bridge arm of the second H bridge.
The control method of the full-bridge CLLC resonant converter further includes the step of obtaining the actually-operated voltage gain G1And G2And (4) deriving by using a fundamental wave analysis method.
Compared with the prior art, the invention has the beneficial effects that: the invention takes the voltage gain as a segmented basis, adopts PFM control when the voltage gain is higher, and adopts EPS control when the voltage gain is lower. The segmented control method enters constant frequency EPS control when the voltage gain is a low-voltage critical value, the switching frequency is not increased continuously along with the reduction of the voltage gain any more, and compared with the full-gain range which only adopts PFM control, the switching frequency change range of the converter is reduced, the soft switching-on range of the primary side switch of the converter is larger, and the switching loss of the converter is smaller; and when the voltage gain exceeds a critical value, the frequency conversion PFM control is started, the phase-shifting duty ratio is not reduced continuously along with the increase of the voltage gain, and compared with the full-gain range which only adopts EPS control, the converter has the advantages of smaller backflow power, smaller power loss and smaller current stress borne by a power element.
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In order to more clearly illustrate the technical solutions in the embodiments of the present invention, the drawings needed to be used in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and it is obvious for those skilled in the art that other drawings can be obtained according to these drawings without creative efforts.
Fig. 1 is a circuit diagram of a bidirectional full-bridge CLLC resonant converter according to an embodiment of the present invention;
FIG. 2 is a schematic diagram of a sectional control of a bidirectional full-bridge CLLC resonant converter according to an embodiment of the present invention;
FIG. 3 shows a switch tube S in the first operating mode of the embodiment of the present invention1-S8A waveform diagram of the control signal of (1);
FIG. 4 is a fundamental wave equivalent circuit diagram of the bidirectional full-bridge CLLC circuit according to the embodiment of the present invention;
FIG. 5 shows a second operating mode of the present invention, in which the switch tube S is turned on1-S8The waveform of the control signal of (1).
Detailed Description
The technical solutions in the embodiments of the present invention will be described clearly and completely with reference to the accompanying drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.
Example (b):
it should be noted that the terms "first," "second," and the like in the description and claims of the present invention and in the drawings described above are used for distinguishing between similar elements and not necessarily for describing a particular sequential or chronological order. It is to be understood that the data so used is interchangeable under appropriate circumstances such that the embodiments of the invention described herein are capable of operation in sequences other than those illustrated or described herein. Furthermore, the terms "comprises," "comprising," and any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, system, article, or apparatus that comprises a list of steps or elements is not necessarily limited to those steps or elements expressly listed, but may include other steps or elements not expressly listed or inherent to such process, method, article, or apparatus.
Referring to fig. 1 to 5, fig. 1 is a circuit diagram of a bidirectional full-bridge CLLC resonant converter according to an embodiment of the present invention; FIG. 2 is a schematic diagram of a sectional control of a bidirectional full-bridge CLLC resonant converter according to an embodiment of the present invention; FIG. 3 shows a switch tube S in the first operating mode of the embodiment of the present invention1-S8A waveform diagram of the control signal of (1); FIG. 4 is a fundamental wave equivalent circuit diagram of the bidirectional full-bridge CLLC circuit according to the embodiment of the present invention;
FIG. 5 shows a second operating mode of the present invention, in which the switch tube S is turned on1-S8The waveform of the control signal of (1).
PFM control is adopted when the voltage gain is high, EPS control is adopted when the voltage gain is low, soft switching-on of a switch at the primary side can be achieved within a large PFM control range and a full EPS control range through sectional control, backflow power caused by traditional phase-shift control is effectively reduced, and large switching frequency change caused by traditional frequency modulation control is reduced.
A bi-directional full bridge CLLC circuit is shown in fig. 1. Defining primary side as voltage UiOn the input side, the secondary side is a voltage UoAnd an output side. The primary side comprises an input capacitor CiFour switching tubes S forming a first H bridge1-S4Resonant inductor Lr1And a resonant inductor Cr1The secondary side comprises four switching tubes S forming a second H bridge5-S8Filter capacitor CoThe primary side and the secondary side are distributed on two sides of the transformer T.
More particularly, the originalThe side of the first H bridge comprises a first H bridge, and a first bridge arm of the first H bridge is composed of a switching tube S1And a switching tube S3The second bridge arm of the first H bridge is composed of a switch tube S2And a switching tube S4The secondary side of the first H bridge is composed of a second H bridge, and the first bridge arm of the second H bridge is composed of a switch tube S5And a switching tube S7Are connected in series, the second H bridge is composed of a switch tube S2And a switching tube S4The energy flows from the primary side to the secondary side.
In the above embodiment, the primary side of the bidirectional full-bridge CLLC resonant converter circuit further includes: voltage U of converter input in parallel with first H-bridgeiD.C. capacitor Ci。
In the above embodiment, the secondary side of the bidirectional full-bridge CLLC resonant converter circuit further includes: voltage U of converter output in parallel with second H-bridgeoD.C. capacitor CoVoltage equalizing resistor Ro。
In the above embodiment, the output end of the first arm of the first H-bridge is connected in series with Cr1And Lr1And the resonant circuit is connected to one end of the primary side of the transformer, and the other end of the primary side of the transformer is connected to the output end of the second bridge arm of the first H bridge. Further, the primary side of the transformer is also connected in parallel with an excitation inductor Lm。
In the above embodiment, the output end of the first bridge arm of the second H-bridge is connected in series with Cr2And Lr2And the resonant circuit is connected to one end of the secondary side of the transformer, and the other end of the secondary side of the transformer is connected to the output end of the second bridge arm of the second H bridge.
The principle of the segmented control of the bi-directional full-bridge CLLC current is shown in fig. 2, where energy flows from the primary side to the secondary side. Determining the operation mode of the converter according to the voltage gain required to be output by the converter when the voltage gain is higher than or equal to the critical value G of the sectional control0While operating in mode one with a boundary condition of [ Gmax，G0]At voltage gain below G0While operating in mode two with a boundary condition of [ G0，Gmin]。
The first working mode is PFM control mode, the switch tubeS1-S8As shown in fig. 3. S1、S4、S5And S8The incoming control signals are identical, S2、S3、S6And S7The control signals flowing in are the same, and the duty ratios of the two control signals are both 50% and complementary. The frequency of the switch control signal being fsAt this time by controlling fsTo control the variation of the voltage gain.
A fundamental wave equivalent circuit of the bidirectional full-bridge CLLC circuit is L 'as shown in FIG. 4'r2、C’r2The values of the resonance inductance and the resonance capacitance in the secondary side resonance circuit equivalent to the primary side are as follows when the transformer transformation ratio is n: l'r2＝Lr2/n2，C’r2＝n2Cr2，ReqIs equivalent to the load resistance of the primary side of the transformer.
Deriving voltage gain G in first operating mode by fundamental analysis1The expression is shown as formula (1):
where k is the ratio of the exciting inductance to the resonant inductance of the transformer, and k is equal to Lm/Lr1(ii) a Q is the quality factor of the CLLC resonant converter, Q ═ Lr1/Cr1)0.5/Req；ReqConverting the equivalent impedance of the secondary side to the primary side for the CLLC resonant converter; f. ofnTo normalize frequency, fn＝fs/fr；fsIs the switching frequency; f. ofrIs the resonant frequency.
The second working mode is an EPS control mode, and a switch tube S1-S8As shown in fig. 5. S1-S8The control signals flowing in are all square waves with the duty ratio of 50 percent, S1And S3Are complementary to each other, S2And S4Are complementary to each other, S5And S8Is the same as the control signal of S6And S7Is the same as the control signal of S5And S6Control ofSystem signal complementation, S1And S3Has a control signal phase difference of D1/fs，S1And S5Has a control signal phase difference of D2/fsWherein D is1＝2D2. At this time the switching frequency fsUnchanged by controlling the phase difference D1To control the variation of the voltage gain.
Deducing voltage gain G in the second working mode by using fundamental wave analysis method2The expression is shown as formula (2):
in the formula, ZmTo the excitation impedance, Zm＝jωLm(ii) a j is an imaginary factor; omega is power frequency angular frequency; z1Is the primary side resonant impedance, Z1＝jωLr1+1/jωCr1；Z2Is secondary side resonance impedance, Z2＝jωL’r2+1/jωC’r2；ZeqIs the equivalent impedance of the secondary side,
Req＝8n2Ro/π2。
switching frequency fsEqual to the resonant frequency frThen, the sectional critical value G of two working modes can be calculated and obtained from (1)0When G is not less than G0The time converter operates in mode one when G < G0The time transformer operates in mode two.
In the sectional control, in the first working mode, the primary side switch can be at the switching frequency fsLess than the resonant frequency frAnd soft switching-on can be realized in the whole range in the second working mode.
In one example, compared with the traditional control method of PFM, the two control methods are respectively adopted to realize the same voltage gain of 0.8-1.2, the switching frequency range of the traditional PFM control is 56kHz-275kHz, and the switching frequency range of the sectional control is 56kHz-96.5kHz, so that the control method has obvious advantages.
The invention combines the traditional control methods, and divides the control into two sections: PFM control is adopted in a higher voltage gain section; the lower voltage gain section is controlled using EPS. The segmented control can realize the soft switching-on of the primary side switch in a larger PFM control range and a full EPS control range, and has smaller reflux power compared with the traditional phase-shift control and narrower switching frequency change range compared with the traditional frequency modulation control.
In the description herein, references to the description of the term "one embodiment," "some embodiments," "an example," "a specific example," or "some examples," etc., mean that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the invention. In this specification, the schematic representations of the terms used above are not necessarily intended to refer to the same embodiment or example. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples. Furthermore, various embodiments or examples and features of different embodiments or examples described in this specification can be combined and combined by one skilled in the art without contradiction.
The above embodiments are only for illustrating the technical concept and features of the present invention, and the purpose thereof is to enable those skilled in the art to understand the contents of the present invention and implement the present invention accordingly, and not to limit the protection scope of the present invention accordingly. All equivalent changes or modifications made in accordance with the spirit of the present disclosure are intended to be covered by the scope of the present disclosure.
Claims (8)
1. Control method of full-bridge CLLC resonant converter, which is used for bidirectional full-bridge CLLC resonant converterThe circuit, two-way full-bridge CLLC resonant converter circuit includes through transformer coupling' S primary side and vice limit side, primary side includes first H bridge, the first bridge arm of first H bridge is by switch tube S1And a switching tube S3The second bridge arm of the first H bridge is composed of a switch tube S2And a switching tube S4The secondary side comprises a second H bridge, and a first bridge arm of the second H bridge is composed of a switch tube S5And a switching tube S7The second H bridge is composed of a switch tube S2And a switching tube S4Is formed by connecting in series, the energy flows from the primary side to the secondary side, and is characterized in that,
the method comprises a first working mode and a second working mode, wherein the critical voltage gain of the converter is determined by the transformation ratio of the transformer, the voltage input by the converter and the voltage output by the converter, the first working mode is determined when the voltage gain of the actual working of the converter circuit is not higher than the critical voltage gain compared with the critical voltage gain, and the second working mode is determined when the voltage gain of the actual working is lower than the critical voltage gain;
the first operating mode includes:
the control waveforms of the switching tubes of the converter circuit are all square wave signals with the duty ratio of 50% under the control of PFM, the rising edge of each square wave signal controls the switching tube to be switched on, and the falling edge of each square wave signal controls the switching tube to be switched off, wherein the switching tube S1Switch tube S4Switch tube S5And a switching tube S8The same control signal flows in, the switch tube S2Switch tube S3Switch tube S6And a switching tube S7The inflowing control signals are the same, and the phase difference of the two control signals is pi;
voltage gain G for practical operation in this mode1：
Wherein k is transformer excitation inductanceRatio to resonant inductance, k ═ Lm/Lr1(ii) a Q is the quality factor of the CLLC resonant converter, Q ═ Lr1/Cr1)0.5/Req；ReqConverting the equivalent impedance of the secondary side to the primary side for the CLLC resonant converter; f. ofnTo normalize frequency, fn＝fs/fr；fsIs the switching frequency; f. ofrIs the resonant frequency;
the second operating mode includes:
the EPS control is adopted, the control waveforms of all the switching tubes of the converter circuit are square wave signals with the duty ratio of 50%, the rising edge of each wave signal controls the switching tube to be switched on, the falling edge of each wave signal controls the switching tube to be switched off, and the switching tube S1And a switching tube S3Control signal complementation of (S), switching tube S2And a switching tube S4Control signal complementation of (S), switching tube S5And a switching tube S8Are the same, switch tube S6And a switching tube S7Are the same, switch tube S5And a switching tube S6Control signal complementation of (S), switching tube S1And a switching tube S3Control signal phase difference of D1/fsSwitching tube S1And a switching tube S5Control signal phase difference of D2/fsWherein: d1＝2D2；D1Is the phase-shift duty ratio of the primary full bridge; d2The phase-shift duty ratio of the secondary side full bridge;
voltage gain G for practical operation in this mode2：
In the formula, ZmTo the excitation impedance, Zm＝jωLm(ii) a j is an imaginary factor; omega is power frequency angular frequency; z1Is the primary side resonant impedance, Z1＝jωLr1+1/jωCr1；Z2Is secondary side resonance impedance, Z2＝jωL’r2+1/jωC’r2；ZeqIs a pairThe equivalent impedance of the edge is obtained,
Req＝8n2Ro/π2。
2. the method of claim 1 wherein the full bridge CLLC resonant converter is controlled at a switching frequency fsEqual to the resonant frequency frThen, the critical voltage gain G of the two working modes is obtained0。
3. The method of claim 1, wherein the primary side of the bi-directional full-bridge CLLC resonant converter circuit further comprises: a voltage U of the converter input in parallel with the first H-bridgeiD.C. capacitor Ci。
4. The method of claim 1, wherein the secondary side of the bi-directional full-bridge CLLC resonant converter circuit further comprises: voltage U output by the converter connected in parallel with the second H-bridgeoD.C. capacitor CoVoltage equalizing resistor Ro。
5. Method for controlling a full-bridge CLLC resonant converter according to claim 1, characterized in that the output of the first leg of the first H-bridge is connected in series Cr1And Lr1And the resonant circuit is connected to one end of the primary side of the transformer, and the other end of the primary side of the transformer is connected to the output end of the second bridge arm of the first H bridge.
6. According to claimThe method for controlling a full-bridge CLLC resonant converter according to claim 5, wherein an excitation inductor L is further connected in parallel to the primary side of the transformerm。
7. Method for controlling a full-bridge CLLC resonant converter according to claim 1, characterized in that the output of the first leg of the second H-bridge is connected in series Cr2And Lr2And the resonant circuit is connected to one end of the secondary side of the transformer, and the other end of the secondary side of the transformer is connected to the output end of the second bridge arm of the second H bridge.
8. Method for controlling a full-bridge CLLC resonant converter according to claim 1, characterized by the fact that the voltage gain G of the actual operation is1And G2And (4) deriving by using a fundamental wave analysis method.
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN116566209A (en) * | 2023-02-24 | 2023-08-08 | 江苏大学 | Control method of isolated bidirectional CLLLC resonant converter |
| WO2023225882A1 (en) * | 2022-05-25 | 2023-11-30 | 深圳市富兰瓦时技术有限公司 | Soft starting method, power conversion system and household energy storage system |
| CN117254698A (en) * | 2023-11-15 | 2023-12-19 | 浙江大学 | CLLC circuit bidirectional switching control method outside limit gain |
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