CN111709202A - Harmonic steady-state value-based modeling method for small-signal harmonic equivalent circuit of two-stage DC-DC converter - Google Patents
Harmonic steady-state value-based modeling method for small-signal harmonic equivalent circuit of two-stage DC-DC converter Download PDFInfo
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Abstract
The invention discloses a harmonic steady state value-based modeling method for a small-signal harmonic equivalent circuit of a two-stage DC-DC converter, which comprises the steps of determining a duty ratio according to the voltage requirements of the front and rear stages of the DC/DC converter, and forming a harmonic state space model under a steady state condition; obtaining harmonic steady-state values of all state variables by the harmonic state space model; adding small disturbance to each input variable in the harmonic state space model to form a harmonic small signal model; generating a plurality of harmonic equivalent circuits containing controlled sources based on the harmonic small signal model and the harmonic steady-state values of the state variables; and forming a two-stage DC/DC converter small-signal harmonic equivalent circuit based on the equivalent controlled source relation of each harmonic equivalent circuit containing a controlled source. The invention firstly provides an equivalent circuit construction method according to a harmonic model of the DC-DC converter, and finally obtains the harmonic equivalent circuit of the DC-DC converter, thereby realizing the organic combination of the mathematical principle and the circuit characteristic.
Description
Technical Field
The invention belongs to the field of power electronic modeling, and particularly relates to a harmonic equivalent circuit modeling method of a two-stage DC-DC converter based on a harmonic state space.
Background
At present, for converter modeling, a state space averaging method based on linear time variation is widely used, but the accuracy is low, and the actual dynamic process of a high-frequency converter cannot be well reflected. In recent years, a modeling method based on a harmonic state space is applied to modeling of power electronic transformer equipment, and the method analyzes harmonic coupling characteristics and harmonic stability by adding extra harmonic impedance. However, the harmonic state space modeling method is mainly used for modeling of a single power electronic device at present, and when a system with multiple converters is faced, a state equation in a pure mathematical form is too abstract, so that a circuit characteristic method deeper than general numerical simulation is urgently needed to be combined with the harmonic state space mathematical description.
Disclosure of Invention
Aiming at the problems, the invention firstly provides an equivalent circuit construction method according to a harmonic model of the DC-DC converter, and finally obtains the harmonic equivalent circuit of the DC-DC converter, thereby realizing the organic combination of the mathematical principle and the circuit characteristics.
In order to achieve the technical purpose and achieve the technical effects, the invention is realized by the following technical scheme:
a modeling method for a small-signal harmonic equivalent circuit of a two-stage DC-DC converter based on harmonic steady-state values comprises the following steps:
determining a duty ratio according to voltage requirements of front and rear stages of a DC/DC converter to form a harmonic state space model under a steady state condition;
obtaining harmonic steady-state values of all state variables by the harmonic state space model;
adding small disturbance to each input variable in the harmonic state space model to form a harmonic small signal model;
generating a plurality of harmonic equivalent circuits containing controlled sources based on the harmonic small signal model and the harmonic steady-state values of the state variables;
and forming a small-signal harmonic equivalent circuit of the two-stage DC/DC converter based on the equivalent controlled source relation of the harmonic equivalent circuits containing the controlled sources, and completing the modeling of the harmonic equivalent circuit of the two-stage DC-DC converter.
Optionally, the harmonic state space model specifically includes:
in the formula, s is a complex number and represents the dynamic behavior of the state variable in a frequency domain; o is a 2h +1 order zero matrix, I is a 2h +1 order identity matrix, and h is the truncated harmonic frequency; c1Preceding stage capacitance parameter, L, for a two-stage DC-DC converter1Preceding stage inductance parameter, C, for a two-stage DC-DC converter2For the subsequent capacitance parameter, L, of a two-stage DC-DC converter2The inductance parameter of the later stage of the two-stage DC-DC converter, R is the load parameter of the two-stage DC-DC converter, Λ ═ diag (-j2 π hf)0,…-j2πf0,0,j2πf0,…-j2πhf0) Displaying the harmonic information of the state variable; d1And D2Is 2h +1 order d1(t) and d2(t) extended Dual toeplitz matrix, IL1、UC1、IL2、UC2And V1Representing a vector of frequency domain amplitudes of each of the positive and negative harmonics.
Alternatively,
alternatively,
alternatively,
alternatively,
IL2＝[IL2-h,…,IL20,…,IL2h]T；UC1＝[UC1-h,…,UC10,…,UC1h]T；UC2＝[UC2-h,…,UC20,…,UC2h]T。
optionally, the calculation formula of the harmonic steady-state value of each state variable is as follows:
in the formula, O is a 2h +1 order zero matrix, I is a 2h +1 order identity matrix, and h is the truncated harmonic frequency; c1Preceding stage capacitance parameter, L, for a two-stage DC-DC converter1Preceding stage inductance parameter, C, for a two-stage DC-DC converter2For the subsequent capacitance parameter, L, of a two-stage DC-DC converter2The inductance parameter of the later stage of the two-stage DC-DC converter, R is the load parameter of the two-stage DC-DC converter, Λ ═ diag (-j2 π hf)0,…-j2πf0,0,j2πf0,…-j2πhf0) Displaying the harmonic information of the state variable; d1And D2Is 2h +1 order d1(t) and d2(t) extended Dual toeplitz matrix, IL1ss、UC1ss、IL2ssAnd UC2ssIs represented byL1、UC1、IL2And UC2The harmonic steady state value of (1) is in a 2h + 1-dimensional vector form; v1And the 2h + 1-dimensional vector is formed by the frequency domain amplitude of the harmonic wave of the input voltage at the front stage.
Optionally, the harmonic small signal model is:
in the formula,. DELTA.V1The input voltage disturbance quantity is in a 2h + 1-dimensional vector form; delta D1、ΔD2The duty ratio disturbance quantity is in a 2h +1 order dual toeplitz matrix form; delta IL1、ΔUC1、ΔIL1、ΔUC2The disturbance quantities of the four state variables are in a 2h +1 dimensional vector form.
Compared with the prior art, the invention has the beneficial effects that:
1. according to the method, a small-signal harmonic model is constructed, so that a transfer function based on frequency domain harmonics is formed conveniently, and a controller is designed based on a frequency domain harmonic space, so that the influence of system harmonics on the stability of a system is researched;
2. the method realizes the mapping of the mathematical model to the circuit model, is favorable for understanding the harmonic model, and has reference significance for establishing the harmonic equivalent circuit and analyzing the stability of the AC/DC hybrid power distribution network under the background of the multi-converter.
Drawings
In order that the present disclosure may be more readily and clearly understood, reference is now made to the following detailed description of the present disclosure taken in conjunction with the accompanying drawings, in which:
FIG. 1 is a two-stage DC/DC converter topology;
FIG. 2 is a harmonic equivalent circuit represented by equation 7 (a);
FIG. 3 is a harmonic equivalent circuit represented by equation 7 (b);
FIG. 4 is a harmonic equivalent circuit represented by equation 7 (c);
FIG. 5 is a harmonic equivalent circuit represented by equation 7 (d);
FIG. 6 is a harmonic equivalent circuit of a finally obtained unified two-stage DC/DC converter;
FIG. 7 is a flow chart of a harmonic equivalent circuit modeling method of a two-stage DC-DC converter based on a harmonic state space according to the invention;
fig. 8 is a schematic diagram of a process for processing variables into vector form.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is further described in detail with reference to the following embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and do not limit the scope of the invention.
The following detailed description of the principles of the invention is provided in connection with the accompanying drawings.
The invention discloses a harmonic equivalent circuit modeling method of a two-stage DC-DC converter based on a harmonic state space, which is used for enabling the implementation mode to be representative, adopts the topology of a front-stage Buck and a rear-stage Boost to be equivalent to a DC/DC converter with voltage reduction and voltage Boost functions in a direct-current power distribution network, and takes an inductor L as a front-stage parameter11.6mH, capacitance C115 muF, input voltage V180V, switching period function d1(t) information as switching frequency f1The required voltage on the capacitor is 56V at 8 kHz; the latter parameter is inductance L21.2mH, capacitance C 220 μ F, load R 220 Ω, switching period function d2(t) information as switching frequency f210kHz, the load voltage is 70V output. The modeling method specifically comprises the following steps:
step 1: from the preceding capacitor voltage, the duty ratio d is obtained170 percent; the duty ratio d is obtained according to the requirement of the output voltage of the later stage 220% by weight. The time domain state space equation of the two-stage DC/DC converter obtained at the moment is as follows (1):
in the formula (1), d1(t) is corresponding to d1A rectangular wave with a frequency of 8kHz, a duty cycle of 70% and a phase of 0; d2(t) is corresponding to d2A rectangular wave having a frequency of 10kHz, a duty ratio of 20%, and a phase of 0. The above time-varying stateThe equation can be converted into a stationary harmonic state space equation of the frequency domain as shown in equation (2), i.e., a harmonic state space model under a steady state condition.
In the formula (2), s is a complex number and represents the dynamic behavior of the state variable in a frequency domain; o is a 2h +1 order zero matrix, I is a 2h +1 order identity matrix, and h is the truncated harmonic frequency; c1Is a preceding stage capacitance parameter, L, of the topology of FIG. 11Is a topological preceding stage inductance parameter, C, of FIG. 12Is a parameter of the post-stage capacitance of the topology of FIG. 1, L2The inductance parameter of the later stage of the topology of the figure 1, R is the load (resistance) parameter of the topology of the figure 1, Λ ═ diag (-j2 π hf)0,…-j2πf0,0,j2πf0,…-j2πhf0) Harmonic information of the state variables is displayed. D1And D2Is 2h +1 order d1(t) and d2(t) extended dual toeplitz matrices as in formula (3), IL1、UC1、IL2、UC2And V1As shown in equation (4), a vector formed by the frequency domain amplitudes of the positive and negative harmonics is expressed.
IL1＝[IL1-h,…,IL10,…,IL1h]T；IL2＝[IL2-h,…,IL20,…,IL2h]T
UC1＝[UC1-h,…,UC10,…,UC1h]T；UC2＝[UC2-h,…,UC20,…,UC2h]T(4)
Step 2: and obtaining harmonic equivalent circuits and harmonic steady-state values of all variables by using the harmonic state space model under the steady-state condition in Step1, namely making the left side of the equal sign of the formula (2) be zero, and obtaining the steady-state value of the state variable as the formula (5).
Step 3: adding small disturbance to each input variable of the harmonic state space model under the steady state condition in Step1, and adding small disturbance to the input voltage V1And front-to-back stage duty cycle d1、d2Making minor perturbations near the steady-state operating point, i.e. in equation (2), let V1＝V1ss+ΔV1，D1＝D1ss+ΔD1，D2＝D2ss+ΔD2Thereby causing a small disturbance of each state variable, i.e. I, in the two-stage DC/DC converter circuitL1＝IL1ss+ΔIL1,UC1＝UC1ss+ΔUC1,IL2＝IL1ss+ΔIL1,UC2＝UC2ss+ΔUC2Then equation (2) is transformed into equation (6), where Λ is a block diagonal array formed by n diagonal arrays Λ, n is an independent state variable or the number of energy storage elements in the topology, h is the number of times of truncated harmonics in the modeling, the larger the number of times, the more harmonic information is contained, f is0For harmonic fundamental frequencies, a divisor of the switching frequency is typically selected to contain harmonic information of the switching frequency.
s(Xss+ΔX)＝(Ass+ΔA-Λ)(Xss+ΔX)+(Bss+ΔB)(Vss+ΔV)＝(Ass-Λ)Xss+BssVss+(Ass-Λ)ΔX+ΔAXss+BssΔV+ΔBVss(6)
Bss＝[D1ss/L1O O O]TΔB＝[ΔD1/L1O O O]T
Λ＝diag(Λ)nΛ＝diag(-j2πhf0,…,-j2πf0,0,j2πf0,…,j2πhf0)
Four independent small signal harmonic expressions are available at this time:
to form the state equation in the conventional form, it is necessary to process the variables into vector form, so Δ D in equation (7)1、ΔD2、V1ss、IL2ss、UC2ssThe transformation of FIG. 8 is performed to extract Δ D1、ΔD2Transforming it from dual toeplitz matrix form to column vector, transforming V1ss、IL2ss、UC2ssTransforming from vector form to dual toeplitz matrix, the transformation being preceded and followed by: delta D1V1ss＝V′1ssΔD′1，ΔD2UC2ss＝U′C2ssΔD′2，ΔD2IL2ss＝I′L2ssΔD′2The three equations hold, and the harmonic small signal equation of the available two-stage DC/DC converter is in the form of equation (8).
Step 4: the equivalent circuits are plotted according to the harmonic small signal model in Step3 and the harmonic steady state values of the variables, as shown in fig. 2, fig. 3, fig. 4, and fig. 5.
FIG. 2 is a graph of equivalent controlled voltage source Δ UC1An equivalent voltage source D1ssΔV1、ΔD1V1ssEquivalent inductance L with harmonic wave1Composition I,. DELTA.UC1、D1ssΔV1And V1ssΔD1Are 2h +1 dimensional vectors, and have the form shown in formula (4), including + -h subharmonic information and 0 th DC component, Δ UC1The controlled variable is DeltaUC1The control coefficient is a unit matrix I; l is1I is in the form of a 2h +1 order matrix. The current in the loop is Δ IL1In the form of formula (4); the voltage on the inductor is L1I(sI+Λ)ΔIL1。
FIG. 3 is a schematic diagram of an equivalent controlled current source Δ IL1Equivalent controlled current source delta IL2Harmonic equivalent capacitor C1I is composed of (A), (B), (C. Delta IL1、ΔIL2Is a 2h + 1 dimensional vector with the form of formula (4), C1I is in a 2h +1 order matrix form, and the voltage at two ends of the equivalent capacitor is delta UC1Is a 2h + 1 dimensional vector; delta IL1The controlled variable is Delta IL1Control coefficient I, Δ IL2The situation is the same; the equivalent harmonic current flowing through the capacitor is C1I(sI+Λ)ΔUC1。
FIG. 4 is a graph of equivalent controlled voltage source Δ UC1Equivalent controlled voltage source (I-D)2ss)ΔUC2Equivalent voltage source delta D2UC2ssHarmonic equivalent inductance L2I is composed of (A), (B), (C. Delta UC1、ΔUC2、ΔIL2Is a 2h + 1 dimensional vector of the formula (4), L2I is a 2h +1 order matrix form; delta UC1The controlled variable is DeltaUC1Control coefficient I, (I-D)2ss)ΔUC2The controlled variable is DeltaUC2Control coefficient I-D2ss(ii) a The voltage across the equivalent inductor is L2I(sI+Λ)ΔIL2And is a 2h +1 dimensional vector.
FIG. 5 is a schematic diagram of an equivalent controlled current source (I-D)2ss)ΔIL2Equivalent current source delta D2IL2ssHarmonic waves, etcEffective capacitance C2I. The harmonic equivalent capacitance RI. Delta IL2Is a 2h + 1 dimensional vector with the form of formula (4), C2I and RI are in 2h +1 order matrix form, and the voltage at two ends of the equivalent capacitor is delta UC2Is a 2h + 1 dimensional vector; (I-D)2ss)ΔIL2The controlled variable is Delta IL2Control coefficient I-D2ss(ii) a The equivalent harmonic current flowing through the capacitor is C2I(sI+Λ)ΔUC2。
Wherein the values of the equivalent harmonic inductance LI, the equivalent harmonic capacitance CI and the equivalent harmonic resistance RI are in a diagonal matrix form of formula (9), which shows that the dynamic effect is provided for each order harmonic, and the differential relation between the inductance current and the capacitance voltage in the original time domain is shown as LI (sI + Λ) delta I in the harmonic frequency domainLAnd CI (sI + Λ) Δ UCWherein LI (sI + Λ) Δ ILRepresents the harmonic voltage across the equivalent harmonic inductance, CI (sI + Λ) Δ UCRepresenting the harmonic current through the equivalent harmonic inductance.
LI＝diag(L)2h+1CI＝diag(C)2h+1RI＝diag(R)2h+1(9)
Step 5: the controlled sources in fig. 2, 3, 4 and 5 are equivalent to a harmonic equivalent circuit coupled by a transformer according to the ideal transformer characteristic, such as fig. 6, and the harmonic equivalent inductance L1I and L1I. Harmonic equivalent capacitance C2I and C1I. Harmonic equivalent resistance RI and harmonic equivalent power supply D1ssΔUC、ΔD1V1ss、ΔD2UC2ssAnd Δ D2IL2ssAnd a harmonic equivalent transformer with a transformation ratio of I-D2ss: I. the equivalent controlled sources with controlled coefficients as the identity matrix I in fig. 2 to 5 are directly interconnected in the circuit of fig. 6.
Furthermore, KCL and KVL are written into the harmonic equivalent circuit in sequence, a formula (8) can be reversely deduced, the correctness of the harmonic equivalent circuit is verified, and the construction of the two-stage DC/DC converter harmonic equivalent circuit model is completed.
The foregoing shows and describes the general principles and broad features of the present invention and advantages thereof. It will be understood by those skilled in the art that the present invention is not limited to the embodiments described above, which are described in the specification and illustrated only to illustrate the principle of the present invention, but that various changes and modifications may be made therein without departing from the spirit and scope of the present invention, which fall within the scope of the invention as claimed. The scope of the invention is defined by the appended claims and equivalents thereof.
Claims (8)
1. A modeling method for a small-signal harmonic equivalent circuit of a two-stage DC-DC converter based on a harmonic steady-state value is characterized by comprising the following steps:
determining a duty ratio according to voltage requirements of front and rear stages of a DC/DC converter to form a harmonic state space model under a steady state condition;
obtaining harmonic steady-state values of all state variables by the harmonic state space model;
adding small disturbance to each input variable in the harmonic state space model to form a harmonic small signal model;
generating a plurality of harmonic equivalent circuits containing controlled sources based on the harmonic small signal model and the harmonic steady-state values of the state variables;
and forming a small-signal harmonic equivalent circuit of the two-stage DC/DC converter based on the equivalent controlled source relation of the harmonic equivalent circuits containing the controlled sources, and completing the modeling of the harmonic equivalent circuit of the two-stage DC-DC converter.
2. The modeling method for the small-signal harmonic equivalent circuit of the two-stage DC-DC converter based on the harmonic steady-state value as claimed in claim 1, characterized in that: the harmonic state space model specifically comprises:
in the formula, s is a complex number and represents the dynamic behavior of the state variable in a frequency domain; o is a 2h +1 order zero matrix, I is a 2h +1 order identity matrix, and h is the truncated harmonic frequency; c1Preceding stage capacitance parameter, L, for a two-stage DC-DC converter1Pre-inductor for two-stage DC-DC converterParameter, C2For the subsequent capacitance parameter, L, of a two-stage DC-DC converter2The inductance parameter of the later stage of the two-stage DC-DC converter, R is the load parameter of the two-stage DC-DC converter, Λ ═ diag (-j2 π hf)0,…-j2πf0,0,j2πf0,…-j2πhf0) Displaying the harmonic information of the state variable; d1And D2Is 2h +1 order d1(t) and d2(t) extended Dual toeplitz matrix, IL1、UC1、IL2、UC2And V1Representing a vector of frequency domain amplitudes of each of the positive and negative harmonics.
3. The modeling method for the small-signal harmonic equivalent circuit of the two-stage DC-DC converter based on the harmonic steady-state value as claimed in claim 2, characterized in that:
4. the modeling method for small-signal harmonic equivalent circuit of two-stage DC-DC converter based on harmonic steady-state value according to claim 2,
5. the modeling method for small-signal harmonic equivalent circuit of two-stage DC-DC converter based on harmonic steady-state value according to claim 2,
6. the modeling method for the small-signal harmonic equivalent circuit of the two-stage DC-DC converter based on the harmonic steady-state value as claimed in claim 2, wherein I isL1＝[IL1-h,…,IL10,…,IL1h]T；IL2＝[IL2-h,…,IL20,…,IL2h]T；UC1＝[UC1-h,…,UC10,…,UC1h]T；UC2＝[UC2-h,…,UC20,…,UC2h]T。
7. The modeling method for the small-signal harmonic equivalent circuit of the two-stage DC-DC converter based on the harmonic steady-state value as claimed in claim 1, wherein the harmonic steady-state value of each state variable is calculated by the following formula:
in the formula, O is a 2h +1 order zero matrix, I is a 2h +1 order identity matrix, and h is the truncated harmonic frequency; c1Preceding stage capacitance parameter, L, for a two-stage DC-DC converter1Preceding stage inductance parameter, C, for a two-stage DC-DC converter2For the subsequent capacitance parameter, L, of a two-stage DC-DC converter2The inductance parameter of the later stage of the two-stage DC-DC converter, R is the load parameter of the two-stage DC-DC converter, Λ ═ diag (-j2 π hf)0,…-j2πf0,0,j2πf0,…-j2πhf0) Displaying the harmonic information of the state variable; d1And D2Is 2h +1 order d1(t) and d2(t) extended Dual toeplitz matrix, IL1ss、UC1ss、IL2ssAnd UC2ssIs represented byL1、UC1、IL2And UC2The harmonic steady state value of (1) is in a 2h + 1-dimensional vector form; v1And the 2h + 1-dimensional vector is formed by the frequency domain amplitude of the harmonic wave of the input voltage at the front stage.
8. The modeling method for the harmonic steady-state value-based two-stage DC-DC converter small-signal harmonic equivalent circuit of claim 7, wherein the harmonic small-signal model is as follows:
in the formula,. DELTA.V1The input voltage disturbance quantity is in a 2h + 1-dimensional vector form; delta D1、ΔD2The duty ratio disturbance quantity is in a 2h +1 order dual toeplitz matrix form; delta IL1、ΔUC1、ΔIL1、ΔUC2The disturbance quantities of the four state variables are in a 2h +1 dimensional vector form.
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112271913A (en) * | 2020-11-11 | 2021-01-26 | 南方电网科学研究院有限责任公司 | Method and device for calculating direct current harmonic impedance of 12-pulse current conversion system |
| CN115021557A (en) * | 2022-06-14 | 2022-09-06 | 北京交通大学 | Application method of Boost _ LLC simplified small signal model |
Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109617405A (en) * | 2018-12-21 | 2019-04-12 | 南京工程学院 | A kind of DC/DC converter modeling method based on harmonic wave state space |
| US20190267951A1 (en) * | 2018-02-28 | 2019-08-29 | Avago Technologies General Ip (Singapore) Pte. Ltd | Amplifier with second-harmonic trap |
| CN110557029A (en) * | 2019-10-16 | 2019-12-10 | 艾尚储能科技(苏州)有限公司 | soft switching method of double-active full-bridge direct current converter under multiple phase-shift control |
| CN110707935A (en) * | 2019-10-16 | 2020-01-17 | 艾尚储能科技(苏州)有限公司 | Optimization control method of double-active full-bridge direct current converter |
| CN110943456A (en) * | 2019-12-11 | 2020-03-31 | 中国南方电网有限责任公司超高压输电公司检修试验中心 | Small signal harmonic state space modeling method and device for LCC-HVDC system |
| CN111027269A (en) * | 2019-12-26 | 2020-04-17 | 南京工程学院 | Two-stage DC/DC converter modeling method based on harmonic equivalent circuit |
-
2020
- 2020-06-03 CN CN202010493005.8A patent/CN111709202B/en active Active
Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20190267951A1 (en) * | 2018-02-28 | 2019-08-29 | Avago Technologies General Ip (Singapore) Pte. Ltd | Amplifier with second-harmonic trap |
| CN109617405A (en) * | 2018-12-21 | 2019-04-12 | 南京工程学院 | A kind of DC/DC converter modeling method based on harmonic wave state space |
| CN110557029A (en) * | 2019-10-16 | 2019-12-10 | 艾尚储能科技(苏州)有限公司 | soft switching method of double-active full-bridge direct current converter under multiple phase-shift control |
| CN110707935A (en) * | 2019-10-16 | 2020-01-17 | 艾尚储能科技(苏州)有限公司 | Optimization control method of double-active full-bridge direct current converter |
| CN110943456A (en) * | 2019-12-11 | 2020-03-31 | 中国南方电网有限责任公司超高压输电公司检修试验中心 | Small signal harmonic state space modeling method and device for LCC-HVDC system |
| CN111027269A (en) * | 2019-12-26 | 2020-04-17 | 南京工程学院 | Two-stage DC/DC converter modeling method based on harmonic equivalent circuit |
Non-Patent Citations (3)
| Title |
|---|
| PLESNIK, M 等: "Efficient Steady-State Simulation of Switching Power Converter Circuits", 《IEEE TRANSACTIONS ON COMPONENTS PACKAGING AND MANUFACTURING TECHNOLOGY》, vol. 9, no. 7, pages 1328 - 1336, XP011735124, DOI: 10.1109/TCPMT.2018.2873486 * |
| SHEN LI等: "Two-stage DC/DC converter modeling method based on harmonic equivalent circuit", 《IEEE PES ASIA-PACIFIC POWER AND ENERGY ENGINEERING CONFERENCE(APPEEC)》, pages 1 - 5 * |
| 钟松锦: "应用于电梯节能系统的双向DC-DC变换器关键技术研究", 《CNKI中国优秀硕士毕业论文全文库（工程科技Ⅱ辑）》, no. 06, pages 038 - 784 * |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112271913A (en) * | 2020-11-11 | 2021-01-26 | 南方电网科学研究院有限责任公司 | Method and device for calculating direct current harmonic impedance of 12-pulse current conversion system |
| CN115021557A (en) * | 2022-06-14 | 2022-09-06 | 北京交通大学 | Application method of Boost _ LLC simplified small signal model |
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| CN111709202B (en) | 2024-02-09 |
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