CN110034674B - High-gain bidirectional three-phase DC-DC converter and control method - Google Patents

High-gain bidirectional three-phase DC-DC converter and control method Download PDF

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CN110034674B
CN110034674B CN201810031749.0A CN201810031749A CN110034674B CN 110034674 B CN110034674 B CN 110034674B CN 201810031749 A CN201810031749 A CN 201810031749A CN 110034674 B CN110034674 B CN 110034674B
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voltage
charging
power switch
capacitor
switch tube
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CN110034674A (en
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王玉斌
王璠
潘腾腾
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Shandong University
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Shandong University
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    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00Conversion of dc power input into dc power output
    • H02M3/02Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

Abstract

The invention discloses a high-gain bidirectional three-phase DC-DC converter and a control method, belonging to the bidirectional DC-DC converter in the field of power electronicsThe high frequency power changes direction. The main circuit of the high-gain bidirectional three-phase DC-DC converter mainly comprises three inductors L1~L2Six power switch tubes S1~S6Four capacitors Cf、CL、CH1、CH2And (4) forming. Wherein, the inductance L1Respectively connected with a power switch tube S1And a power switch tube S4Connected, inductor L2Respectively connected with a power switch tube S2And a capacitor CfConnected, inductor L3Respectively connected with a power switch tube S3Capacitor CH1And a capacitor CH2Are connected. The 180-degree staggered control mode in the control method can increase the duty ratio range to the maximum extent and reduce the total voltage ripple on the high-voltage side; the 120 deg. staggered control mode can reduce the total current ripple at the low-voltage side to the maximum extent. The invention has higher voltage conversion ratio, the power switch tube has lower voltage stress, and the two high-voltage side capacitors CH1And CH2Automatic voltage stabilization can be realized, and automatic current sharing is realized by the three filter inductors.

Description

High-gain bidirectional three-phase DC-DC converter and control method
Technical Field
The invention relates to the technical field of DC-DC converters, in particular to a high-gain bidirectional three-phase DC-DC converter and a control method thereof.
Background
In recent years, with the development of fields such as new energy power generation, electric vehicles, energy storage systems, and the like, a bidirectional high-gain DC-DC converter has received extensive attention and research.
In the prior art, the circuit topology of the conventional bidirectional three-phase DC-DC converter is as shown in fig. 1, and is affected by parasitic parameters in the circuit, especially the equivalent internal resistance of inductance and capacitance, the voltage conversion ratio of the conventional bidirectional three-phase DC-DC converter is limited, and it is difficult to increase the voltage conversion ratio by more than 4 times. Therefore, when a sufficiently large voltage conversion ratio is required, the circuit cannot meet the actual requirement; in addition, the voltage borne by each power switch tube of the conventional converter during turn-off is high-side voltage, and the voltage stress is large.
To improve the voltage conversion ratio of the DC-DC converter, there are three main solutions:
the first method is to use a transformer to realize voltage increase and reduction, and the energy conversion link is dc-ac-dc, but this scheme has a low energy conversion efficiency due to more conversion links.
The second is to use a switched capacitor technology to realize voltage step-up and step-down, but this scheme requires too many switching devices, which increases the cost and complicates the control.
The third is to use the coupled inductor technique to realize voltage step-up and step-down, but the leakage inductance of the coupled inductor will cause too large voltage spike and increase the loss.
In summary, the prior art is still lack of an effective solution to the problem that the DC-DC converter cannot meet the requirement of obtaining a sufficiently large voltage conversion ratio.
Disclosure of Invention
In order to solve the defects of the prior art, the invention provides a high-gain bidirectional three-phase DC-DC converter which is used for improving the voltage conversion ratio of the DC-DC converter.
A high gain bidirectional three phase DC-DC converter comprising:
three inductors L1、L2、L3: wherein, the inductance L1Respectively connected with a power switch tube S1And a power switch tube S4Connected, inductor L2Respectively connected with a power switch tube S2And a capacitor CfConnected, inductor L3Respectively connected with a power switch tube S3Capacitor CH1And a capacitor CH2Connecting;
low-voltage side, power switch tube S1、S2、S3Average power switch tube S6Connected, capacitor CfRespectively connected with a power switch tube S4And a power switch tube S5Connected, capacitor CH1Connected to the high-voltage side, a capacitor CH2Respectively connected with a power switch tube S6And the high-pressure side.
Further, an inductance L1Inductor L2And an inductance L3One end of the low-voltage side power supply V is connected with the low-voltage side power supply V simultaneouslyLIs connected to the positive pole of, or inductance L1Inductor L2And an inductance L3Is simultaneously connected with the load RLIs connected with the positive pole of the inductor L1The other end of the power switch tube S1First ofTerminal and S4Is connected to the second terminal of the inductor L2The other end of the power switch tube S2First terminal and capacitor CfIs connected with the negative electrode of the inductor L3The other end of the power switch tube S3First terminal of (1), capacitor CH1Negative electrode of (2) and capacitor CH2The positive electrodes of the two electrodes are connected;
further, a low-voltage side power supply VLNegative electrode of (1), power switch tube S1、S2、S3Second end of (S) and6is connected to a first terminal of, or a load RLNegative electrode of (1), power switch tube S1、S2、S3Second end of (S) and6is connected to a first terminal of a capacitor CfPositive pole and power switch tube S4First end of (1) and S5Is connected to the second terminal of the capacitor CH1Positive and high voltage side power supply VHPositive electrode or load R ofHIs connected to the positive pole of the capacitor CH2Negative pole of (2) and power switch tube S6Second terminal and high-voltage side power supply VHNegative electrode or load RHThe negative electrodes are connected; power switch tube S1~S6The third ends of the first and second driving circuits are respectively connected with the driving circuits;
further, a power switch tube S1~S6Respective first and second terminals are connected with diodes D in inverse parallel1~D6Are connected.
Further, the low-voltage side power supply VLOr a load RLTwo ends are connected in parallel with a filter capacitor CL
Further, the power switch tube S1~S6The respective third terminals are respectively connected with the respective driving circuits.
Further, the power switch tube S1~S6The power switch tube is an N-channel field effect transistor MOSFET or an insulated gate transistor IGBT, when the power switch tube is the N-channel field effect transistor MOSFET, the first end of the power switch tube is the drain electrode of the MOSFET, the second end of the power switch tube is the source electrode of the MOSFET, and the third end of the power switch tube is the grid electrode of the MOSFET;
when the power switch tube is an insulated gate transistor IGBT, the first end of the power switch tube is a collector electrode of the IGBT, the second end of the power switch tube is an emitter electrode of the IGBT, and the third end of the power switch tube is a grid electrode of the IGBT.
Further, when the DC-DC converter works in a boost mode, the low-voltage side is connected with a power supply, and the high-voltage side is connected with a load; when the DC-DC converter works in buck voltage reduction mode, the low-voltage side is connected with a load, and the high-voltage side is connected with a power supply.
Furthermore, the high-gain bidirectional three-phase DC-DC converter has the advantages that the high-voltage side filter capacitor can realize automatic voltage stabilization, and the three filter inductors can realize automatic current equalization. Further analysis was as follows: when the circuit works in a steady state, the power switch tube S1、S2、S3When the duty ratio is the same and equal to D, in a switching period, the inductance L1、L2、L3The charge and discharge volt-second balance respectively comprises:
VLDT=(VCf-VL)(1-D)T
VLDT=(VCH1-VCf-VL)(1-D)T
VLDT=(VCH2-VL)(1-D)T
the following can be obtained:
therefore, the high-side capacitor can automatically stabilize the voltage.
In one switching cycle, the capacitor Cf、CH1、CH2The charge and discharge ampere-second balance is as follows:
IL1(1-D)T=IL2(1-D)T
(IL2-IH)(1-D)T=IHDT
(IL3-IH)(1-D)T=IHDT
the following can be obtained:
IL1=IL2=IL3
therefore, the inductor current can be automatically equalized.
A control method for high-gain bidirectional three-phase DC-DC converter includes 180 deg. alternative control mode, power switch tube S1And S4、S2And S5、S3And S6Respectively, are complementarily turned on (no dead time is considered), and S1And S3Same phase, S1And S2The phase difference is 180 DEG, S1、S2、S3The duty cycle is the same and greater than 0.5.
Further, in the 180 ° interleaved control mode, when the converter operates in the boost mode, the voltage conversion ratio (i.e. gain, the same applies below) is:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty ratio of on-state, and 0.5<D<1. In a switching period, the converter has four working modes:
1) modes 1, 3[ t ]0-t1,t2-t3]: power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, low-voltage side supply VLTo the inductance L1、L2、L3Charging, inductor current iL1、iL2、iL3Linear increase, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2A linear decrease;
2) mode 2[ t ]1-t2]: power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, low-voltage side supply VLTo the inductance L1、L3Charging, inductor current iL1、iL3Linear increase, inductance L2To the capacitor Cf、CH1Charging, inductor current iL2Linear decrease, capacitor voltage vCfLinear decrease, capacitor voltage vCH1Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH2A linear decrease;
mode 4[ t ]3-t4]: power switch tube S2、S4、S6Conduction, S1、S3、S5Off, S1、S3、S5Is connected in parallel with the diode D1、D3、D5Cut-off, low-voltage side supply VLTo the inductance L2Charging, inductor current iL2Linear increase, inductance L1To the capacitor CfCharging, inductor current iL1Linear decrease, capacitor voltage vCfLinear increase, inductance L3To the capacitor CH2Charging, inductor current iL3Linear decrease, capacitor voltage vCH2Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1The linearity decreases.
Further, in the 180 ° staggered control mode, when the converter operates in buck mode, the voltage conversion ratio is:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty ratio of on-state, and 0.5<D<1. In a switching period, the circuit has four working modes:
1) mode 1, 3[ t ]0-t1,t2-t3]: power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, inductance L1、L2、L3For low-voltage side load RLCharging, inductor current iL1、iL2、iL3Linear reduction, capacitance Cf、CH1、CH2Without charging and discharging, capacitor voltage vCf、vCH1、vCH2The change is not changed;
2) mode 2[ t ]1-t2]: power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, inductance L1、L3For low-voltage side load RLCharging, inductor current iL1、iL3Linear reduction, capacitance Cf、CH1To the inductance L2Charging, inductor current iL2Linearly increasing, capacitor voltage vCfLinearly increasing, capacitor voltage vCH1Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH2Linear increase;
mode 4[ t ]3-t4]: power switch tube S2、S4、S6Conduction, S1、S3、S5Off, S1、S3、S5Is connected in parallel with the diode D1、D3、D5Cut-off, inductance L2For low-voltage side load RLCharging, inductor current iL2Linear reduction, capacitance CfTo the inductance L1Charging, inductor current iL1Linearly increasing, capacitor voltage vCfLinear reduction, capacitance CH2To the inductance L3Charging, inductor current iL3Linearly increasing, capacitor voltage vCH2Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH1The linearity increases.
High-gain bidirectional three-phase DC-DC converterThe control method comprises a 120-degree staggered control mode, and the power switch tube S1And S4、S2And S5、S3And S6Respectively, are complementarily turned on (no dead time is considered), and S1、S2And S3The phases differ by 120 DEG, S1、S2、S3The duty cycle is the same and greater than 2/3.
Further, in the 120 ° interleaved control mode, when the converter operates in the boost mode, the voltage conversion ratio is:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty cycle of on, and 2/3<D<1。
In a switching period, the converter has six working modes:
1) mode 1, 3, 5[ t ]0-t1,t2-t3,t4-t5]: power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, low-voltage side supply VLTo the inductance L1、L2、L3Charging, inductor current iL1、iL2、iL3Linear increase, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2A linear decrease;
2) mode 2[ t ]1-t2]: power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, low-voltage side supply VLTo the inductance L1、L3Charging, inductor current iL1、iL3Linear increase, inductance L2To the capacitor Cf、CH1Charging, inductor current iL2Linear decrease, capacitor voltage vCfLinear decrease, capacitor voltage vCH1Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH2A linear decrease;
3) mode 4[ t ]3-t4]: power switch tube S1、S2、S6Conduction, S3、S4、S5Off, S3、S4、S5Is connected in parallel with the diode D3、D4、D5Cut-off, low-voltage side supply VLTo the inductance L1、L2Charging, inductor current iL1、iL2Linear increase, inductance L3To the capacitor CH2Charging, inductor current iL3Linear decrease, capacitor voltage vCH2Linear increase, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1A linear decrease;
4) mode 6[ t ]5-t6]: power switch tube S2、S3、S4Conduction, S1、S5、S6Off, S1、S5、S6Is connected in parallel with the diode D1、D5、D6Cut-off, low-voltage side supply VLTo the inductance L2、L3Charging, inductor current iL2、iL3Linear increase, inductance L1To the capacitor CfCharging, inductor current iL3Linear decrease, capacitor voltage vCfLinear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2The linearity decreases.
Furthermore, under the 120-degree staggered control mode, when the converter works in buck mode, the voltage of the converter is convertedThe conversion ratio is as follows:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty cycle of on, and 2/3<D<1. In a switching period, the converter has six working modes:
1) mode 1, 3, 5[ t ]0-t1,t2-t3,t4-t5]: power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, inductance L1、L2、L3For low-voltage side load RLCharging, inductor current iL1、iL2、iL3Linear reduction, capacitance Cf、CH1、CH2Without charging and discharging, capacitor voltage vCf、vCH1、vCH2The change is not changed;
2) mode 2[ t ]1-t2]: power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, inductance L1、L3For low-voltage side load RLCharging, inductor current iL1、iL3Linear reduction, capacitance Cf、CH1To the inductance L2Charging, inductor current iL2Linearly increasing, capacitor voltage vCfLinearly increasing, capacitor voltage vCH1Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH2Linear increase;
3) mode 4[ t ]3-t4]: power switch tube S1、S2、S6Conduction, S3、S4、S5The power is turned off and the power is turned off,S3、S4、S5is connected in parallel with the diode D3、D4、D5Cut-off, inductance L1、L2For low-voltage side load RLCharging, inductor current iL1、iL2Linear reduction, capacitance CH2To the inductance L3Charging, inductor current iL3Linearly increasing, capacitor voltage vCH2Linear reduction, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, high-voltage side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH1Linear increase;
4) mode 6[ t ]5-t6]: power switch tube S2、S3、S4Conduction, S1、S5、S6Off, S1、S5、S6Is connected in parallel with the diode D1、D5、D6Cut-off, inductance L2、L3For low-voltage side load RLCharging, inductor current iL2、iL3Linear reduction, capacitance CfTo the inductance L1Charging, inductor current iL1Linearly increasing, capacitor voltage vCfLinear reduction, capacitance CH1、CH2Without charging and discharging, capacitor voltage vCH1、vCH2And is not changed.
Compared with the prior art, the invention has the beneficial effects that:
the invention has higher voltage conversion ratio which can be increased to three times of that of the traditional bidirectional three-phase DC-DC converter; the power switch tube has lower voltage stress, wherein the power switch tube S1、S2、S3、S6The voltage born when the power switch is turned off is one third of the voltage of the high-voltage side, and the power switch tube S4、S5The voltage sustained during turn-off of (a) is two thirds of the voltage on the high-voltage side.
According to the invention, two high-voltage side filter capacitors can realize automatic voltage stabilization, and three filter inductors can realize automatic current sharing.
High-voltage side filter capacitor CH1Voltage of at is VH2/3, high-side filter capacitor CH2Voltage of at is VH1/3 of (1).
The invention only adds two capacitors, has simple circuit topology and few circuit elements, reduces the cost of the converter and improves the overall working efficiency of the converter.
The converter is simple to control and easy to realize. The 180-degree staggered control mode can increase the duty ratio range to the maximum extent and reduce the total voltage ripple at the high-voltage side; the total current ripple on the low-voltage side can be reduced to the maximum extent by the 120-degree staggered control mode.
Drawings
The accompanying drawings, which are incorporated in and constitute a part of this application, illustrate embodiments of the application and, together with the description, serve to explain the application and are not intended to limit the application.
FIG. 1 is a circuit topology of a conventional bidirectional three-phase DC-DC converter;
FIG. 2 is a circuit topology of a high-gain bidirectional three-phase DC-DC converter according to the present invention;
fig. 3 is a control signal of each power switching tube of the high-gain bidirectional three-phase DC-DC converter provided by the present invention under a 180 ° staggered control mode;
fig. 4 shows control signals of power switching tubes of the high-gain bidirectional three-phase DC-DC converter in a 120 ° staggered control manner;
fig. 5(a) -5 (c) are operation modes of the high-gain bidirectional three-phase DC-DC converter provided by the present invention when the converter operates in a boost mode under a 180 ° staggered control mode;
6(a) -6 (c) are operation modes of the high-gain bidirectional three-phase DC-DC converter in the buck mode under the 180 ° staggered control mode;
fig. 7(a) -7 (d) are operation modes of the high-gain bidirectional three-phase DC-DC converter provided by the present invention when the converter operates in a boost mode under a 120 ° staggered control mode;
8(a) -8 (d) are operation modes of the high-gain bidirectional three-phase DC-DC converter in buck mode under 120 ° staggered control mode;
fig. 9(a) -9 (c) are simulation waveforms of the high-gain bidirectional three-phase DC-DC converter operating in the boost mode under the 180 ° staggered control mode;
fig. 10(a) -10 (c) are simulation waveforms of the high-gain bidirectional three-phase DC-DC converter operating in buck mode under the 180 ° staggered control mode.
Detailed Description
It should be noted that the following detailed description is exemplary and is intended to provide further explanation of the disclosure. Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this application belongs.
It is noted that the terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of example embodiments according to the present application. As used herein, the singular forms "a", "an" and "the" are intended to include the plural forms as well, and it should be understood that when the terms "comprises" and/or "comprising" are used in this specification, they specify the presence of stated features, steps, operations, devices, components, and/or combinations thereof, unless the context clearly indicates otherwise.
As described in the background of the invention, there is a XXX deficiency in the prior art, and in order to solve the above technical problems, the present application provides a high-gain bidirectional three-phase DC-DC converter and a control method thereof.
In an exemplary embodiment of the present application, a high-gain bidirectional three-phase DC-DC converter is provided, and the embodiment of the present invention adopts a topology shown in fig. 2, which includes three inductors L1~L3Six power switch tubes S1~S6Four capacitors Cf、CL、CH1、CH2The circuit connection relationship is as follows:
inductor L1Inductor L2And an inductance L3One end of the low-voltage side power supply V is connected with the low-voltage side power supply V simultaneouslyLIs connected to the positive pole of, or inductance L1Inductor L2And an inductance L3One end of (A)Simultaneously with the load RLIs connected with the positive pole of the inductor L1The other end of the power switch tube S1First end of (1) and S4Is connected to the second terminal of the inductor L2The other end of the power switch tube S2First terminal and capacitor CfIs connected with the negative electrode of the inductor L3The other end of the power switch tube S3First terminal of (1), capacitor CH1Negative electrode of (2) and capacitor CH2The positive electrodes of the two electrodes are connected;
low voltage side power supply VLNegative electrode of (1), power switch tube S1、S2、S3Second end of (S) and6is connected to a first terminal of, or a load RLNegative electrode of (1), power switch tube S1、S2、S3Second end of (S) and6is connected to a first terminal of a capacitor CfPositive pole and power switch tube S4First end of (1) and S5Is connected to the second terminal of the capacitor CH1Positive and high voltage side power supply VHPositive electrode or load R ofHIs connected to the positive pole of the capacitor CH2Negative pole of (2) and power switch tube S6Second terminal and high-voltage side power supply VHNegative electrode or load RHThe negative electrodes are connected; power switch tube S1~S6The third ends of the first and second driving circuits are respectively connected with the driving circuits;
power switch tube S1~S6Respective first and second terminals are connected with diodes D in inverse parallel1~D6Are connected.
Power switch tube S1~S6The respective third terminals are respectively connected with the respective driving circuits. The preferred embodiment adopts an N-channel field effect transistor MOSFET as the power switch tube, the first terminal of the power switch tube is the drain of the MOSFET, the second terminal of the power switch tube is the source of the MOSFET, and the third terminal of the power switch tube is the gate of the MOSFET.
In another exemplary embodiment of the present application, the power switch tube is an insulated gate bipolar transistor IGBT, a first end of the power switch tube is a collector of the IGBT, a second end of the power switch tube is an emitter of the IGBT, and a third end of the power switch tube is a gate of the IGBT.
The preferred embodiment verifies the bi-directional operating characteristics of the converter by changing the connections of the low and high voltage sides to the power source or load. When the converter works in a boost mode, a mode that a low-voltage side is connected with a power supply and a high-voltage side is connected with a load is adopted; when the buck voltage reducing circuit works in the buck voltage reducing mode, a mode that a low-voltage side is connected with a load and a high-voltage side is connected with a power supply is adopted. The load anode is one end of the load connected with the anode of the filter capacitor, and the load cathode is one end of the load connected with the cathode of the filter capacitor.
When the converter adopts a 180-degree staggered control mode, the conduction condition of the power switch tube is as shown in figure 3, and the power switch tube S1And S4、S2And S5、S3And S6Respectively, are complementarily turned on (no dead time is considered), and S1And S3Same phase, S1And S2The phase difference is 180 DEG, S1、S2、S3The duty cycle is the same and greater than 0.5.
Under the 180 DEG staggered control mode, when the converter works in the boost mode, the voltage conversion ratio is as follows:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty ratio of on-state, and 0.5<D<1, in a switching period, the circuit has four working modes:
3) modes 1, 3[ t ]0-t1,t2-t3]: as shown in fig. 5(a), the power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, low-voltage side supply VLTo the inductance L1、L2、L3Charging, inductor current iL1、iL2、iL3LinearityIncrease the capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2The linearity decreases.
4) Mode 2[ t ]1-t2]: as shown in fig. 5(b), the power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, low-voltage side supply VLTo the inductance L1、L3Charging, inductor current iL1、iL3Linear increase, inductance L2To the capacitor Cf、CH1Charging, inductor current iL2Linear decrease, capacitor voltage vCfLinear decrease, capacitor voltage vCH1Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH2The linearity decreases.
5) Mode 4[ t ]3-t4]: as shown in fig. 5(c), the power switch tube S2、S4、S6Conduction, S1、S3、S5Off, S1、S3、S5Is connected in parallel with the diode D1、D3、D5Cut-off, low-voltage side supply VLTo the inductance L2Charging, inductor current iL2Linear increase, inductance L1To the capacitor CfCharging, inductor current iL1Linear decrease, capacitor voltage vCfLinear increase, inductance L3To the capacitor CH2Charging, inductor current iL3Linear decrease, capacitor voltage vCH2Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1The linearity decreases.
Under the 180-degree staggered control mode, when the converter works in buck mode, the voltage conversion ratio is as follows:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty ratio of on-state, and 0.5<D<1, in a switching period, the circuit has four working modes:
3) mode 1, 3[ t ]0-t1,t2-t3]: as shown in fig. 6(a), the power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, inductance L1、L2、L3For low-voltage side load RLCharging, inductor current iL1、iL2、iL3Linear reduction, capacitance Cf、CH1、CH2Without charging and discharging, capacitor voltage vCf、vCH1、vCH2And is not changed.
4) Mode 2[ t ]1-t2]: as shown in fig. 6(b), the power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, inductance L1、L3For low-voltage side load RLCharging, inductor current iL1、iL3Linear reduction, capacitance Cf、CH1To the inductance L2Charging, inductor current iL2Linearly increasing, capacitor voltage vCfLinearly increasing, capacitor voltage vCH1Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH2The linearity increases.
5) Mode 4[ t ]3-t4]: as shown in fig. 6(c), the power switch tube S2、S4、S6Conduction, S1、S3、S5Off, S1、S3、S5Is connected in parallel with the diode D1、D3、D5Cut-off, inductance L2For low-voltage side load RLCharging, inductor current iL2Linear reduction, capacitance CfTo the inductance L1Charging, inductor current iL1Linearly increasing, capacitor voltage vCfLinear reduction, capacitance CH2To the inductance L3Charging, inductor current iL3Linearly increasing, capacitor voltage vCH2Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH1The linearity increases.
When the converter adopts a 120-degree staggered control mode, the conduction condition of the power switch tube is shown in figure 4, and the power switch tube S1And S4、S2And S5、S3And S6Respectively, are complementarily turned on (no dead time is considered), and S1、S2And S3The phases differ by 120 DEG, S1、S2、S3The duty cycle is the same and greater than 2/3.
Under the 120-degree staggered control mode, when the converter works in the boost mode, the voltage conversion ratio is as follows:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty cycle of on, and 2/3<D<1, in a switching period, the circuit has six working modes:
5) mode 1, 3, 5[ t ]0-t1,t2-t3,t4-t5]: as shown in fig. 7(a), the power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, low-voltage side supply VLTo the inductance L1、L2、L3Charging, inductor current iL1、iL2、iL3Linear increase, electricityContainer CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2The linearity decreases.
6) Mode 2[ t ]1-t2]: as shown in fig. 7(b), the power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, low-voltage side supply VLTo the inductance L1、L3Charging, inductor current iL1、iL3Linear increase, inductance L2To the capacitor Cf、CH1Charging, inductor current iL2Linear decrease, capacitor voltage vCfLinear decrease, capacitor voltage vCH1Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH2The linearity decreases.
7) Mode 4[ t ]3-t4]: as shown in fig. 7(c), the power switch tube S1、S2、S6Conduction, S3、S4、S5Off, S3、S4、S5Is connected in parallel with the diode D3、D4、D5Cut-off, low-voltage side supply VLTo the inductance L1、L2Charging, inductor current iL1、iL2Linear increase, inductance L3To the capacitor CH2Charging, inductor current iL3Linear decrease, capacitor voltage vCH2Linear increase, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1The linearity decreases.
8) Mode 6[ t ]5-t6]: as shown in fig. 7(d), the power switch tube S2、S3、S4Conduction, S1、S5、S6Off, S1、S5、S6Is connected in parallel with the diode D1、D5、D6Cut-off, low-voltage side supply VLTo the inductance L2、L3Charging, inductor current iL2、iL3Linear increase, inductance L1To the capacitor CfCharging, inductor current iL3Linear decrease, capacitor voltage vCfLinear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2The linearity decreases.
Under the 120-degree staggered control mode, when the converter works in buck mode, the voltage conversion ratio is as follows:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty cycle of on, and 2/3<D<1, in a switching period, the circuit has six working modes:
5) mode 1, 3, 5[ t ]0-t1,t2-t3,t4-t5]: as shown in fig. 8(a), the power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, inductance L1、L2、L3For low-voltage side load RLCharging, inductor current iL1、iL2、iL3Linear reduction, capacitance Cf、CH1、CH2Without charging and discharging, capacitor voltage vCf、vCH1、vCH2And is not changed.
6) Mode 2[ t ]1-t2]: as shown in fig. 8(b), the power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-offInductance L1、L3For low-voltage side load RLCharging, inductor current iL1、iL3Linear reduction, capacitance Cf、CH1To the inductance L2Charging, inductor current iL2Linearly increasing, capacitor voltage vCfLinearly increasing, capacitor voltage vCH1Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH2The linearity increases.
7) Mode 4[ t ]3-t4]: as shown in fig. 8(c), the power switch tube S1、S2、S6Conduction, S3、S4、S5Off, S3、S4、S5Is connected in parallel with the diode D3、D4、D5Cut-off, inductance L1、L2For low-voltage side load RLCharging, inductor current iL1、iL2Linear reduction, capacitance CH2To the inductance L3Charging, inductor current iL3Linearly increasing, capacitor voltage vCH2Linear reduction, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, high-voltage side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH1The linearity increases.
8) Mode 6[ t ]5-t6]: power switch tube S as shown in FIG. 8(d)2、S3、S4Conduction, S1、S5、S6Off, S1、S5、S6Is connected in parallel with the diode D1、D5、D6Cut-off, inductance L2、L3For low-voltage side load RLCharging, inductor current iL2、iL3Linear reduction, capacitance CfTo the inductance L1Charging, inductor current iL1Linearly increasing, capacitor voltage vCfLinear reduction, capacitance CH1、CH2Without charging and discharging, capacitor voltage vCH1、vCH2And is not changed.
The two control methods are optimized control methods, and the control method obtained by adjusting the conduction sequence of the power switch tube and the simple phase shift of the conduction time of the power switch tube is still protected by the invention.
Fig. 9(a) -9 (c) and fig. 10(a) -10 (c) are simulated waveform diagrams of the converter according to the present invention under a 180 ° staggered control mode. Wherein (a), (b) and (c) of fig. 9 are waveforms of drain-source voltage, input-output voltage and inductance current of each phase of each power switch when the converter operates in boost mode, respectively; fig. 10(a), (b), and (c) show the drain-source voltage, input-output voltage, and inductor current waveform of each phase of the power switch when the converter operates in buck mode. The 120 ° interleaving control method is similar to the 180 ° interleaving control method, and is not described herein again.
The simulation parameters are as follows: inductor L1、L2、L3Respectively 1.0mH, 1.1mH and 1.2mH, the internal resistances of three inductors are all 0.05 omega, and a capacitor CL、Cf、CH1、CH21000 muF, 100 muF, 1000 muF and 1000 muF respectively, the equivalent internal resistance of four capacitors is 0.05 omega, and the power switch tube S1And S4、S2And S5、S3And S6Respectively, are complementarily turned on (no dead time is considered), and S1And S3Same phase, S1And S2The phase difference is 180 DEG, S1、S2、S3The duty cycle is the same and equal to 0.7 and the switching frequency is 50 kHz. When the converter works in boost mode, the low-voltage side power supply VLVoltage 20V, high-voltage side load RHThe resistance is 500; when the converter works in buck mode, the low-voltage side load RLResistance of 5 omega, high-voltage side power supply VHThe voltage was 200V.
Analysis and simulation of the preferred embodiment show that the high-gain bidirectional three-phase DC-DC converter has a three-time voltage conversion ratio compared with a common bidirectional three-phase DC-DC converter, and the power switch tube has the functions of lower voltage stress and automatic current sharing of inductive current.
The above description is only a preferred embodiment of the present application and is not intended to limit the present application, and various modifications and changes may be made by those skilled in the art. Any modification, equivalent replacement, improvement and the like made within the spirit and principle of the present application shall be included in the protection scope of the present application.

Claims (9)

1. A high-gain bidirectional three-phase DC-DC converter is characterized by an inductor L1Inductor L2And an inductance L3One end of the low-voltage side power supply V is connected with the low-voltage side power supply V simultaneouslyLIs connected to the positive pole of, or inductance L1Inductor L2And an inductance L3Is simultaneously connected with the load RLIs connected with the positive pole of the inductor L1The other end of the power switch tube S1First end of (1) and S4Is connected to the second terminal of the inductor L2The other end of the power switch tube S2First terminal and capacitor CfIs connected with the negative electrode of the inductor L3The other end of the power switch tube S3First terminal of (1), capacitor CH1Negative electrode of (2) and capacitor CH2The positive electrodes of the two electrodes are connected;
low voltage side power supply VLNegative electrode of (1), power switch tube S1、S2、S3Second end of (S) and6is connected to a first terminal of, or a load RLNegative electrode of (1), power switch tube S1、S2、S3Second end of (S) and6is connected to a first terminal of a capacitor CfPositive pole and power switch tube S4First end of (1) and S5Is connected to the second terminal of the capacitor CH1Positive and high voltage side power supply VHPositive electrode or load R ofHIs connected to the positive pole of the capacitor CH2Negative pole of (2) and power switch tube S6Second terminal and high-voltage side power supply VHNegative electrode or load RHThe negative electrodes are connected; power switch tube S1~S6The third ends of the first and second driving circuits are respectively connected with the driving circuits;
power switch tube S1~S6Respective first and second terminals are connected with diodes D in inverse parallel1~D6Are connected.
2. A high gain twin as defined in claim 1To a three-phase DC-DC converter, characterized in that the low-voltage side power supply VLOr a load RLTwo ends are connected in parallel with a filter capacitor CL
3. A high gain bidirectional three phase DC-DC converter as claimed in claim 1, wherein said power switch S1~S6Is an N-channel field effect transistor MOSFET or an insulated gate transistor IGBT;
when the power switch tube is an N-channel field effect transistor MOSFET, the first end of the power switch tube is the drain electrode of the MOSFET, the second end of the power switch tube is the source electrode of the MOSFET, and the third end of the power switch tube is the grid electrode of the MOSFET;
when the power switch tube is an insulated gate transistor IGBT, the first end of the power switch tube is a collector electrode of the IGBT, the second end of the power switch tube is an emitter electrode of the IGBT, and the third end of the power switch tube is a grid electrode of the IGBT.
4. The method as claimed in claim 1, wherein the method includes a 180 ° staggered control mode, and the power switch S is a power switch1And S4、S2And S5、S3And S6Respectively in complementary conduction without taking dead time into account, and S1And S3Same phase, S1And S2The phase difference is 180 DEG, S1、S2、S3The duty cycle is the same and greater than 0.5.
5. The method as claimed in claim 4, wherein in the 180 ° interleaved control mode, the converter operates in boost mode with a voltage conversion ratio of:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty ratio of on-state, and 0.5<D<1, a switchIn the period, the converter has four working modes:
modes 1, 3[ t ]0-t1,t2-t3]: power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, low-voltage side supply VLTo the inductance L1、L2、L3Charging, inductor current iL1、iL2、iL3Linear increase, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2A linear decrease;
mode 2[ t ]1-t2]: power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, low-voltage side supply VLTo the inductance L1、L3Charging, inductor current iL1、iL3Linear increase, inductance L2To the capacitor Cf、CH1Charging, inductor current iL2Linear decrease, capacitor voltage vCfLinear decrease, capacitor voltage vCH1Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH2A linear decrease;
mode 4[ t ]3-t4]: power switch tube S2、S4、S6Conduction, S1、S3、S5Off, S1、S3、S5Is connected in parallel with the diode D1、D3、D5Cut-off, low-voltage side supply VLTo the inductance L2Charging, inductor current iL2Linear increase, inductance L1To the capacitor CfCharging, inductor current iL1The linear decrease is carried out and the linear decrease,capacitor voltage vCfLinear increase, inductance L3To the capacitor CH2Charging, inductor current iL3Linear decrease, capacitor voltage vCH2Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1The linearity decreases.
6. The method as claimed in claim 4, wherein in the 180 ° interleaved control mode, when the converter operates in buck mode, the voltage conversion ratio is:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty ratio of on-state, and 0.5<D<1, in a switching period, the circuit has four working modes:
mode 1, 3[ t ]0-t1,t2-t3]: power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, inductance L1、L2、L3For low-voltage side load RLCharging, inductor current iL1、iL2、iL3Linear reduction, capacitance Cf、CH1、CH2Without charging and discharging, capacitor voltage vCf、vCH1、vCH2The change is not changed;
mode 2[ t ]1-t2]: power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, inductance L1、L3For low-voltage side load RLCharging, inductor current iL1、iL3Linear reduction, capacitance Cf、CH1To the inductance L2Charging, inductor current iL2Linearly increasing, capacitor voltage vCfLinearly increasing, capacitor voltage vCH1Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH2Linear increase;
mode 4[ t ]3-t4]: power switch tube S2、S4、S6Conduction, S1、S3、S5Off, S1、S3、S5Is connected in parallel with the diode D1、D3、D5Cut-off, inductance L2For low-voltage side load RLCharging, inductor current iL2Linear reduction, capacitance CfTo the inductance L1Charging, inductor current iL1Linearly increasing, capacitor voltage vCfLinear reduction, capacitance CH2To the inductance L3Charging, inductor current iL3Linearly increasing, capacitor voltage vCH2Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH1The linearity increases.
7. The method as claimed in claim 1, wherein the method includes a 120 ° staggered control mode, and the power switch S is a power switch1And S4、S2And S5、S3And S6Respectively in complementary conduction without taking dead time into account, and S1、S2And S3The phases differ by 120 DEG, S1、S2、S3The duty cycle is the same and greater than 2/3.
8. The method as claimed in claim 7, wherein in the 120 ° interleaved control mode, the converter operates in boost mode with a voltage conversion ratio of:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty cycle of on, and 2/3<D<1, in a switching period, the converter has six working modes:
mode 1, 3, 5[ t ]0-t1,t2-t3,t4-t5]: power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, low-voltage side supply VLTo the inductance L1、L2、L3Charging, inductor current iL1、iL2、iL3Linear increase, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2A linear decrease;
mode 2[ t ]1-t2]: power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, low-voltage side supply VLTo the inductance L1、L3Charging, inductor current iL1、iL3Linear increase, inductance L2To the capacitor Cf、CH1Charging, inductor current iL2Linear decrease, capacitor voltage vCfLinear decrease, capacitor voltage vCH1Linear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH2A linear decrease;
mode 4[ t ]3-t4]: power switch tube S1、S2、S6Conduction, S3、S4、S5Off, S3、S4、S5Is connected in parallel with the diode D3、D4、D5Cut-off, low-voltage side supply VLTo the inductance L1、L2Charging, inductor current iL1、iL2Linear increase, inductance L3To the capacitor CH2Charging, inductor current iL3Linear decrease, capacitor voltage vCH2Linear increase, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1A linear decrease;
mode 6[ t ]5-t6]: power switch tube S2、S3、S4Conduction, S1、S5、S6Off, S1、S5、S6Is connected in parallel with the diode D1、D5、D6Cut-off, low-voltage side supply VLTo the inductance L2、L3Charging, inductor current iL2、iL3Linear increase, inductance L1To the capacitor CfCharging, inductor current iL3Linear decrease, capacitor voltage vCfLinear increase, capacitance CH1、CH2Common pair of high-voltage side loads RHCharging, capacitor voltage vCH1、vCH2The linearity decreases.
9. The method as claimed in claim 7, wherein in the 120 ° interleaved control mode, when the converter operates in buck mode, the voltage conversion ratio is:in the formula VHIs a high side DC voltage, VLIs a low-voltage side DC voltage, D is a power switch tube S1、S3、S5Duty cycle of on, and 2/3<D<1, in a switching period, the converter has six working modes:
mode 1, 3, 5[ t ]0-t1,t2-t3,t4-t5]: power switch tube S1、S2、S3Conduction, S4、S5、S6Off, S4、S5、S6Is connected in parallel with the diode D4、D5、D6Cut-off, inductance L1、L2、L3For low-voltage side load RLCharging, inductor current iL1、iL2、iL3Linear reduction, capacitance Cf、CH1、CH2Without charging and discharging, capacitor voltage vCf、vCH1、vCH2The change is not changed;
mode 2[ t ]1-t2]: power switch tube S1、S3、S5Conduction, S2、S4、S6Off, S2、S4、S6Is connected in parallel with the diode D2、D4、D6Cut-off, inductance L1、L3For low-voltage side load RLCharging, inductor current iL1、iL3Linear reduction, capacitance Cf、CH1To the inductance L2Charging, inductor current iL2Linearly increasing, capacitor voltage vCfLinearly increasing, capacitor voltage vCH1Linear reduced, high side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH2Linear increase;
mode 4[ t ]3-t4]: power switch tube S1、S2、S6Conduction, S3、S4、S5Off, S3、S4、S5Is connected in parallel with the diode D3、D4、D5Cut-off, inductance L1、L2For low-voltage side load RLCharging, inductor current iL1、iL2Linear reduction, capacitance CH2To the inductance L3Charging, inductor current iL3Linearly increasing, capacitor voltage vCH2Linear reduction, capacitance CfWithout charging and discharging, capacitor voltage vCfConstant, high-voltage side supply VHTo the capacitor CH1、CH2Charging, capacitor voltage vCH1Linear increase;
mode 6[ t ]5-t6]: power switch tube S2、S3、S4Conduction, S1、S5、S6Off, S1、S5、S6Is connected in parallel with the diode D1、D5、D6Cut-off, inductance L2、L3For low-voltage side load RLCharging, inductor current iL2、iL3Linear reduction, capacitance CfTo the inductance L1Charging, inductor current iL1Linearly increasing, capacitor voltage vCfLinear reduction, capacitance CH1、CH2Without charging and discharging, capacitor voltage vCH1、vCH2And is not changed.
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CN110729899B (en) * 2019-11-01 2020-08-04 山东大学 Wide-input wide-output three-phase high-gain direct current converter and control method
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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104218798A (en) * 2014-09-18 2014-12-17 天津大学 High voltage gain bidirectional DC-DC (direct current-direct current) converter based on switching capacitors and coupling inductors
CN204633600U (en) * 2015-05-18 2015-09-09 安徽理工大学 A kind of novel crisscross parallel topology structure of stepping-up/stepping-down chopper circuit
CN106329914A (en) * 2015-06-15 2017-01-11 伊顿公司 Interleaved parallel DC-DC converter and control method thereof
CN106533173A (en) * 2016-12-29 2017-03-22 三峡大学 High-gain DC/DC converter with adjustable input phase number

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7932633B2 (en) * 2008-10-22 2011-04-26 General Electric Company Apparatus for transferring energy using power electronics and machine inductance and method of manufacturing same
TWI495242B (en) * 2013-10-09 2015-08-01 Nat Univ Tsing Hua Bidirectional dc-dc converter

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104218798A (en) * 2014-09-18 2014-12-17 天津大学 High voltage gain bidirectional DC-DC (direct current-direct current) converter based on switching capacitors and coupling inductors
CN204633600U (en) * 2015-05-18 2015-09-09 安徽理工大学 A kind of novel crisscross parallel topology structure of stepping-up/stepping-down chopper circuit
CN106329914A (en) * 2015-06-15 2017-01-11 伊顿公司 Interleaved parallel DC-DC converter and control method thereof
CN106533173A (en) * 2016-12-29 2017-03-22 三峡大学 High-gain DC/DC converter with adjustable input phase number

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