CN109239671A - A kind of double frequency continuous wave Doppler radar circuit structure inhibiting direct current biasing - Google Patents

A kind of double frequency continuous wave Doppler radar circuit structure inhibiting direct current biasing Download PDF

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Publication number
CN109239671A
CN109239671A CN201811093886.3A CN201811093886A CN109239671A CN 109239671 A CN109239671 A CN 109239671A CN 201811093886 A CN201811093886 A CN 201811093886A CN 109239671 A CN109239671 A CN 109239671A
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power
way
signal
frequency
analog
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马建国
杨自凯
周绍华
杨闯
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Tianjin University
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Tianjin University
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Priority to CN201811093886.3A priority Critical patent/CN109239671A/en
Priority to LU101013A priority patent/LU101013B1/en
Publication of CN109239671A publication Critical patent/CN109239671A/en
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/06—Systems determining position data of a target
    • G01S13/08—Systems for measuring distance only
    • G01S13/32—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated
    • G01S13/34—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated using transmission of continuous, frequency-modulated waves while heterodyning the received signal, or a signal derived therefrom, with a locally-generated signal related to the contemporaneously transmitted signal
    • G01S13/347—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated using transmission of continuous, frequency-modulated waves while heterodyning the received signal, or a signal derived therefrom, with a locally-generated signal related to the contemporaneously transmitted signal using more than one modulation frequency
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/50—Systems of measurement based on relative movement of target
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/88—Radar or analogous systems specially adapted for specific applications
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/023—Interference mitigation, e.g. reducing or avoiding non-intentional interference with other HF-transmitters, base station transmitters for mobile communication or other radar systems, e.g. using electro-magnetic interference [EMI] reduction techniques
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/03—Details of HF subsystems specially adapted therefor, e.g. common to transmitter and receiver
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/35—Details of non-pulse systems
    • G01S7/352—Receivers
    • G01S7/354—Extracting wanted echo-signals
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/36—Means for anti-jamming, e.g. ECCM, i.e. electronic counter-counter measures
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/41—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00 using analysis of echo signal for target characterisation; Target signature; Target cross-section
    • G01S7/415—Identification of targets based on measurements of movement associated with the target
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/03—Details of HF subsystems specially adapted therefor, e.g. common to transmitter and receiver
    • G01S7/034—Duplexers

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  • Engineering & Computer Science (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Physics & Mathematics (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • General Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Radar Systems Or Details Thereof (AREA)

Abstract

The invention discloses a kind of double frequency continuous wave Doppler radar circuit structures for inhibiting direct current biasing, receiving antenna connects No. four power splitters, No. four power splitter output ends are connected No.1 bandpass filter, No.1 low-noise amplifier, No.1 frequency mixer, No. five bandpass filters and No.1 analog-digital converter all the way, No. two bandpass filters of another way series connection, No. two low-noise amplifiers, No. two frequency mixers, No. six bandpass filters and No. two analog-digital converters, No.1 analog-digital converter and No. two analog-digital converters are all connected with field programmable gate array；Transmitting antenna Series power amplifier, No. two power splitters, No. two connections of power splitter input terminal, No. three power splitters；No.1 power splitter connects No.1 local oscillator, and output end connects No. two power splitters all the way, and another way connects No.1 frequency mixer through No. three bandpass filters；No. three power splitters connect No. two local oscillators, and output end connects No. two power splitters all the way, and another way connects No. two frequency mixers through No. four bandpass filters.

Description

A kind of double frequency continuous wave Doppler radar circuit structure inhibiting direct current biasing
Technical field
The present invention relates to dual frequency doppler radar circuit fields, and more specifically, it relates to a kind of inhibition direct current biasings Double frequency continuous wave Doppler radar circuit structure.
Background technique
Continuous wave Doppler radar is a kind of main radar arrangement for realizing vital signs detecting.In continuous wave Doppler thunder Up in numerous receiver structures, zero-if architecture is a kind of most common receiver structure, and there is no image frequencies to do for the structure The problem of disturbing, it is no longer necessary to image-reject filter, therefore simplify the structure of radar, but the local frequency of the structure and penetrate The frequency of frequency signal is equal, thus can have DC offset problem after being mixed in receivers, this can seriously affect signal demodulation As a result precision, or even will limit the structure in the application in high-precision field.
For the DC offset problem of zero intermediate frequency reciver structure, it is thus proposed that digital low intermediate frequency receiver structure [1], Lesser local oscillation signal input mixer is differed with emission signal frequency using one and is mixed with signal is received, and mixing generates Low intermediate frequency signal sampled again by analog-digital converter, finally carry out second mixing in numeric field and generate baseband signal.At this In structure, need to generate the signal of two different frequencies, one is used as transmitting signal, another is used as local oscillation signal, this Signal source is wasted to a certain extent.
Based on existing digital low intermediate frequency receiver structure, it is necessary to a kind of novel receiver structure is proposed, to improve letter The utilization rate in number source.
[bibliography]
[1]Wu Y,Li J.The design of digital radar receivers[J].IEEE Aerospace& Electronic Systems Magazine,1998,13(1):35-41.
Summary of the invention
Purpose of the invention is to overcome the shortcomings in the prior art, and it is continuous to provide a kind of double frequency for inhibiting direct current biasing Wave Doppler radar circuit structure, improves the utilization rate of signal source, and the signal source of two kinds of different frequencies is enabled to be used as transmitting letter Number, and it is used as local oscillation signal mutually to realize digital low intermediate frequency receiver structure；The precision for improving vital signs detecting, due to The signal of two frequencies is used as transmitting signal, therefore the signal of two frequencies can detect vital sign parameter signals.
The purpose of the present invention is what is be achieved through the following technical solutions.
The double frequency continuous wave Doppler radar circuit structure of inhibition direct current biasing of the invention, including receiving antenna and transmitting Antenna, the receiving antenna are connected with No. four power splitters, and No. four power splitter output ends are divided into two-way, wherein successively going here and there all the way It is associated with No.1 bandpass filter, No.1 low-noise amplifier, No.1 frequency mixer, No. five bandpass filters and No.1 analog-to-digital conversion Device, another way have been sequentially connected in series No. two bandpass filters, No. two low-noise amplifiers, No. two frequency mixers, No. six bandpass filters With No. two analog-digital converters, the No.1 analog-digital converter and No. two analog-digital converters are all connected with field programmable gate array；
The transmitting antenna connects power amplifier, and the power amplifier input is connected with No. two power splitters, institute It states No. two power splitter input terminals and is divided into two-way, wherein being connected with No.1 power splitter all the way, another way is connected with No. three power splitters；Institute It states No.1 power splitter input terminal and is connected with No.1 local oscillator, output end is divided into two-way, wherein No. two power splitter input terminals are connected all the way, Another way is connected to No.1 mixer input through No. three bandpass filters；No. three power splitter input terminals are connected with No. two sheets Vibration, output end are divided into two-way, wherein connecting No. two power splitter input terminals all the way, another way is connected to two through No. four bandpass filters Number mixer input.
In transmitting terminal, the frequency that No.1 local oscillator and No. two local oscillators generate is respectively 1.67GHz and 2.06GHz, two frequencies Signal pass through No.1 power splitter respectively and No. three power splitters are divided into two-way, be both used as transmitting signal all the way, in addition use all the way Make local oscillation signal；Two transmitting signals are synthesized using No. two power splitters, pass through transmitting day after power amplifier (PA) amplification Line is launched；
In receiving end, the signal received first passes through No. four power splitters and divides the signal into two-way, then receives signal difference By No. two bandpass filters of No.1 bandpass filter and 1.67GHz that centre frequency is 2.06GHz, two-way receives letter later Number respectively through No.1 low-noise amplifier and No. two low-noise amplifiers amplifications, the local oscillator for being respectively 1.67GHz with centre frequency The local oscillation signal that signal and centre frequency are 2.06GHz is mixed；Obtained low intermediate frequency signal is mixed first respectively by No. five Bandpass filter and No. six band-pass filters, then respectively through No.1 analog-digital converter and No. two analog-digital converter sample conversions At digital signal, low intermediate frequency signal carries out second of orthogonal mixing in programmable gate array numeric field at the scene later, final To baseband signal, it is uploaded to computer.
Compared with prior art, the beneficial effects brought by the technical solution of the present invention are as follows:
(1) present invention improves the utilization rate of signal source, and the signal source of two kinds of different frequencies is used as transmitting signal, and mutually It is used as local oscillation signal input mixer, mutually to realize digital low intermediate frequency receiver structure.
(2) since the signal of two frequencies is used as transmitting signal in the present invention, the signal of two frequencies is ok Vital sign parameter signals are detected, and relevant treatment is carried out to two detection results, can be further improved vital signs detecting Precision.
Detailed description of the invention
Fig. 1 is the double frequency continuous wave Doppler radar circuit structure schematic diagram that the present invention inhibits direct current biasing.
Appended drawing reference: LO1 No.1 local oscillator, No. bis- local oscillators of LO2, Power Divider1 No.1 power splitter, No. bis- power splitters of PowerDivider2, No. tri- power splitters of Power Divider3, No. tetra- power splitters of Power Divider4, PA Power amplifier, Tx_Antenna transmitting antenna, Rx_Antenna receiving antenna, BPF1 No.1 bandpass filter, BPF2 bis- Bandpass filter, No. tri- bandpass filters of BPF3, No. tetra- bandpass filters of BPF4, No. five bandpass filters of BPF5, BPF6 six Bandpass filter, No. seven bandpass filters of BPF7, No. eight bandpass filters of BPF8, No. nine bandpass filters of BPF9, BPF10 ten Bandpass filter, LNA1 No.1 low-noise amplifier, No. bis- low-noise amplifiers of LNA2, Mixer1 No.1 frequency mixer, Mixer2 No. two frequency mixers, No. tri- frequency mixers of Mixer3, No. tetra- frequency mixers of Mixer4, No. five frequency mixers of Mixer5, Mixer6 six mixing Device, ADC1 No.1 analog-digital converter, No. bis- analog-digital converters of ADC2, FPGA field programmable gate array, Computer computer.
Specific embodiment
Illustrate technical solution of the present invention in order to clearer, the present invention will be further explained below with reference to the attached drawings.It is right For those of ordinary skill in the art, without creative efforts, it can also be obtained according to these attached drawings His attached drawing.
The double frequency continuous wave Doppler radar circuit structure of inhibition direct current biasing of the invention, as shown in Figure 1, including receiving Antenna Rx_Antenna and transmitting antenna Tx_Antenna.The receiving antenna Rx_Antenna is connected with No. four power splitters Power Divider4, No. four power splitters Power Divider4 output end is divided into two-way, wherein being sequentially connected in series all the way No.1 bandpass filter BPF1, No.1 low-noise amplifier LNA1, No.1 frequency mixer Mixer1, No. five bandpass filter BPF5 and No.1 analog-digital converter ADC1, another way have been sequentially connected in series No. two bandpass filter BPF2, No. two low-noise amplifier LNA2, two Number frequency mixer Mixer2, No. six bandpass filter BPF6 and No. two analog-digital converters ADC2, the No.1 analog-digital converter ADC1 On-site programmable gate array FPGA is all connected with No. two analog-digital converter ADC2.Wherein, the work of on-site programmable gate array FPGA With being equivalent to four bandpass filters and four frequency mixers, No. seven bandpass filter BPF7 as shown in Figure 1, No. eight band logicals filters Wave device BPF8, No. nine bandpass filter BPF9, No. ten bandpass filter BPF10, No. three frequency mixer Mixer3, No. four frequency mixers Mixer4, No. five frequency mixer Mixer5, No. six frequency mixer Mixer6.
The transmitting antenna Tx_Antenna connection power amplifier PA output end, the power amplifier PA input terminal connect No. two power splitter Power Divider2 output ends are connect, No. two power splitters Power Divider2 input terminal is divided into two-way, It is wherein connected with No.1 power splitter Power Divider1 all the way, another way is connected with No. three power splitter Power Divider3. The No.1 power splitter Power Divider1 input terminal is connected with No.1 local oscillator LO1, and output end is divided into two-way, wherein defeated all the way Outlet A connection No. two power splitter Power Divider2 input terminal E, another output end B connect through No. three bandpass filter BPF3 It is connected to No.1 frequency mixer Mixer1 input terminal.No. three power splitters Power Divider3 input terminal is connected with No. two local oscillators LO2, output end are divided into two-way, wherein No. two power splitter Power Divider2 input terminal F of output end C connection all the way, another way Output end D is connected to No. two frequency mixer Mixer2 input terminals through No. four bandpass filter BPF4.
In transmitting terminal, the frequency that No.1 local oscillator LO1 and No. two local oscillator LO2 are generated is respectively 1.67GHz and 2.06GHz, and two The signal of a frequency passes through No.1 power splitter Power Divider1 respectively and No. three power splitter Power Divider3 are divided into two Road is both used as transmitting signal all the way, is in addition both used as local oscillation signal all the way.In order to minimize mixing after baseband signal remnants Phase noise drives two local oscillation signal sources using same crystal oscillator.Two transmitting signals utilize No. two power splitter Power Divider2 synthesis is launched after power amplifier PA amplification by transmitting antenna Tx_Antenna.In receiving end, connect The signal received first passes through No. four power splitter Power Divider4 and divides the signal into two-way, then receives during signal passes through respectively Frequency of heart is No. two bandpass filter BPF2 of No.1 the bandpass filter BPF1 and 1.67GHz of 2.06GHz, leads to each receive The signal of a frequency is contained only in road.Two-way receives signal respectively through No.1 low-noise amplifier LNA1 and No. two low noises later Acoustic amplifier LNA2 amplification, the local oscillator letter that the local oscillation signal and centre frequency for being respectively 1.67GHz with centre frequency are 2.06GHz It number is mixed.When mixing, the reception signal of 1.67GHz is mixed with the local oscillation signal of 2.06GHz, the reception of 2.06GHz Signal is mixed with the local oscillation signal of 1.67GHz.Obtained low intermediate frequency signal is mixed first respectively by No. five bandpass filters BPF5 and No. six bandpass filter BPF6 filtering, then adopted respectively through No.1 analog-digital converter ADC1 and No. two analog-digital converter ADC2 Sample is converted into digital signal, later low intermediate frequency signal carry out in programmable gate array FPGA numeric field at the scene second it is orthogonal mixed Frequently, baseband signal is finally obtained, computer Computer is uploaded to.
The mode that vital signs detecting is realized is specific as follows.Ignore amplitude variation, if transmitting signal T (t) such as formula
(1) shown in:
T (t)=cos (2 π ft+ φ (t)) (1)
In formula (1), f is the frequency for emitting signal, and t is the time, and φ (t) is initial phase.The chest cavity movement of people can be right Emit signal and generate modulating action, and makes to emit signal generation reflection.The frequency that receiving antenna receives is f1Reflection signal R1 (t) and frequency is f2Reflection signal R2(t) respectively as shown in formula (2), (3):
In formula (2), (3), d0For the distance between radar and measured object, x (t) is the chest cavity movement of human body, λ1And λ2Point Other respective frequencies f1And f2Wavelength, c be signal spread speed, φ1(t-2d0/ c) and φ2(t-2d0/ c) it is residual phase. After reflection signal is mixed with local oscillation signal, obtained two-way intermediate-freuqncy signal RIF1(t) and RIF2(t) respectively as shown in formula (4), (5):
In formula (4), (5), fIF=f1-f2For the intermediate-freuqncy signal after mixing, Δ φ1With Δ φ2For residual phase.Such as formula (4), intermediate-freuqncy signal shown in (5) becomes digital signal respectively after No.1 analog-digital converter and No. two analog-digital converters, and It carries out second in numeric field to be mixed, obtained baseband signal BI1(n)、BQ1(n)、BI2(n)、BQ2(n) respectively such as formula (6)-(9) It is shown:
Vital sign parameter signals, the complex signal S of reconstruction are extracted using complex signal demodulation method1(n)、S2(n) decibel such as formula (10), shown in (11):
Embodiment:
The model of specifically used component is described below in the present invention, and No.1 local oscillator LO1 and No. two local oscillator LO2 are all made of The LTC6948IUFD of Analog Devices company generates two frequencies of 1.67GHz and 2.06GHz using the local oscillator；No.1 function Divide device Power Divider1, No. two power splitter Power Divider2, No. three power splitter Power Divider3, No. four function point Device Power Divider4 is all made of the PD0922J5050S2HF of Anaren company；No. two bandpass filter BPF2 of 1.67GHz The TQQ7303 of TriQuint company is all made of with No. three bandpass filter BPF3；The No.1 bandpass filter BPF1 of 2.06GHz and No. four bandpass filter BPF4 are all made of the 856738 of TriQuint company；No. five bandpass filter BPF5 of 390MHz and No. six Bandpass filter BPF6 is all made of the B39391B5047Z810 of Qualcomm company；No.1 low-noise amplifier LNA1 and No. two Low-noise amplifier LNA2 is all made of the HMC618ALP3ETR of Analog Devices company；No.1 frequency mixer Mixer1 and two Number frequency mixer Mixer2 is all made of the LT5575EUF of AnalogDevices company；No.1 analog-digital converter ADC1 and No. two moduluses Converter ADC2 uses the AD9625 of Analog Devices company；On-site programmable gate array FPGA is using Intel Company 5CSXFC6D6F31C6N。
Although function and the course of work of the invention are described above in conjunction with attached drawing, the invention is not limited to Above-mentioned concrete function and the course of work, the above mentioned embodiment is only schematical, rather than restrictive, ability The those of ordinary skill in domain under the inspiration of the present invention, is not departing from present inventive concept and scope of the claimed protection situation Under, many forms can also be made, all of these belong to the protection of the present invention.

Claims (2)

1. a kind of double frequency continuous wave Doppler radar circuit structure for inhibiting direct current biasing, including receiving antenna (Rx_Antenna) With transmitting antenna (Tx_Antenna), which is characterized in that the receiving antenna (Rx_Antenna) is connected with No. four power splitters (Power Divider4), output end is divided into two-way to No. four power splitters (Power Divider4), wherein successively going here and there all the way It is associated with No.1 bandpass filter (BPF1), No.1 low-noise amplifier (LNA1), No.1 frequency mixer (Mixer1), No. five band logical filters Wave device (BPF5) and No.1 analog-digital converter (ADC1), another way be sequentially connected in series No. two bandpass filters (BPF2), No. two it is low Noise amplifier (LNA2), No. two frequency mixers (Mixer2), No. six bandpass filters (BPF6) and No. two analog-digital converters (ADC2), the No.1 analog-digital converter (ADC1) and No. two analog-digital converters (ADC2) are all connected with field programmable gate array (FPGA)；
The transmitting antenna (Tx_Antenna) connects power amplifier (PA), power amplifier (PA) the input terminal connection Having No. two power splitters (Power Divider2), No. two power splitters (Power Divider2) input terminal is divided into two-way, In be connected with No.1 power splitter (Power Divider1) all the way, another way is connected with No. three power splitter (Power Divider3)；No.1 power splitter (Power Divider1) input terminal is connected with No.1 local oscillator (LO1), and output end is divided into Two-way, wherein connecting No. two power splitter (Power Divider2) input terminals all the way, another way is through No. three bandpass filters (BPF3) it is connected to No.1 frequency mixer (Mixer1) input terminal；No. three power splitters (Power Divider3) the input terminal connection There are No. two local oscillators (LO2), output end is divided into two-way, wherein No. two power splitter (Power Divider2) input terminals are connected all the way, Another way is connected to No. two frequency mixer (Mixer2) input terminals through No. four bandpass filters (BPF4).
2. the double frequency continuous wave Doppler radar circuit structure according to claim 1 for inhibiting direct current biasing, feature exist In, in transmitting terminal, the frequency that No.1 local oscillator (LO1) and No. two local oscillators (LO2) generate is respectively 1.67GHz and 2.06GHz, and two The signal of frequency passes through No.1 power splitter (Power Divider1) respectively and No. three power splitters (Power Divider3) are divided into Two-way is both used as transmitting signal all the way, is in addition both used as local oscillation signal all the way；Two transmitting signals utilize No. two power splitters (Power Divider2) synthesis is launched after power amplifier (PA) amplification by transmitting antenna (Tx_Antenna) It goes；
In receiving end, the signal received first passes through No. four power splitters (Power Divider4) and divides the signal into two-way, then Receive No. two band logicals filter that signal passes through No.1 bandpass filter (BPF1) and 1.67GHz that centre frequency is 2.06GHz respectively Wave device (BPF2), two-way receives signal respectively through No.1 low-noise amplifier (LNA1) and No. two low-noise amplifiers later (LNA2) amplify, the local oscillation signal that the local oscillation signal and centre frequency for being respectively 1.67GHz with centre frequency are 2.06GHz carries out Mixing；Obtained low intermediate frequency signal is mixed first respectively by No. five bandpass filters (BPF5) and No. six bandpass filters (BPF6) Filtering, then respectively through No.1 analog-digital converter (ADC1) and No. two analog-digital converter (ADC2) sample conversions at digital signal, it Low intermediate frequency signal carries out second of orthogonal mixing in programmable gate array (FPGA) numeric field at the scene afterwards, finally obtains base band letter Number, it is uploaded to computer (Computer).
CN201811093886.3A 2018-09-19 2018-09-19 A kind of double frequency continuous wave Doppler radar circuit structure inhibiting direct current biasing Pending CN109239671A (en)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116087892A (en) * 2023-04-10 2023-05-09 中山大学 FMCW-SAR interference method, electronic equipment and storage medium

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1179071A (en) * 1996-08-07 1998-04-15 诺基亚流动电话有限公司 Double frequency band mobile station using cross joint tramsmitter and receiver circuit
JP3010622B1 (en) * 1998-10-01 2000-02-21 日本電気株式会社 Dual band transceiver
US20080096508A1 (en) * 2004-09-20 2008-04-24 Frontler Silicon Limited Low Intermediate Frequency (If) Radio Receiver Circuits
US20090103654A1 (en) * 2007-10-23 2009-04-23 Stefan Van Waasen Low intermediate frequency receiver
CN106533474A (en) * 2016-11-22 2017-03-22 四川九洲电器集团有限责任公司 Receiver and signal processing method

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1179071A (en) * 1996-08-07 1998-04-15 诺基亚流动电话有限公司 Double frequency band mobile station using cross joint tramsmitter and receiver circuit
JP3010622B1 (en) * 1998-10-01 2000-02-21 日本電気株式会社 Dual band transceiver
US20080096508A1 (en) * 2004-09-20 2008-04-24 Frontler Silicon Limited Low Intermediate Frequency (If) Radio Receiver Circuits
US20090103654A1 (en) * 2007-10-23 2009-04-23 Stefan Van Waasen Low intermediate frequency receiver
CN106533474A (en) * 2016-11-22 2017-03-22 四川九洲电器集团有限责任公司 Receiver and signal processing method

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
ISAR MOSTAFANEZHAD ET AL.: ""A Coherent Low IF Receiver Architecture for Doppler Radar Motion Detector Used in Life Signs Monitoring"", 《RWS 2010》 *

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116087892A (en) * 2023-04-10 2023-05-09 中山大学 FMCW-SAR interference method, electronic equipment and storage medium
CN116087892B (en) * 2023-04-10 2023-06-16 中山大学 FMCW-SAR interference method, electronic equipment and storage medium

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