CN108011395B - Control method for automatically optimizing charge-discharge loop in hybrid inverter - Google Patents

Control method for automatically optimizing charge-discharge loop in hybrid inverter Download PDF

Info

Publication number
CN108011395B
CN108011395B CN201711307261.8A CN201711307261A CN108011395B CN 108011395 B CN108011395 B CN 108011395B CN 201711307261 A CN201711307261 A CN 201711307261A CN 108011395 B CN108011395 B CN 108011395B
Authority
CN
China
Prior art keywords
frequency
disturbance
circuit
charge
inverter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN201711307261.8A
Other languages
Chinese (zh)
Other versions
CN108011395A (en
Inventor
肖遥
王祺
詹国敏
赵兴国
许斌斌
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Phono Solar Technology Co ltd
Original Assignee
Phono Solar Technology Co ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Phono Solar Technology Co ltd filed Critical Phono Solar Technology Co ltd
Priority to CN201711307261.8A priority Critical patent/CN108011395B/en
Publication of CN108011395A publication Critical patent/CN108011395A/en
Application granted granted Critical
Publication of CN108011395B publication Critical patent/CN108011395B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

The invention discloses a control method for automatically optimizing a charge and discharge circuit in a hybrid inverter, which comprises the steps of enabling a bidirectional LLC resonant circuit to work in a reverse mode through constant-voltage closed-loop control of an inverter circuit and constant-current closed-loop control of a Buck/Boost converter, disturbing the extreme value gain of an LLC circuit driving frequency searching circuit, disturbing output power to search a plurality of extreme values, and comprehensively determining the optimal frequency operating point of the charge and discharge circuit in the hybrid inverter. The invention can quickly and accurately determine the resonant frequency of the system based on the gain characteristic of the LLC circuit and combining with a plurality of control steps, can enable the charge-discharge loop to work at the optimal frequency point, can improve the efficiency of the circuit and reduce EMI interference, and can simplify the design process of the circuit because the gain of the frequency point is fixed. In the calibration process, an accurate reference voltage source and extra wiring are not needed, and the resonant frequency correction program can be started in the normal use process of the equipment.

Description

Control method for automatically optimizing charge-discharge loop in hybrid inverter
Technical Field
The invention relates to the technical field of power electronic application, in particular to a control method for automatically optimizing a charge-discharge loop in a hybrid inverter.
Background
With the development of distributed energy, hybrid inverters including energy storage units and based on a spontaneous self-use mode are increasingly widely used by users. The DC connection end of the inverter comprises a photovoltaic array input port, a low-voltage (generally 48V or less) battery port, and an AC connection end comprises a commercial power port and an off-grid emergency power output port. In order to output alternating-current voltage close to mains voltage, the voltage of a direct-current bus is usually 8-10 times of the voltage of a battery, a conventional bidirectional Buck/Boost circuit cannot efficiently and economically achieve a required Boost ratio, therefore, a primary high-frequency transformer needs to be added to achieve a DC/DC Boost function, and a common topological scheme is a full-bridge LLC circuit.
In the LLC + Buck/Boost two-stage circuit structure, because the Buck/Boost is used for closed-loop control of voltage or current, an LLC circuit is not required to change the gain of a loop in a frequency modulation mode, and the LLC circuit usually works at a theoretical resonant frequency point so as to obtain higher efficiency. However, since it is usually difficult to maintain the manufacturing precision of the capacitors and the transformer leakage inductances that form the resonant circuit, which may cause the deviation of the resonant frequency, especially when the capacitors and the transformer leakage inductances are both in positive deviation or negative deviation, the defect becomes more obvious, and the frequency operating point set by the hybrid inverter in mass production is usually fixed at the theoretical design value, which is difficult to ensure that all inverters operate at the optimal frequency point, and it is obviously unrealistic due to the low efficiency by adopting the manual calibration method, and it is necessary to find a method for automatically finding the optimal operating frequency point applied to the hybrid inverter.
Disclosure of Invention
In view of the above-mentioned defects in the prior art, the present invention provides a control method for automatically optimizing a charge/discharge loop in a hybrid inverter, which utilizes the transfer function characteristic of a circuit to obtain an optimal operating frequency point by means of frequency disturbance.
The invention discloses a control method for automatically optimizing a charge-discharge loop in a hybrid inverter, which comprises the following steps of:
1) enabling the grid-connected side DC/AC inverter to work in a direct-current bus constant-voltage closed-loop control mode;
2) the bidirectional Buck/Boost converter works in a constant current closed-loop control mode, and the LLC converter works in a reverse running mode by giving a current direction;
3) the LLC converter works in a reverse running mode, and a full-control switch device of the H bridge on the same side of the resonant capacitor does not have a driving signal, wherein a body diode forms an uncontrolled rectifying circuit and applies a driving signal with the duty ratio of 50% to a full-control switch of the H bridge directly connected with the transformer;
4) the LLC converter starts a frequency disturbance mode, namely firstly, the direction of a disturbance step length delta f is judged, and if the delta f is equal to 0, the set starting frequency f is setrsAs a point of resonance frequency, otherwise with a set starting frequency frsTaking delta f as a starting point to carry out frequency disturbance, calculating the voltage gain of the LLC converter, judging the disturbance direction according to the change direction of the gain, continuing the disturbance in the original direction if the gain is increased, and indicating that the previous frequency point is the resonant frequency point if the gain is reduced;
5) starting a power disturbance mode of the bidirectional Buck/Boost converter, namely sequentially increasing the given current value of the step 2) to 100% of the rated value by a set step length, repeating the steps 2) -4) n times to obtain n frequency points, and marking the frequency points as fr1，fr1…frnAnd if n is the repetition number, the operation frequency of the charge-discharge loop of the hybrid inverter is set as follows: f. ofr＝∑(fr1…frn)/n。
In step 4), the frequency disturbance mode comprises the step of setting a starting point frequency f during first disturbancersThe positive direction and the negative direction are disturbed once respectively, the direction in which the gain is increased is taken as the disturbance direction, and if the gains in the positive direction and the negative direction are both reduced, the disturbance is not needed.
In step 5), the initial power in the power disturbance mode is greater than 50% of the rated power.
In step 5), the power disturbance mode is increased to 100% of the rated value in 10% steps.
The DC/AC inverter is a single-phase inverter or a three-phase inverter.
The DC/AC inverter stabilizes the DC bus voltage by power balance control.
The invention has the beneficial effects that: the invention can quickly and accurately determine the resonant frequency of the system based on the gain characteristic of the LLC circuit and combining with a plurality of control steps, can enable the charge-discharge loop to work at the optimal frequency point, can improve the efficiency of the circuit and reduce EMI interference, and can simplify the design process of the circuit because the gain of the frequency point is fixed. In the calibration process, an accurate reference voltage source and extra wiring are not needed, and the resonant frequency correction program can be started in the normal use process of the equipment. And the scheme only needs little data storage space, and the operation speed is high.
The conception, the specific structure and the technical effects of the present invention will be further described with reference to the accompanying drawings to fully understand the objects, the features and the effects of the present invention.
Drawings
FIG. 1 is a circuit topology of the present invention;
FIG. 2 is a block diagram of the single phase DC/AC inverter voltage closed loop control of the present invention;
FIG. 3 is a block diagram of the three-phase DC/AC inverter voltage closed loop control of the present invention;
FIG. 4 is a block diagram of the current closed-loop control of the bidirectional Buck/Boost converter of the present invention;
FIG. 5 is a gain curve of the transfer function at different quality factors when the bidirectional LLC converter of the invention is run in reverse;
FIG. 6 is a flow chart of the present invention.
Detailed Description
As shown in fig. 6, a control method for automatically optimizing a charge-discharge loop in a hybrid inverter includes the following steps:
1) the grid-connected side DC/AC inverter works in a direct-current bus constant-voltage closed-loop control mode;
2) the bidirectional Buck/Boost converter works in a constant current closed-loop control mode, and the current direction enables the LLC converter to work in a reverse running mode;
3) the LLC converter works in a reverse running mode, a full-control switch device of the H bridge on the same side with the resonant capacitor has no driving signal, a body diode of the LLC converter forms an uncontrolled rectifying circuit, and a full-control switch of the H bridge directly connected with the transformer applies a driving signal with the duty ratio of 50%;
4) starting a frequency disturbance mode of the LLC converter, setting a disturbance step length delta f to design a resonant frequency frsPerforming frequency disturbance for a starting point, calculating the voltage gain of the LLC circuit, judging the disturbance direction according to the change direction of the gain until the maximum gain is found, and recording a frequency point corresponding to the gain;
5) starting a power disturbance mode of the bidirectional Buck/Boost converter, sequentially increasing the given current value of the step 2 to 100% of the rated value by a specific step length, repeating the step 2-the step 4 for multiple times to obtain multiple frequency points marked as fr1，fr1…frnAnd n is the repetition number, and the operation frequency of a charge-discharge loop of the hybrid inverter is set as follows: f. ofr＝∑(fr1…frn)/n。
In this embodiment, the frequency disturbance mode in step 4) includes determining the direction of the frequency disturbance by respectively disturbing once in the positive direction and the negative direction during the first disturbance.
In this embodiment, the initial power in the power disturbance mode in step 5) is greater than 50% of the rated power.
In this embodiment, the power disturbance mode of step 5) is increased to 100% of the rated value in 10% steps.
In this embodiment, the DC/AC inverter is a single-phase inverter or a three-phase inverter.
In this embodiment, the DC/AC inverter stabilizes the DC bus voltage by power balance control.
The embodiments of the present invention will be described in detail below with reference to the accompanying drawings.
FIG. 1 shows a topology of a single-phase grid-connected hybrid inverterThe system comprises a bidirectional LLC resonant converter 101, a bidirectional Buck/Boost converter 102 and a full-bridge inverter 103. Wherein, the DC output end of the LLC resonant converter 101 is connected with the input end of the bidirectional Buck/Boost converter 102, and both ends of the DC bus are connected with a filter capacitor C2The output end of the bidirectional Buck/Boost converter 102 is connected with the DC input end of the full-bridge inverter 103, and the two ends of the DC bus are connected with a filter capacitor C3。。
101102103 is a basic functional unit, is common knowledge in the art, and need not be explained. Therefore, the connection mode of known basic elements such as a resonant capacitor, an H bridge, a fully-controlled switching device, a diode, an uncontrolled rectifying circuit, a transformer, a fully-controlled switch and the like in each unit does not need to be introduced.
Such inverters also usually have a Boost circuit connected to the photovoltaic panel, which is irrelevant in the present invention. The double-stage DC/DC converter formed by the LLC circuit and the Buck/Boost circuit has the advantages that the LLC circuit at the front stage realizes a high-efficiency direct-current transformer function, and the control of the Buck/Boost circuit at the rear stage is simpler. LLC circuits do not require frequency modulation to adjust the output voltage of the circuit, and therefore operate optimally at a fixed resonant frequency point. Its resonant frequency frBy a resonant inductance LrAnd a resonance capacitor CrDetermining, as shown in formula 1:
Figure BDA0001502225060000051
however, due to the relatively low manufacturing accuracy of the inductor and the capacitor and the influence of the stray parameters in the circuit, which cannot be accurately predicted, it is difficult for the mass-produced hybrid inverters to work at a uniform resonant frequency point, so that it is necessary for the individual inverters to automatically find their respective resonant frequencies before normal operation. The specific implementation steps are as follows:
1) starting the grid-connected side inverter 101, and stabilizing the DC bus voltage U through a double closed-loop control strategy3FIG. 2 shows a block diagram of a voltage closed-loop control strategy of a single-phase inverter, and FIG. 3 showsA voltage closed-loop control strategy block diagram of a three-phase inverter is disclosed. The direct control method is characterized in that a single-phase inverter or a three-phase inverter stabilizes the voltage of a direct-current bus through power balance control, and the direct control object is active grid-connected current on the premise that the voltage of a power grid is fixed.
2) The Buck/Boost converter 102 works in a Buck running state, namely the IGBT of V6 does not act, the IGBT of V5 acts, and the control inductor L1Flows from point a to point B in fig. 1, and in order to operate the LLC circuit at the high Q point, the magnitude of the current should be large, e.g., equal to or greater than 0.5InWherein Q is a quality factor, InIs the rated current. Fig. 4 shows a current closed-loop control strategy of the Buck/Boost converter. The output power of the LLC circuit is stabilized through constant current closed-loop control and constant voltage closed-loop control in the step 1, and the fluctuation range of the Q value of the system is smaller.
3) The LLC circuit works in a reverse mode, namely MOSFETs of Q5-Q8 do not work, a full-bridge uncontrolled rectifying circuit is formed by body diodes of the MOSFETs, the MOSFETs of Q1-Q4 work, and square wave excitation voltage with 50% of duty ratio is applied to the resonant cavity. At this time, the excitation inductor is connected in parallel with the battery end, no influence is generated on the resonant cavity, the circuit is degenerated into an LC circuit, but the resonant frequency at this time is irrelevant to the running direction of the LLC circuit and is still determined by the formula (1), and the gain can be expressed as follows:
Figure BDA0001502225060000052
wherein: ω is 2 pi f, f is the actual operating frequency of the circuit;
Figure BDA0001502225060000061
RACis defined as the equivalent impedance of the alternating current,
Vofor the output voltage of LLC circuit, IoAnd outputting current for the LLC circuit, wherein N is the transformer transformation ratio.
Fig. 5 is a gain curve corresponding to different Q values in the operating state, and the theoretical value of the peak gain is 1, but due to the influence of the transformer transformation ratio and the line stray parameters, the actually calculated value is hardly equal to 1, but it can still be determined that the frequency corresponding to the peak gain point is the resonant frequency point, and it can be seen that the attenuation of the gain derivative is faster when the Q value is larger, which is advantageous for extracting the maximum gain.
The reverse operation mode described in step 2 and step 3 is determined according to the position where the resonance capacitor is connected.
4) As shown in FIG. 6, the LLC circuit starts the frequency perturbation mode, sets a perturbation step size Δ f, Δ f > 0, and designs the resonant frequency frsPerforming frequency disturbance as a starting point, and outputting a voltage value u to the LLC circuitoutAnd a battery terminal voltage value uinSampling is performed. Calculating f at first disturbancersGain G corresponding to frequency point1＝uout1/uin1、frsGain G corresponding to + Δ f frequency point2＝uout2/uin2And frs- Δ f frequency point corresponding gain G3＝uout3/uin3If G is2＜G1＜G3Then continue the perturbation with Δ f as the step size, if G3＜G1＜G2Then continue the perturbation with- Δ f as step length, if G2＜G1＞G3F is thenrsNamely the resonance frequency point. When the disturbance step length is delta f, the disturbance is continued until G appears from the disturbance to the nth timen-1＜GnThen f will bers+ (n-1) Δ f is used as a resonance frequency point of the LLC circuit; otherwise, carrying out reverse-direction disturbance until G appears when the disturbance reaches the nth timen-1＜GnThen f will bers- (n-1) Δ f as a resonance frequency point of the LLC circuit.
In the disturbance process, the output voltage of the LLC circuit and the battery terminal voltage are likely to fluctuate, but the disturbance caused by fluctuation of the absolute value of the voltage is shielded by a gain calculation mode. The fluctuation of the output voltage of the LLC circuit will also cause the equivalent AC impedance RACThe Q value fluctuates, but it is indicated by the Gain shown in fig. 5 that the frequency corresponding to the maximum Gain point is always fixed regardless of the Q-Gain curve. Of course, limiting the Q value to a small range can reduce the settling time of the system and speed up the search for the resonant frequencyThe speed of (2).
5) Since the power level may affect the electrical parameters of the resonator, and to eliminate the error in a single search, the power is perturbed to increase the number of sampling gain curves, starting at 50% of the rated power and starting at 10% InIncreasing the output current of the Buck/Boost converter for the step length until reaching 100 percent InRepeating the steps 2 to 4 to obtain resonant frequencies marked as f under a plurality of Q value curvesr0.5，fr0.6…fr1.0The simpler method to eliminate the error is to set the actual operating frequency of the circuit to fr＝(fr0.5+fr0.6…+fr1.0)/6. In the actual operation process, the frequency which may be solved has a value with a large deviation, and the data can be analyzed and processed in a statistical correlation mode. For the initially determined frequency point, the frequency and the density of power scanning can be increased, more actual calculated values of the resonant frequency can be obtained, and the calculation accuracy is further improved.
The scheme eliminates the influence of parasitic parameters, does not need to calculate an absolute output voltage value, does not need an auxiliary accurate voltage source or a load, can be executed at any time in an actual application scene, and can effectively correct the frequency offset caused by nonlinear factors in the operation of the circuit, so that the charging and discharging loop of the hybrid inverter always works at an optimal working point.
The foregoing detailed description of the preferred embodiments of the invention has been presented. It should be understood that numerous modifications and variations could be devised by those skilled in the art in light of the present teachings without departing from the inventive concepts. Therefore, the technical solutions available to those skilled in the art through logic analysis, reasoning and limited experiments based on the prior art according to the concept of the present invention should be within the scope of protection defined by the claims.

Claims (6)

1. A control method for automatically optimizing a charge-discharge loop in a hybrid inverter is characterized by comprising the following steps:
1) enabling the grid-connected side DC/AC inverter to work in a direct-current bus constant-voltage closed-loop control mode;
2) the bidirectional Buck/Boost converter works in a constant current closed-loop control mode, and the LLC converter works in a reverse running mode by giving a current direction;
3) the LLC converter works in a reverse running mode, and a full-control switch device of the H bridge on the same side of the resonant capacitor does not have a driving signal, wherein a body diode forms an uncontrolled rectifying circuit and applies a driving signal with the duty ratio of 50% to a full-control switch of the H bridge directly connected with the transformer;
4) the LLC converter starts a frequency disturbance mode, namely firstly, the direction of a disturbance step length delta f is judged, and if the delta f is equal to 0, the set starting frequency f is setrsAs a point of resonance frequency, otherwise with a set starting frequency frsTaking delta f as a starting point to carry out frequency disturbance, calculating the voltage gain of the LLC converter, judging the disturbance direction according to the change direction of the gain, continuing the disturbance in the original direction if the gain is increased, and indicating that the previous frequency point is the resonant frequency point if the gain is reduced;
5) starting a power disturbance mode of the bidirectional Buck/Boost converter, namely sequentially increasing the given current value of the step 2) to 100% of the rated value by a set step length, repeating the steps 2) -4) n times to obtain n frequency points, and marking the frequency points as fr1，fr1…frnAnd if n is the repetition number, the operation frequency of the charge-discharge loop of the hybrid inverter is set as follows: f. ofr＝∑(fr1…frn)/n。
2. The method for controlling automatic optimization of the charge-discharge loop in the hybrid inverter according to claim 1, wherein: in step 4), the frequency disturbance mode comprises the step of setting a starting point frequency f during first disturbancersThe positive direction and the negative direction are disturbed once respectively, the direction in which the gain is increased is taken as the disturbance direction, and if the gains in the positive direction and the negative direction are both reduced, the disturbance is not needed.
3. The control method for automatically optimizing the charge and discharge loop in the hybrid inverter according to claim 1, wherein: in step 5), the initial power in the power disturbance mode is greater than 50% of the rated power.
4. The control method for automatically optimizing the charge and discharge loop in the hybrid inverter according to claim 1, wherein: in step 5), the power disturbance mode is increased to 100% of the rated value in 10% steps.
5. The control method for automatically optimizing the charge and discharge loop in the hybrid inverter according to claim 1, wherein: the DC/AC inverter is a single-phase inverter or a three-phase inverter.
6. The control method for automatically optimizing the charge and discharge loop in the hybrid inverter according to claim 1, wherein: the DC/AC inverter stabilizes the DC bus voltage through power balance control.
CN201711307261.8A 2017-12-11 2017-12-11 Control method for automatically optimizing charge-discharge loop in hybrid inverter Active CN108011395B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201711307261.8A CN108011395B (en) 2017-12-11 2017-12-11 Control method for automatically optimizing charge-discharge loop in hybrid inverter

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201711307261.8A CN108011395B (en) 2017-12-11 2017-12-11 Control method for automatically optimizing charge-discharge loop in hybrid inverter

Publications (2)

Publication Number Publication Date
CN108011395A CN108011395A (en) 2018-05-08
CN108011395B true CN108011395B (en) 2021-04-02

Family

ID=62057798

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201711307261.8A Active CN108011395B (en) 2017-12-11 2017-12-11 Control method for automatically optimizing charge-discharge loop in hybrid inverter

Country Status (1)

Country Link
CN (1) CN108011395B (en)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109103850B (en) * 2018-10-24 2019-12-31 西安特锐德智能充电科技有限公司 Storage medium, and short-circuit protection control method, device and system of bidirectional power converter
CN109067016B (en) * 2018-10-31 2024-07-30 刘应许 Wireless charging system and charging parameter adjusting device and method
CN110620517B (en) * 2019-09-27 2021-08-17 中南大学 Parallel input and serial output aging power supply device
CN112564265A (en) * 2020-12-10 2021-03-26 深圳市瑞能时代科技有限公司 Power supply switching circuit

Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102047549A (en) * 2009-01-07 2011-05-04 德克萨斯仪器股份有限公司 Sweeping frequency LLC resonant power regulator
CN102857095A (en) * 2011-06-28 2013-01-02 世系动力公司 Optimization of a power converter employing an LLC converter
WO2014088708A1 (en) * 2012-12-07 2014-06-12 Apple Inc. A hysteretic-mode pulse frequency modulated (hm-pfm) resonant ac to dc converter
CN104467429A (en) * 2014-12-02 2015-03-25 西安理工大学 Method for improving performance of multiplexed output switching power supply
CN204733095U (en) * 2015-01-19 2015-10-28 华南理工大学 A kind of two-stage becomes turn ratio high-frequency isolation photovoltaic DC-to-AC converter
WO2016157963A1 (en) * 2015-03-30 2016-10-06 株式会社村田製作所 Switching power supply device
CN107257198A (en) * 2017-08-14 2017-10-17 艾德克斯电子（南京）有限公司 The adjusting method and circuit of a kind of power-efficient

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR100967031B1 (en) * 2008-04-01 2010-06-30 삼성전기주식회사 Dc/dc converter with multi-output
EP2449665B1 (en) * 2009-07-03 2015-09-23 Koninklijke Philips N.V. Low cost power supply circuit and method
CN102281002B (en) * 2010-06-09 2014-05-14 光宝电子(广州)有限公司 Resonant-type electric switching circuit
US9584044B2 (en) * 2013-03-15 2017-02-28 Sunpower Corporation Technologies for converter topologies
CN104076199B (en) * 2013-03-28 2017-04-26 艾默生网络能源系统北美公司 Resonance frequency detecting method and device
CN205724930U (en) * 2016-04-22 2016-11-23 深圳中电长城能源有限公司 A kind of mixing inverter system

Patent Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102047549A (en) * 2009-01-07 2011-05-04 德克萨斯仪器股份有限公司 Sweeping frequency LLC resonant power regulator
CN102857095A (en) * 2011-06-28 2013-01-02 世系动力公司 Optimization of a power converter employing an LLC converter
WO2014088708A1 (en) * 2012-12-07 2014-06-12 Apple Inc. A hysteretic-mode pulse frequency modulated (hm-pfm) resonant ac to dc converter
CN104467429A (en) * 2014-12-02 2015-03-25 西安理工大学 Method for improving performance of multiplexed output switching power supply
CN204733095U (en) * 2015-01-19 2015-10-28 华南理工大学 A kind of two-stage becomes turn ratio high-frequency isolation photovoltaic DC-to-AC converter
WO2016157963A1 (en) * 2015-03-30 2016-10-06 株式会社村田製作所 Switching power supply device
CN107257198A (en) * 2017-08-14 2017-10-17 艾德克斯电子（南京）有限公司 The adjusting method and circuit of a kind of power-efficient

Non-Patent Citations (4)

* Cited by examiner, † Cited by third party
Title
"PV module integrated LLC resonant converter with an extended input voltage range";Umme Mumtahina, et al.;《2017 Australasian Universities Power Engineering Conference (AUPEC)》;20171122;第1-6页 *
"一种 Boost 型宽电压范围输入 LLC 谐振变换器";孙孝峰 等;《中国电机工程学报》;20150805;第35卷(第15期);第3895-3902页 *
"采用比例谐振控制的三相4桥臂并网逆变器的研究";董钺 等;《电气传动》;20141231;第44卷(第4期);第42-45页 *
"高频LLC隔离型双降压式光伏逆变器模块研究";刘闯 等;《电力电子技术》;20160331;第50卷(第3期);第41-44页 *

Also Published As

Publication number Publication date
CN108011395A (en) 2018-05-08

Similar Documents

Publication Publication Date Title
CN108011395B (en) Control method for automatically optimizing charge-discharge loop in hybrid inverter
CN110118945B (en) Energy-feedback type direct current electronic load system and self-organizing fuzzy control method thereof
CN112165183B (en) Parameter control method and system for constant-current and constant-voltage output of wireless charging system
CN108039821B (en) Current stress optimization two-phase shift control method of double-active full-bridge DC-DC converter
AU2020346195A1 (en) Method, apparatus, and system for controlling string inverter, and storage medium
CN110912282B (en) Wireless power transmission system and optimization method thereof
US11251720B1 (en) Method and apparatus for controlling grid-tie inverter
CN111416524A (en) High-disturbance-rejection fast-response control system and method for resonant DC-DC converter
CN114709940A (en) Method for simultaneously identifying load and mutual inductance of multi-load wireless power transmission system
CN110445263B (en) Cooperative control method of wireless power transmission system based on multi-coupling parameter identification
CN105141043B (en) Wireless charging control method and device
US10491018B2 (en) Power output management apparatus of battery and managment method thereof
CN110557011B (en) LLC system resonance parameter calculation method for AC/DC hybrid power distribution network
CN116707311A (en) LLC resonant converter and control system thereof
CN110247429B (en) Analysis method for voltage feedforward control photovoltaic power generation considering coupling
CN114895737B (en) Remote voltage real-time compensation system and compensation method based on power supply cable impedance detection
CN115864671A (en) Method, system, device and medium for efficiency optimization control of wireless power transmission system
CN111865085B (en) Control method and control device of combined isolation converter
CN113809911B (en) Power conversion device
CN112600414B (en) Resonant network, transformer and isolated DC converter and parameter design method thereof
Kim et al. Coil misalignment compensation algorithm for single-stage inductive wireless power transfer system using model-based approach
Bento et al. Model-Free Predictive Control of Multilevel DC–DC Converters for Energy Storage Applications
CN113824306B (en) Power conversion device
CN112600415B (en) Bidirectional resonant network, bidirectional direct current converter and parameter design method thereof
CN113708636B (en) Energy storage type bidirectional direct current conversion circuit and method for wide-voltage gain battery

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant