CN107026301A - A kind of exact and digital phase shifting method not limited by sample rate - Google Patents
A kind of exact and digital phase shifting method not limited by sample rate Download PDFInfo
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- CN107026301A CN107026301A CN201710184776.7A CN201710184776A CN107026301A CN 107026301 A CN107026301 A CN 107026301A CN 201710184776 A CN201710184776 A CN 201710184776A CN 107026301 A CN107026301 A CN 107026301A
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/18—Phase-shifters
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H11/00—Networks using active elements
- H03H11/02—Multiple-port networks
- H03H11/16—Networks for phase shifting
Abstract
The invention discloses a kind of exact and digital phase shifting method not limited by sample rate, including determine phase shift amplitude, while gathering double-channel signal data, signal coarse alignment, signal fine alignment and signal 5 steps of synthesis being carried out to data data1 and data2 "；The present invention is a kind of suitable simple signal and non-simple signal, is not limited by sample rate, calculates exact and digital phase shifting method that is simple, easily being realized using CPLD/FPGA grade high performances PLD.
Description
Technical field
The invention belongs to eliminate the skills such as sampling channel signal phase difference, non-simple signal phase shift and multi channel signals synthesis
A kind of art field, and in particular to exact and digital phase shifting method not limited by sample rate.
Background technology
So-called phase shift refers to signal of the two-way with frequency, and with therein all the way for reference, another road surpasses relative to the reference
Preceding or delayed movement, that is, be known as the movement of phase.
Tradition phase-shifting generally has two approach mainly for simple signal：One is that directly simulation simple signal is moved
Phase, such as capacitance-resistance phase shift, transformer phase shift etc., the phase shift of early stage is generally in this way.The phase shift manufactured in this way
Device has many weak points, such as:Output waveform is influenceed by defeated people's waveform, and phase shift operation is inconvenient, and phase shift angle is with connect negative
Carry and the influence of factor such as time and produce drift etc..
Another approach is the development of the development with electronic technology, particularly singlechip technology and the digital phase shift skill risen
Art, is the trend of phase shift technology a few days ago, digital drift-phase technology be first will simulation simple signal digitlization, it is shifted after be then reduced into
Analog signal.Under the control of CPLD devices, the two-way Wave data preserved in RAM is sent to high-speed d/a with DMA methods,
Exported after being changed through D/A.If what is deposited in RAM is two-way sinusoidal wave data, as long as data all the way have relative to another road
Certain phase delay, it is possible to while exporting two-way has the sine wave signal of certain phase difference, to change two paths of signals
Phase difference, only need to be data form cyclic shift wherein all the way.It is as data form is moved to high address direction, then defeated
Go out the phase delay increase on relatively another road of signal, it is on the contrary then reduce.As it was previously stated, a data form is by 1024 data points
Composition, stores the sine wave of a cycle, so one ram cell of data form cyclic shift, and the phase difference of generation is：
Because two channel signals are through D/A conversion one clock pulses of phase difference, even if so the data of two passages are complete
Exactly the same, the phase difference of output waveform can also differ 0.35 °, but this angle of lag can be compensated by Phase-shifting algorithm.Carrying out
During specific phase shift, the digit that RAM wants cyclic shift can be calculated by the phase difference value set.As a result of floating number
Computing, computational accuracy is up to 0.00001, but the displacement in RAM must be integer, therefore, and the maximum of the phase difference of generation is absolutely
Still it is 0.35 ° to error.
In a word, traditional digital drift-phase technology is on the basis of high-speed programmable device, after signal digital quantization, to lead to
Cross and move point to realize the function of digital phase shift, this method has larger limitation, is simple signal first by object, i.e. frequency
The single signal of rate, it is difficult to which phase shift is implemented to the non-simple signal with certain bandwidth；Secondly phase shifting accuracy is limited by sample rate,
The least unit of phase shift is 360/ sample rate, it is difficult to realize high-precision phase shift.
The content of the invention
The invention aims to overcoming that conventional digital phase-moving method requirement frequency is single, limited by sample rate, phase shift
The not high deficiency of precision, it is proposed that a kind of suitable simple signal and non-simple signal, do not limited by sample rate, calculate it is simple, hold
The exact and digital phase shifting method easily realized using the high performance PLD such as CPLD/FPGA.
The technical solution adopted in the present invention is：A kind of exact and digital phase shifting method not limited by sample rate, it is special
Levy and be, comprise the following steps：
Step 1：Determine phase shift amplitude；
Two-way sampling channel is tested, the time delay T of two paths is determinedi, then it is converted into product certainly
The time delay T of body sample ratei'+ti, wherein Ti' it is integer part, tiFor fractional part, i values 1 or 2；
Step 2：Double-channel signal data are gathered simultaneously；
Conditioning shaping is carried out to the signal of dual channel receiver, binary channels is then carried out and gathers simultaneously, two-way is respectively obtained and leads to
The signal data data1 and data2 in road；
Step 3：Signal coarse alignment；
Sampled signal data data2 is carried out to move point operation, makes parallel moving of signal T2(two channel signals are through D/A for ' -1 point
Change one clock pulses of phase difference), obtain coarse alignment signal data data2', data2' and be registered to a sampling with data1
In resolution ratio；
Step 4：Signal fine alignment；
The high-precision Phase-shifting algorithm phase shift for signal data data2' convert based on FFT-IFFT, phase shift size
For 2 π ft2/fs, obtain fine alignment signal data data2 ", data2 " and reach accurate alignment with data1；Wherein f is sampled signal
Frequency, fsFor the sample rate of signal；
Step 5：Signal synthesis is carried out to data data1 and data2 ".
The present invention has following features：
1st, Phase-shifting algorithm proposed by the present invention overcomes the deficiency that conventional digital Phase-shifting algorithm is only acted on simple signal, no
Only can be to simple signal, and exact and digital phase shifting can be carried out to the non-simple signal with certain bandwidth, with more
Widely use field.
2nd, phase shifting accuracy is not limited by signal sampling rate.The present invention utilizes Fourier transform and inverse transformation, to digital quantization
Signal afterwards carries out phase shift processing, it is possible to achieve the arbitrary phase movement of simple signal and non-simple signal, without being adopted by signal
The limitation of sample rate, reaches the accurate alignment of two paths of signals.
3rd, calculating process is simple, it is easy to realized using the high performance PLD such as CPLD/FPGA.Inventive algorithm
Succinctly, arithmetic speed is fast, is especially suitable for realizing two-way sampled signal using the high performance PLD such as CPLD/FPGA
High accuracy synthesis.
4th, the signal to noise ratio of composite signal is improved.The present invention is directed to the channel delay produced in double-channel signal Acquisition Circuit and entered
Row exact and digital phase shifting, makes two-way gather signal and is accurately aligned, the amplitude of composite signal is higher than using tradition phase-shifting algorithm
The signal amplitude synthesized afterwards, and noise signal amplitude keeps constant, can improve the signal to noise ratio of composite signal.
5th, the phase accuracy of composite signal is improved.Conventional digital Phase-shifting algorithm is limited by sample rate, and two-way collection signal is only
Can be registered in a sampling resolution, causing the phase of composite signal can change, and using the present invention design it is high-precision
Number of degrees word Phase-shifting algorithm can be such that two-way collection signal is accurately aligned, and the phase of composite signal will not change, for needing
For the system measured using phase factor, the present invention has stronger use value.
Brief description of the drawings
Fig. 1 is the method flow diagram of the embodiment of the present invention；
Fig. 2 is the signal condition Acquisition Circuit figure of the embodiment of the present invention；
Fig. 3 is the waveform phase shift schematic diagram of the embodiment of the present invention；
Fig. 4 is the LoranC system calibration pulse oscillogram of the embodiment of the present invention；
Fig. 5 is the Loran-C signal form schematic diagram of the embodiment of the present invention；
Fig. 6 is the right-angled intersection loop omnidirectional magnetic antenna of the embodiment of the present invention；
Fig. 7 is the Loran-C signal oscillogram of the actual double channels acquisition of the embodiment of the present invention；
Fig. 8 is the composite signal comparison of wave shape figure of the embodiment of the present invention.
Embodiment
Understand for the ease of those of ordinary skill in the art and implement the present invention, below in conjunction with the accompanying drawings and embodiment is to this hair
It is bright to be described in further detail, it will be appreciated that implementation example described herein is merely to illustrate and explain the present invention, not
For limiting the present invention.
A kind of exact and digital phase shifting method not limited by sample rate provided see Fig. 1, the present invention, including following step
Suddenly：
Step 1：Determine phase shift amplitude；
Use auxiliary high sampling rate equipment two-way sampling channel is tested (aid in high sampling rate equipment sample rate for
1000 times of collected signal frequency), determine the time delay T of two pathsi, then it is converted into product itself sample rate
Time delay Ti'+ti, wherein Ti' it is integer part, tiFor fractional part, i values 1 or 2；
Step 2：Double-channel signal data are gathered simultaneously；
Conditioning shaping is carried out to the signal of dual channel receiver, binary channels is then carried out and gathers simultaneously, two-way is respectively obtained and leads to
The signal data data1 and data2 in road；
See Fig. 2, double-channel signal data are gathered while the present embodiment, are realized using signal condition Acquisition Circuit；
The signal condition Acquisition Circuit by power subsystem, voltage follow unit, amplifying unit, filter unit, signal gathering unit and
CPLD processing units are constituted, and wherein voltage follow unit, amplifying unit, filter unit, signal gathering unit and CPLD processing is single
Member is in turn connected into sequential circuit, the output end of power subsystem respectively with voltage follow unit, amplifying unit, signal sampling unit
It is connected with CPLD processing unit power inputs.
Step 3：Signal coarse alignment；
Sampled signal data data2 is carried out to move point operation, makes parallel moving of signal T2(two channel signals are through D/A for ' -1 point
Change one clock pulses of phase difference), obtain coarse alignment signal data data2', data2' and be registered to a sampling with data1
In resolution ratio；
Step 4：Signal fine alignment；
The high-precision Phase-shifting algorithm phase shift for signal data data2' convert based on FFT-IFFT, phase shift size
For 2 π ft2/fs, obtain fine alignment signal data data2 ", data2 " and reach accurate alignment with data1；Wherein f is sampled signal
Frequency, fsFor the sample rate of signal；
The step 3 of the present embodiment to step 4 is realized using Verilog hardware languages in CPLD processing units.
The core of the present invention is the high-precision Phase-shifting algorithm converted based on FFT-IFFT, and its general principle is as follows：
Assuming that the time domain signal waveform of a certain passage is x1, its phase isBecause there is phase in sampling channelDifference,
To eliminate the difference, it is easy to signal to synthesize, it is necessary to signal x1Constant amplitude phase shift processing is carried out, signal x is obtained2, its phase isThat is x2It is in x1On the basis of phase shiftx1And x2Oscillogram is as shown in Figure 3.
Signal x1And x2It is represented by after Fourier transform is carried out：
X1=Re [X1]+j*Im[X1] (1)
X2=Re [X2]+j*Im[X2] (2)
X1Represent signal x1Frequency domain value sequence；X2Represent signal x2Frequency domain value sequence；J represents imaginary number；
Meanwhile, it is also denoted as after Fourier transform：
Wherein, A represents signal frequency domain amplitude；
Contrast (1), (3) can be obtained：
Similarly contrast (2), (4) can be obtained：
(5), (6) formula are substituted into (7), (8) Shi Ke get：
So, in signal x1In the case of known, according to (9), (10) formula, the signal x after constant amplitude translation can be obtained2Fu
The result of vertical leaf transformation.To signal x2The result of Fourier transform carries out further conversion process, i.e.,：
Wherein, n represents frequency domain sequence number；N represents band width；
All parts that sequence is more than Nyquist frequencies are set to zero, now, then to new sequence X2' carry out Fourier
Leaf inverse transformation, and the result of inverse transformation is multiplied by coefficient 2, time-domain signal x will be obtained2', with signal x1Compare, it is no longer real number
Type data point, but complex number type data, and have Re [x2']=x2, i.e., by signal x1It is shifted
Step 5：Signal synthesis is carried out to data data1 and data2 ".
Design for LoranC system omnidirectional magnetic antenna carries out the synthesis of two-way collection signal using the algorithm of the present invention.LoranC system
The working frequency of signal be 100KHz ± 10KHz, its calibration pulse waveform as shown in figure 4,
Loran-C signal form is as shown in Figure 5.Loran-C system is made up of the chain of stations of many transmission interval strict regulations, each
The chain of stations is all comprising one main and several secondary platforms, and 9 pulses of main transmitting are spaced 1ms, the 9th pulse between preceding 8 pulses
With previous pulse spacing 2ms, each pair platform launches the time interval between 8 interval 1ms pulse, two neighboring master signal
Referred to as impulse train repetition period GRI (Group Repetition Interval).In LoranC system omnidirectional magnetic antenna design process,
Because single magnetic rod antenna has directionality, it is difficult to receive the signal that the multiple guidance stations of a certain chain of stations are launched by a bar magnet,
Therefore, in order that magnetic antenna has the ability of comprehensive reception signal, it is necessary to the collection of letters is combined using many bar magnets, using ten
Omnidirectional's magnetic antenna that word intersects loop design is as shown in Figure 6.
For every bar magnet received signal, LoranC system letter is carried out using the high-precision Phase-shifting algorithm designed by the present invention
Number alignment and synthesis.
The first step：Determine phase shift amplitude；
Use auxiliary high sampling rate equipment to twin-channel signal sampling rate for 100M, by gathered data to score
Analysis, learns that the signal in two-way acquisition channel differs 334 sampled points, understands that two-way is adopted when sample rate is 1M by calculating
Time delay in collection passage should be 3.34 points.Therefore, for actual LoranC system front end double channels acquisition part, its signal is adopted
Sample rate is 1M, and the data now adopted should translate 2 points (in double channels acquisition, because two channel signals are through D/A conversion phases
A poor clock pulses, so two paths of signals should actually translate 3-1=2 point), remaining 0.34 being translated across for point is based on
The exact and digital phase shifting algorithm of FFT-IFFT conversion is completed.
Second step：Signal binary channels is gathered simultaneously；
Double channel A, B actual acquisitions Loran-C signal waveform it is as shown in Figure 7.
3rd step：Signal coarse alignment and fine alignment；
By traditional digital phase shift algorithm, shifting point is carried out to data data2,2 points of translation obtain the data of coarse alignment
Data2 ', using the exact and digital phase shifting algorithm converted based on FFT-IFFT, data data2 ' is carried out 0.068 π=
12.24 ° of phase shift, obtains the data data2 " of fine alignment.Composite signals and data of the data data1 with data data2 '
Data1 is as shown in Figure 8 with data data2 " composite signal.
Phase shift, the coarse alignment letter of gained are carried out using conventional digital Phase-shifting algorithm it can be seen from the waveform of composite signal
After number being synthesized, the wave-shape amplitude of composite signal is smaller；And use the exact and digital phase shifting converted based on FFT-IFFT to calculate
Method, it is further to signal to be handled in the case of coarse alignment, after the fine alignment signal of gained is synthesized, composite signal
Wave-shape amplitude it is larger, higher signal to noise ratio can be obtained.
What the present invention was used in double channels acquisition signal fine alignment can based on FFT-IFFT exact and digital phase shifting algorithms
To complete any angle phase shift of non-simple signal, without being limited by signal sampling rate, the algorithm carries out FFT changes to signal first
Change, in the signal frequency domain of gained, the frequency spectrum of signal is changed, then carry out IFFT conversion, obtain the time domain after phase shift
Waveform, the algorithm calculates simple, and amount of calculation is smaller, is highly suitable in the high performance PLD such as FPGA/CPLD real
It is existing, with extensive use value.
The present invention is in Data Analysis Services flow, and first by external accessory, the delay to sampling channel is carried out
Accurate test, is then convert into the amplitude that Acquisition Circuit itself sample rate answers phase shift, and integer part passes through CPLD control sampling letters
Number move point complete, reach two-way gather signal coarse alignment；Fractional part is then by based on FFT-IFFT exact and digital phase shiftings
Complete, reach the accurate alignment of two paths of signals.This method clear thinking, the phase shift for efficiently solving non-single-frequency data signal is difficult
Topic, improves the precision of digital phase shift, and the composite signal for acquisition high s/n ratio, high phase place precision is laid a good foundation.
It should be appreciated that the part that this specification is not elaborated belongs to prior art.
It should be appreciated that the above-mentioned description for preferred embodiment is more detailed, therefore it can not be considered to this
The limitation of invention patent protection scope, one of ordinary skill in the art is not departing from power of the present invention under the enlightenment of the present invention
Profit is required under protected ambit, can also be made replacement or be deformed, each fall within protection scope of the present invention, this hair
It is bright scope is claimed to be determined by the appended claims.
Claims (4)
1. a kind of exact and digital phase shifting method not limited by sample rate, it is characterised in that comprise the following steps：
Step 1：Determine phase shift amplitude；
Two-way sampling channel is tested, the time delay T of two paths is determinedi, then it is converted into product itself sampling
The time delay T of ratei'+ti, wherein Ti' it is integer part, tiFor fractional part, i values 1 or 2；
Step 2：Double-channel signal data are gathered simultaneously；
Conditioning shaping is carried out to the signal of dual channel receiver, binary channels is then carried out and gathers simultaneously, respectively obtain two paths
Signal data data1 and data2；
Step 3：Signal coarse alignment；
Sampled signal data data2 is carried out to move point operation, makes parallel moving of signal T2' -1 point, obtains coarse alignment signal data
Data2', data2' are registered in a sampling resolution with data1；
Step 4：Signal fine alignment；
The high-precision Phase-shifting algorithm phase shift for signal data data2' convert based on FFT-IFFT, phase shift size is 2 π
ft2/fs, obtain fine alignment signal data data2 ", data2 " and reach accurate alignment with data1；Wherein f is the frequency of sampled signal
Rate, fsFor the sample rate of signal；
Step 5：Signal synthesis is carried out to data data1 and data2 ".
2. the exact and digital phase shifting method according to claim 1 not limited by sample rate, it is characterised in that：Step 1
Middle that two-way sampling channel is tested using auxiliary high sampling rate equipment, the sample rate of the auxiliary high sampling rate equipment is quilt
Gather 1000 times of signal frequency.
3. the exact and digital phase shifting method according to claim 1 not limited by sample rate, it is characterised in that：Step 2
Described in simultaneously gather double-channel signal data, be using signal condition Acquisition Circuit realize；The signal condition Acquisition Circuit
It is made up of power subsystem, voltage follow unit, amplifying unit, filter unit, signal gathering unit and CPLD processing units, wherein
Voltage follow unit, amplifying unit, filter unit, signal gathering unit and CPLD processing units are in turn connected into sequential circuit,
The output end of power subsystem is defeated with voltage follow unit, amplifying unit, signal sampling unit and CPLD processing unit power supplys respectively
Enter end to be connected.
4. the exact and digital phase shifting method not limited by sample rate according to claim 1, it is characterised in that step
The high-precision Phase-shifting algorithm phase shift converted based on FFT-IFFT is carried out in 4 to signal data data2', its general principle is：
Assuming that the time domain signal waveform of a certain passage is x1, its phase isBecause there is phase in sampling channelDifference, to disappear
Except the difference, it is easy to signal to synthesize, it is necessary to signal x1Constant amplitude phase shift processing is carried out, signal x is obtained2, its phase isI.e.
x2It is in x1On the basis of phase shift
Signal x1And x2It is represented by after Fourier transform is carried out：
X1=Re [X1]+j*Im[X1] (1)
X2=Re [X2]+j*Im[X2] (2)
Wherein, X1Represent signal x1Frequency domain value sequence；X2Represent signal x2Frequency domain value sequence；J represents imaginary number；
Meanwhile, it is also denoted as after Fourier transform：
Wherein, A represents signal frequency domain amplitude；
Contrast (1), (3) can be obtained：
Similarly contrast (2), (4) can be obtained：
(5), (6) formula are substituted into (7), (8) Shi Ke get：
So, in signal x1In the case of known, according to (9), (10) formula, the signal x after constant amplitude translation can be obtained2Fourier becomes
The result changed；
To signal x2The result of Fourier transform carries out further conversion process, i.e.,：
Wherein, n represents frequency domain sequence number；N represents band width；
All parts that sequence is more than Nyquist frequencies are set to zero, now, then to new sequence X2' carry out Fourier contravariant
Change, and the result of inverse transformation is multiplied by coefficient 2, time-domain signal x will be obtained2', with signal x1Compare, it is no longer Real-valued data
Point, but complex number type data, and have Re [x2']=x2, i.e., by signal x1It is shifted
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