CN106817020B - Driving circuit - Google Patents

Driving circuit Download PDF

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Publication number
CN106817020B
CN106817020B CN201510867765.XA CN201510867765A CN106817020B CN 106817020 B CN106817020 B CN 106817020B CN 201510867765 A CN201510867765 A CN 201510867765A CN 106817020 B CN106817020 B CN 106817020B
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China
Prior art keywords
voltage value
driving
inductance
driving switch
input capacitance
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CN201510867765.XA
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CN106817020A (en
Inventor
忽培青
曾剑鸿
叶浩屹
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Delta Optoelectronics Inc
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Delta Optoelectronics Inc
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Priority to CN201510867765.XA priority Critical patent/CN106817020B/en
Priority to TW105113087A priority patent/TWI587615B/en
Priority to US15/332,623 priority patent/US10483949B2/en
Publication of CN106817020A publication Critical patent/CN106817020A/en
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Publication of CN106817020B publication Critical patent/CN106817020B/en
Priority to US16/548,781 priority patent/US10734976B2/en
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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K3/00—Circuits for generating electric pulses; Monostable, bistable or multistable circuits
    • H03K3/01—Details
    • H03K3/012—Modifications of generator to improve response time or to decrease power consumption
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/04—Modifications for accelerating switching
    • H03K17/041—Modifications for accelerating switching without feedback from the output circuit to the control circuit
    • H03K17/0412—Modifications for accelerating switching without feedback from the output circuit to the control circuit by measures taken in the control circuit
    • H03K17/04123—Modifications for accelerating switching without feedback from the output circuit to the control circuit by measures taken in the control circuit in field-effect transistor switches
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/16—Modifications for eliminating interference voltages or currents
    • H03K17/161—Modifications for eliminating interference voltages or currents in field-effect transistor switches
    • H03K17/162—Modifications for eliminating interference voltages or currents in field-effect transistor switches without feedback from the output circuit to the control circuit
    • H03K17/163—Soft switching
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/34—Snubber circuits
    • H02M1/346—Passive non-dissipative snubbers
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

This case is a kind of driving circuit, is switched to driving power, and driving circuit includes inductance and an at least driving switch, and driving circuit and power switch are equivalent at equivalent circuit, and equivalent circuit includes: the first equivalent capacity, at least reflects the input capacitance of power switch；Equivalent inductance, the inductance comprising driving circuit, and be connected in series with the first equivalent capacity；Second equivalent capacity reflects the parasitic parameter of an at least driving switch for driving circuit, and is connected in series with the first equivalent capacity and equivalent inductance；In the first equivalent capacity charging process, from the electric current of inductance be zero to the voltage value of input capacitance be setting voltage value when, the charge variation amount in the first equivalent capacity be greater than or equal to from the electric current of inductance be zero reach final steady-state value to the voltage value of input capacitance when the second equivalent capacity on charge variation amount.Without providing constant-current source in present invention driver circuit, inductance sensibility reciprocal is reduced, and inductance volume is reduced, and the loss of resistance is smaller, and system cost reduces.

Description

Driving circuit
Technical field
This case is about a kind of driving circuit, in particular to a kind of driving circuit for driving power switch.
Background technique
In recent years, since legerity type electronic equipment becomes more and more popular, in order to reduce the body of the Switching Power Supply in electronic equipment Long-pending and weight, the working frequency of Switching Power Supply is higher and higher, reduces the passive element in Switching Power Supply (such as inductance, electricity with this Hold etc.) volume.However, in the case where the working frequency of Switching Power Supply is higher and higher, the driving of the switch in Switching Power Supply Loss also can be higher and higher, as shown in Figure 1.Further, since energy conservation movement is carried out extensively in the world, switch electricity is being required While volume source reduces, the efficiency of the supply convertor in electronic equipment can not be reduced, or even be needed higher.Therefore, have The drive loss that effect reduces switch becomes particularly important.
Fig. 2 is the driving circuit of traditional switch.As shown in Fig. 2, this driving circuit mainly by driving switch S11, S12 with And resistance R is constituted, and capacitor Ciss is the input capacitance of power switch (not shown).Driving switch S11 is for opening power The input capacitance of pass charges, and for driving switch S12 for making the input capacitance of power switch discharge, resistance R is in charging and discharging circuit Dead resistance.
With currently used Metal-Oxide Semiconductor field effect transistor (Metal Oxide Semiconductor Field Effect Transistor, hereinafter referred to as MOSFET) for, as shown in figure 3, input capacitance Ciss is defined as: if Voltage change is Vgs between the grid (G) and source electrode (S) of MOSFET, and voltage change is Vgd between corresponding drain electrode (D) and grid When, then input capacitance Ciss=Cgs+Cgd* (Vgd/Vgs), i.e. MOSFET all charges for flowing in or out grid when being driven Capacitance when voltage change Vgs between gate-to-source is corresponded to, wherein capacity effect of the Cgs between grid (G) and source electrode (S), Cgd is the capacity effect between grid (G) and drain electrode (D).Input capacitance Ciss can be all provided in the specifications of usual MOSFET Magnitude curve.
The specific working sequence of traditional driving circuit are as follows: when the input capacitance Ciss of power switch needs to charge, drive Dynamic switch S11 conducting, driving switch S12 cut-off, input source then make input capacitance Ciss by driving switch S11 and resistance R Charge to voltage value Vcc, and the state of driving switch S11, S12 is always maintained at the charging process of input capacitance Ciss and terminates. In this charging process, resistance R consumes 0.5*Ciss*Vcc2Energy.When the input capacitance Ciss needs of power switch are put When electric, driving switch S11 cut-off, driving switch S12 is connected, and input capacitance Ciss then passes through driving switch S12 and resistance R electric discharge To zero, and the state of driving switch S11, S12 is always maintained to the discharge process of input capacitance Ciss and terminates.In this discharge process In, resistance R consumes 0.5*Ciss*Vcc again2Energy.Therefore, the resistance R of each driving circuit is in charge and discharge process Energy total losses are Ciss*Vcc2。
In order to reduce energy total losses of the resistance R in charge and discharge process, method used in driving circuit at present are as follows: make It is that input capacitance Ciss makees charge and discharge with the electric current of constant-current source.Concrete implementation circuit is as shown in figure 4, working timing figure such as Fig. 5 It is shown.The working sequence of this conventional driving circuit are as follows: when the input capacitance Ciss of power switch needs to charge, driving switch S21, S23 conducting, make the electric current on inductance L reach a definite value L1 close to constant-current source, such as time t0 to t1.Then, it turns off Driving switch S21, S23 makes inductance L provide the electric current input capacitance Ciss close to constant-current source and charges to voltage value Vcc, such as Time t1 to t2.When input capacitance Ciss charges to voltage value Vcc, (such as time point t2) is connected into driving switch S22, S24, Complete the charging process of input capacitance Ciss.It is constant-current source due to flowing through the electric current on resistance R, when stream in the identical time One timing of electricity of resistance R is crossed, the energy loss of resistance R can be smaller.In addition, the input capacitance Ciss needs when power switch are put When electric, the conducting of driving switch S22, S24 makes the electric current on inductance L reach a definite value L2 close to constant-current source, extremely such as time t2 t3.Then, driving switch S22, S24 is turned off, so that inductance L is provided the electric current input capacitance Ciss close to constant-current source and is discharged to Zero, such as time t3 to t4.When input capacitance Ciss is discharged to zero, (such as time point t4) is connected into driving switch S21, S23, it is complete At the discharge process of input capacitance Ciss.Due to identical as charging process, so the energy loss of resistance R similarly can be smaller.
However, since inductance L needs to provide an approximate constant current in input capacitance Ciss charging, the electric discharge of power switch The electric current in source, therefore sensibility reciprocal needed for inductance L is larger, therefore volume also can be larger.Further, since thering is electric current to deposit always in inductance L So energy loss is still also larger.
Therefore, a kind of driving circuit of power switch that can be solved the above problems how is developed, actually the relevant technologies are led Domain person problem in the urgent need to address at present.
Summary of the invention
A kind of driving circuit for being designed to provide power switch of this case makes the inductance in driving circuit be not required to provide In the case where the electric current of constant-current source, the energy loss of resistance is similarly smaller, in order to solve conventional driving circuit inductance because that need to mention For constant-current source electric current and keep required sensibility reciprocal larger, in turn result in the larger problem of inductance volume.
In order to achieve the above object, a preferable state sample implementation of this case is to provide a kind of driving circuit, switched to driving power, Driving circuit includes: inductance；And an at least driving switch, it is electrically connected with inductance；Wherein, driving circuit and power switch are equivalent At equivalent circuit, equivalent circuit includes: the first equivalent capacity, at least reflects an input capacitance of power switch；Equivalent inductance, packet It is connected in series containing inductance, and with the first equivalent capacity；And second equivalent capacity, the parasitic ginseng of a reflection at least driving switch Number, and be connected in series with the first equivalent capacity and equivalent inductance and form charging and discharging circuit, to pass through charging and discharging circuit to first Equivalent capacity carries out charge or discharge running；It wherein, is zero to defeated from the electric current of inductance in the first equivalent capacity charging process The voltage value for entering capacitor is the first setting voltage value, or in the first equivalent capacity discharge process, from the electric current of inductance be zero to The voltage value of input capacitance is the second setting voltage value, and the charge variation amount in the first equivalent capacity is greater than or equal to from inductance Electric current is the charge variation amount in zero second equivalent capacity when reaching final steady-state value to the voltage value of input capacitance；Wherein, Maximum value in the threshold voltage range for the grid that one setting voltage value is greater than power switch, the second setting voltage value are less than power Minimum value in the threshold voltage range of the grid of switch.
Based on the above-mentioned technical proposal it is found that this case has the technical effect that inductance used in driving circuit is not required to provide The electric current of constant-current source, sensibility reciprocal used in inductance is smaller than the sensibility reciprocal of inductance used in conventional driving circuit, therefore inductance volume Also can be relatively small, and flowing through ohmically loss also can be smaller than the loss of conventional driving circuit.
Detailed description of the invention
Fig. 1 is frequency-drive loss schematic diagram of switch.
Fig. 2 is the drive circuit schematic diagram of traditional power switch.
Fig. 3 is the schematic diagram of currently used metal-oxide half field effect transistor.
Fig. 4 is the drive circuit schematic diagram of another traditional power switch.
Fig. 5 is the timing diagram of driving switch shown in Fig. 4, inductance and input capacitance.
Fig. 6 is the electrical block diagram of the driving circuit of the power switch of this case first embodiment.
Fig. 7 be first embodiment input capacitance in charging process a demonstration example of running corresponding with driving switch when Sequence figure.
Fig. 8 be first embodiment input capacitance in discharge process a demonstration example of running corresponding with driving switch when Sequence figure.
Fig. 9 is the equivalent circuit structure schematic diagram of Fig. 6.
Figure 10 is the electrical block diagram of the driving circuit of the power switch of this case second embodiment.
Figure 11 be second embodiment input capacitance in charging process a demonstration example of running corresponding with driving switch Timing diagram.
Figure 12 is the electrical block diagram of the driving circuit of the power switch of this case 3rd embodiment.
Figure 13 be 3rd embodiment input capacitance during the charging and discharging one operated corresponding with driving switch show The timing diagram of example.
Figure 14 is the electrical block diagram of the driving circuit of the power switch of this case fourth embodiment.
Figure 15 be fourth embodiment input capacitance in charging process a demonstration example of running corresponding with driving switch Timing diagram.
Figure 16 is another demonstration example of input capacitance running corresponding with driving switch in charging process of fourth embodiment Timing diagram.
Figure 17 is the electrical block diagram of the driving circuit of the power switch of the 5th embodiment of this case.
Figure 18 be the 5th embodiment input capacitance in charging process a demonstration example of running corresponding with driving switch Timing diagram.
Figure 19 is the electrical block diagram of the driving circuit of the power switch of this case sixth embodiment.
Figure 20 be sixth embodiment input capacitance in discharge process a demonstration example of running corresponding with driving switch Timing diagram.
Figure 21 is the electrical block diagram of the driving circuit of the power switch of the 7th embodiment of this case.
Figure 22 be the 7th embodiment input capacitance in charging process a demonstration example of running corresponding with driving switch Timing diagram.
Figure 23 be the 7th embodiment input capacitance in discharge process a demonstration example of running corresponding with driving switch Timing diagram.
Figure 24 is the electrical block diagram of the driving circuit of the power switch of the 8th embodiment of this case.
Figure 25 be the 8th embodiment input capacitance during the charging and discharging one operated corresponding with driving switch show The timing diagram of example.
Figure 26 is the electrical block diagram of the driving circuit of the power switch of the 9th embodiment of this case.
Figure 27 be the 9th embodiment input capacitance in charging process a demonstration example of running corresponding with driving switch Timing diagram.
Figure 28 is the electrical block diagram of the driving circuit of the power switch of the tenth embodiment of this case.
Figure 29 is the electrical block diagram of the driving circuit of the power switch of the 11st embodiment of this case.
Figure 30 is the electrical block diagram of the driving circuit of the power switch of the 12nd embodiment of this case.
Figure 31 is a demonstration example of input capacitance running corresponding with driving switch in charging process of the 12nd embodiment Timing diagram.
Figure 32 is a demonstration example of input capacitance running corresponding with driving switch in discharge process of the 12nd embodiment Timing diagram.
Figure 33 is the electrical block diagram of the driving circuit of the power switch of the 13rd embodiment of this case.
Figure 34 is a demonstration example of input capacitance running corresponding with driving switch in charging process of the 13rd embodiment Timing diagram.
Figure 35 is a demonstration example of input capacitance running corresponding with driving switch in discharge process of the 13rd embodiment Timing diagram.
Specific embodiment
The some exemplary embodiments for embodying this case features and advantages will describe in detail in the explanation of back segment.It should be understood that This case can have various variations in different aspects, all not depart from the range of this case, and explanation therein and attached drawing It is illustrated as being used in itself, not for limitation this case.
The driving circuit of this case is switched to driving power, and includes inductance, at least a driving switch and resistance, wherein Inductance, at least a driving switch and resistance are electrically connected to each other, and an at least driving switch has parasitic parameter.
Fig. 6 is the electrical block diagram of the driving circuit of the power switch of this case first embodiment.In this present embodiment, Driving circuit 1 includes inductance L31, the first driving switch S31, the second driving switch S32 and resistance R, and capacitor Ciss is function Rate switchs the input capacitance of (not shown).The first end of first driving switch S31 is electrically connected with input source, the first driving switch The second end of S31 is electrically connected with the first end of the first end of the second driving switch S32 and inductance L31, the second driving switch S32's Second end is electrically connected with ground terminal, and the second end of inductance L31 is electrically connected with the first end of resistance R, the second end and input of resistance R Capacitor Ciss electrical connection.In addition, in this present embodiment, the first driving switch S31 and the second driving switch S32 can actually have Parasitic parameter is respectively the first parasitic capacitance Coss31 and the second parasitic capacitance Coss32.
The charging and discharging of input capacitance Ciss further described below operate.In this present embodiment, driving circuit 1 is logical Cross the first driving switch S31 and the second driving switch S32 on or off running come control input capacitance Ciss charging and Electric discharge.
Please refer to Fig. 7 and cooperate Fig. 6, Fig. 7 be first embodiment input capacitance in charging process with driving switch pair The timing diagram for the demonstration example that should be operated.When input capacitance Ciss need to be charged, the first driving switch S31 in time t0 extremely T1 conducting, makes the electric energy of input source charge by the first driving switch S31 to inductance L31 and input capacitance Ciss.Second Driving switch S32 in time t0 to t1 terminate and the first driving switch S31 end when (i.e. when time point t1) be connected, make inductance The current discharge of L31 makes input capacitance Ciss continue to charge to input capacitance Ciss.Second driving switch S32 is in inductance End (i.e. when time point t2) when the electric current of L31 is zero, so that input capacitance Ciss is charged to voltage value Vp1, wherein voltage value Vp1 The voltage value Vcc of input source need to be less than, otherwise the energy in input capacitance Ciss can fill back input source again, so that charge efficiency Decline.In time point t2, due to the charging process of above-mentioned driving circuit 1, the first parasitic capacitance Coss31 charges to voltage value Vcc, and the voltage value of the second parasitic capacitance Coss32 is zero.When time t2 to t3, the first parasitic capacitance Coss31 and second Parasitic capacitance Coss32 can carry out resonance by inductance L31 and input capacitance Ciss, make the voltage value Vp1 of input capacitance Ciss A final steady-state value Vo can be reached, and the voltage meeting resonance on the second parasitic capacitance Coss32 is extremely equal with input capacitance Ciss Final steady-state value Vo, the voltage value Vcc of the first parasitic capacitance Coss31 then can resonance to voltage value Vcc-Vo.Due to input capacitance The second parasitic capacitance Coss32 of the first parasitic capacitance Coss31 of Ciss and the first driving switch S31, the second driving switch S32 For series relationship, therefore when time t2 to t3, electricity that input capacitance Ciss is released from voltage value Vp1 to final steady-state value Vo Lotus can be equal to the first parasitic capacitance Coss31 and change to Vcc-Vo and the second parasitic capacitance Coss32 from voltage value from voltage value Vcc Zero changes to the sum of charge of Vo Q1.The voltage value on input capacitance Ciss needed due to power switch is reaching final stable state Being higher than the first setting voltage value VH when value Vo, (VH is greater than in specifications in a threshold voltage range of the grid of power switch most Big value Vmax), to guarantee that power switch conduction impedance in the on-state or conduction voltage drop are lower, so in time t2 to t3 When, input capacitance Ciss need to be greater than or equal to defeated from the charge variation amount Q2 that voltage value Vp1 changes to the first setting voltage value VH Enter the first parasitic capacitance Coss31 and the second parasitic capacitance when capacitor Ciss changes to final steady-state value Vo from voltage value Vp1 The charge variation amount Q1 of Coss32.Therefore, following equation (1) to (3) is met in input capacitance Ciss charging process:
Q1=Coss31*Vo+Coss32*Vo (1)
Q2=Ciss* (Vp1-VH) (2)
Q1≦Q2 (3)
In above-described embodiment, driving circuit 1 forms oscillating circuit (when time t2 to t3) when due to resonance, if concussion When resistance R is larger in circuit, i.e., oscillating circuit is overdamp concussion, and the voltage value of input capacitance Ciss just will not shake final Steady-state value Vo is hereinafter, as shown in solid in Fig. 7.If resistance R is smaller in oscillating circuit, i.e., oscillating circuit is underdamping concussion, The voltage value of input capacitance Ciss can using final steady-state value Vo as median sustained oscillation several periods after stablize in final stable state Value Vo, as shown in phantom in Figure 7.The input capacitance Ciss of power switch needs to be higher than voltage value Vmax (i.e. when circuit shakes Maximum value in specifications in the threshold voltage ranges of the grid of power switch), to prevent power switch in turn on process Accidentally turn off, thus it is smaller in resistance R and when oscillating circuit being made to have multiple concussion, the final steady-state value Vo needed need to be greater than 0.5* (Vp1+Vmax).Preferable resistance R's is selected as critical resistance of the oscillating circuit between underdamping concussion and overdamp concussion Buddhist nun's state.
Please refer to Fig. 8 and cooperate Fig. 6, Fig. 8 be first embodiment input capacitance in discharge process with driving switch pair The timing diagram for the demonstration example that should be operated.When input capacitance Ciss need to be discharged, the second driving switch S32 in time t4 extremely T5 conducting, make input capacitance Ciss by inductance L31 discharge inductance L31 electric current increase.Second driving switch S32 is in inductance End (i.e. when time point t5) when the electric current of L31 increases to certain value, and the first driving switch S31 connects conducting, makes input electricity Hold Ciss and is gradually reduced by inductance L31 to the electric current of input source electric discharge inductance L31, it is corresponding such as time t5 to t6.First drives Dynamic switch S31 also ends (i.e. when time point t6) when the electric current of inductance L31 is zero, and input capacitance Ciss is made to be discharged to voltage value Vp2.In time point t6, due to the discharge process of above-mentioned driving circuit 1, the voltage value of the first parasitic capacitance Coss31 is zero, And the second parasitic capacitance Coss32 charges to voltage value Vcc.When time t6 to t7, the first parasitic capacitance Coss31 and second is posted Raw capacitor Coss32 can carry out resonance by inductance L31 and input capacitance Ciss, make the voltage value Vp2 meeting of input capacitance Ciss Reach a final steady-state value Vo, and voltage on the second parasitic capacitance Coss32 can resonance to it is equal with input capacitance Ciss most Whole steady-state value Vo, the voltage value of the first parasitic capacitance Coss31 then can resonance to voltage value Vcc-Vo.Due to input capacitance Ciss It is string with the first parasitic capacitance Coss31 of the first driving switch S31, the second parasitic capacitance Coss32 of the second driving switch S32 Connection relationship, therefore when time t6 to t7, the charge meeting that input capacitance Ciss is filled with from voltage value Vp2 to final steady-state value Vo Voltage value Vcc-Vo and the second parasitic capacitance Coss32 are changed to from voltage from voltage value zero equal to the first parasitic capacitance Coss31 Value Vcc changes to the sum of charge of Vo Q3.The voltage value on input capacitance Ciss needed due to power switch is reaching final Lower than the second setting voltage value VL, (VL is less than in specifications in a threshold voltage range of the grid of power switch when steady-state value Vo Minimum value Vmin), to guarantee that the conduction impedance of power switch in the off case is higher or leakage current is smaller, so in the time When t6 to t7, input capacitance Ciss need to be greater than from the charge variation amount Q4 that voltage value Vp2 changes to the second setting voltage value VL or The parasitic electricity of first parasitic capacitance Coss31 and second when changing to final steady-state value Vo from voltage value Vp2 equal to input capacitance Ciss Hold the charge variation amount Q3 of Coss32.Therefore, following equation (4) to (6) are met in input capacitance Ciss discharge process:
Q3=(Coss31+Coss32) * (Vcc-Vo) (4)
Q4=Ciss* (Vp2-VL) (5)
Q3≦Q4 (6)
In above-described embodiment, the preferred plan of voltage value Vp2 is zero.If the turn-on time mistake of the first driving switch S31 Long, input capacitance Ciss meeting reverse charging makes voltage value Vp2 less than zero, and then make the concussion width of voltage on input capacitance Ciss It spends greatly, and increases loss.Further, since driving circuit 1 forms oscillating circuit (when time t6 to t7) when resonance, if concussion When resistance R is larger in circuit, i.e., oscillating circuit is overdamp concussion, and the voltage value of input capacitance Ciss just will not shake final Steady-state value Vo or more, as shown in solid in Fig. 8.If resistance R is smaller in oscillating circuit, i.e., oscillating circuit is underdamping concussion, The voltage value of input capacitance Ciss can using final steady-state value Vo as median sustained oscillation several periods after stablize in final stable state Value Vo, as shown in phantom in Figure 8.The input capacitance Ciss of power switch is needed when circuit shakes lower than voltage value Vmin (i.e. Minimum value in specifications in the threshold voltage ranges of the grid of power switch), to prevent power switch in turn off process Mislead, thus it is smaller in resistance R and when oscillating circuit being made to have multiple concussion, the final steady-state value Vo needed need to be less than 0.5* (Vp2+Vmin).Preferable resistance R's is selected as critical resistance of the oscillating circuit between underdamping concussion and overdamp concussion Buddhist nun's state.
Since the input capacitance Ciss of the driving circuit 1 of this case meets corresponding formula in charge and discharge process, drive Inductance L31 used in dynamic circuit 1 is just not required to provide the electric current of constant-current source, in this way, which sensibility reciprocal used in inductance L31 can compare The sensibility reciprocal of inductance used in conventional driving circuit is small, therefore inductance volume also can be relatively small, and flows through the electricity of same charge The loss hindered on R also can be smaller than the loss of conventional driving circuit.In addition, inductance L31 can be only for entity in some embodiments Vertical inductance can also be formed by parasitic inductance with the input capacitance Ciss connecting line connecting for driving switch.
Fig. 9 is the equivalent circuit structure schematic diagram of Fig. 6.As shown in figure 9, equivalent circuit 2 include the first equivalent capacity Ci, etc. Imitate inductance L, equivalent resistance R1 and the second equivalent capacity Coss.The input capacitance of first equivalent capacity Ci reflection power switch Ciss, and equivalent inductance L includes inductance L31, equivalent resistance R1 includes resistance R, and is connected in series with the first equivalent capacity Ci.This Outside, the second equivalent capacity Coss reflects the parasitic parameter of an at least driving switch, such as in this present embodiment, and at least one driving is opened The second of first parasitic capacitance Coss31 and second driving switch S32 of the parasitic parameter of pass comprising the first driving switch S31 is posted Raw capacitor Coss32.Second equivalent capacity Coss actually reflect the first parasitic capacitance Coss31 of the first driving switch S31 with And second driving switch S32 the second parasitic capacitance Coss32, and with the first equivalent capacity Ci, equivalent inductance L and equivalent resistance R1 is connected in series and forms a charging and discharging circuit, i.e. equivalent circuit 2, with by the charging and discharging circuit to the first equivalent capacity Ci into The running of row charge or discharge.
Therefore, the refresh operations of aforementioned driving circuit 1 are cooperated according to above-mentioned equivalent circuit 2 it is found that in the first equivalent capacity In Ci charging process, input capacitance Ciss is changed to from the voltage value Vp1 (i.e. when the electric current of inductance is zero) of input capacitance Ciss Voltage value be the first setting voltage value VH, the charge variation amount Q2 of the first equivalent capacity Ci is greater than or equal to from input capacitance The voltage value that the voltage value Vp1 (i.e. when the electric current of inductance is zero) of Ciss changes to input capacitance Ciss reaches final steady-state value Vo When the second equivalent capacity Coss charge variation amount Q1.In addition, cooperating putting for aforementioned driving circuit 1 according to above-mentioned equivalent circuit 2 Electricity running is it is found that in the first equivalent capacity Ci discharge process, from voltage value Vp2 (the i.e. electric current of inductance of input capacitance Ciss When being zero) voltage value of input capacitance Ciss is changed to as the second setting voltage value VL, the charge variation of the first equivalent capacity Ci Amount Q4, which is greater than or equal to from the voltage value Vp2 (i.e. when the electric current of inductance is zero) of input capacitance Ciss, changes to input capacitance Ciss Voltage value second equivalent capacity Coss when reaching final steady-state value Vo charge variation amount Q3.
Figure 10 is the electrical block diagram of the driving circuit of the power switch of this case second embodiment.As shown in Figure 10, The framework of the driving circuit 1A of the present embodiment is similar to element function to embodiment illustrated in fig. 6, and identical element numbers represent Identical structure, element and function, repeat no more in this.Compared to driving circuit 1 shown in fig. 6, the driving electricity of the present embodiment Road 1A and driving circuit 1 shown in fig. 6 the difference is that, the driving circuit 1A of the present embodiment further includes third driving switch S33, wherein third driving switch S33 has third parasitic capacitance Coss33, and the first end electrical connection of third driving switch S33 Between the second end of inductance L31 and the first end of resistance R, the second end of third driving switch S33 is electrically connected with ground terminal.
In this present embodiment, driving circuit 1A can also be equivalent to the equivalent circuit 2 such as Fig. 9, so equivalent with driving circuit 1 The difference is that, the first equivalent capacity Ci also include reflect power switch input capacitance Ciss and reflection third driving switch The third parasitic capacitance Coss33 of S33.
It please refers to Figure 11 and cooperates Fig. 9 and Figure 10, wherein Figure 11 is the input capacitance of second embodiment in charging process The timing diagram of one demonstration example of running corresponding with driving switch.Compared to the charging process of first embodiment, the drive of the present embodiment Dynamic circuit 1A is operated again by the on or off of the first driving switch S31 and the second driving switch S32 and is controlled and input The charging of capacitor Ciss, the difference is that, driving circuit 1A is to control input capacitance by the conducting of third driving switch S33 The electric discharge of Ciss, in other words, third driving switch S33 are maintained at mono- section of final steady-state value Vo in the voltage value of input capacitance Ciss It is connected after time, i.e. when time point t3 ' is connected, so that the voltage value of input capacitance Ciss drops to zero, accelerates power switch (not Diagram) turn-off speed.Since the first equivalent capacity Ci of the present embodiment is by input capacitance Ciss's and third driving switch S33 Third parasitic capacitance Coss33 institute is equivalent, therefore the first equivalent capacity Ci of the present embodiment meets following equation during the charging process (7) to (9):
Q1=(Coss31+Coss32) * Vo (7)
Q2=(Ciss+Coss33) * (Vp1-VH) (8)
Q1≦Q2 (9)
Figure 12 is the electrical block diagram of the driving circuit of the power switch of this case 3rd embodiment.As shown in figure 12, The framework of the driving circuit 1B of the present embodiment is similar to element function to embodiment illustrated in fig. 6, and identical element numbers represent Identical structure, element and function, repeat no more in this.Compared to driving circuit 1 shown in fig. 6, the driving electricity of the present embodiment Road 1B and driving circuit 1 shown in fig. 6 the difference is that, the driving circuit 1B of the present embodiment further includes the first clamp circuit C35 and the second clamp circuit C34.First clamp circuit C35 has third parasitic capacitance Coss35, the second clamp circuit C34 tool There is the 4th parasitic capacitance Coss34, wherein the first end of the first end of the first clamp circuit C35 and the first driving switch S31 and defeated Enter source electrical connection, the second end of the second end of the first clamp circuit C35 and inductance L31, the first end of the second clamp circuit C34 and The first end of resistance R is electrically connected, and the second end of the second clamp circuit C34 is electrically connected with ground terminal.
In this present embodiment, driving circuit 1B can also be equivalent to the equivalent circuit 2 such as Fig. 9, so equivalent with driving circuit 1 The difference is that, the first equivalent capacity Ci also include reflect power switch input capacitance Ciss, reflection the first clamp circuit C35 Third parasitic capacitance Coss35 and reflect the second clamp circuit C34 the 4th parasitic capacitance Coss34.
It please refers to Figure 13 and cooperates Fig. 9 and Figure 12, wherein Figure 13 is the input capacitance of 3rd embodiment in charging and discharging The timing diagram of a demonstration example of running corresponding with driving switch in the process.Compared to the charging and discharging process of first embodiment, The present embodiment and first embodiment the difference is that, the first clamp circuit C35 in input capacitance Ciss charging process for inputting The voltage value of clamper input capacitance Ciss is to be somebody's turn to do (in time t1 ' to t2) when the voltage value of capacitor Ciss is higher than an overvoltage value Overvoltage value, wherein the overvoltage value is voltage value Vcc in this present embodiment, and in other words, input capacitance Ciss is in charging process Middle voltage value Vp1 can be very close to voltage value Vcc.And the second clamp circuit S34 is for defeated in input capacitance Ciss discharge process The voltage value of clamper input capacitance Ciss is (in time t5 ' to t6) when entering the voltage value of capacitor Ciss lower than a under-voltage value The under-voltage value, wherein the under-voltage value is zero in this present embodiment, in other words, input capacitance Ciss voltage during discharge Value Vp2 can very close to zero, in this way, in input capacitance Ciss charging process, the second driving switch S32 time t1 extremely T2 does not just need to accurately control when being connected, and in input capacitance Ciss discharge process, the first driving switch S31 is in time t5 It does not need equally to accurately control when being connected to t6 yet.Due to the present embodiment the first equivalent capacity Ci by input capacitance Ciss, The 4th parasitic capacitance Coss34 institute of the third parasitic capacitance Coss35 of first clamp circuit C35 and the second clamp circuit C34 It is equivalent, therefore the first equivalent capacity Ci of the present embodiment meets following equation (10) to (12) during the charging process:
Q1=(Coss31+Coss32) * Vo (10)
Q2=(Ciss+Coss34+Coss35) * (Vp1-VH) (11)
Q1≦Q2 (12)
And the first equivalent capacity Ci meets following equation (13) to (15) during discharge:
Q3=(Coss31+Coss32) * (Vcc-Vo) (13)
Q4=(Ciss+Coss34+Coss35) * (Vp2-VL) (14)
Q3≦Q4 (15)
Figure 14 is the electrical block diagram of the driving circuit of the power switch of this case fourth embodiment.As shown in figure 14, The framework of the driving circuit 1C of the present embodiment is similar to element function to embodiment illustrated in fig. 6, and identical element numbers represent Identical structure, element and function, repeat no more in this.Compared to driving circuit 1 shown in fig. 6, the driving electricity of the present embodiment Road 1C and driving circuit 1 shown in fig. 6 the difference is that, the driving circuit 1C of the present embodiment further includes the first clamp circuit C35 and third driving switch S33.First clamp circuit C35 has third parasitic capacitance Coss35, third driving switch S33 tool There is the 4th parasitic capacitance Coss33, wherein the first end of the first end of the first clamp circuit C35 and the first driving switch S31 and defeated Enter source electrical connection, the second end of the second end of the first clamp circuit C35 and inductance L31, the first end of third driving switch S33, The first end of resistance R is electrically connected, and the second end of third driving switch S33 is electrically connected with ground terminal.
In this present embodiment, driving circuit 1C can also be equivalent to the equivalent circuit 2 such as Fig. 9, so equivalent with driving circuit 1 The difference is that, the first equivalent capacity Ci also include reflect power switch input capacitance Ciss, reflection the first clamp circuit C35 Third parasitic capacitance Coss35 and reflect third driving switch S33 the 4th parasitic capacitance Coss33.
It please refers to Figure 15 and cooperates Fig. 9 and Figure 14, wherein Figure 15 is the input capacitance of fourth embodiment in charging process The timing diagram of one demonstration example of running corresponding with driving switch.Compared to the charging and discharging process of first embodiment, this implementation Example with first embodiment the difference is that, the first clamp circuit C35 be used for input capacitance Ciss charging process in input capacitance The voltage value of clamper input capacitance Ciss is that this is excessively electric (in time t1 ' to t2) when the voltage value of Ciss is higher than an overvoltage value Pressure value, wherein the overvoltage value is voltage value Vcc in this present embodiment, and in other words, input capacitance Ciss is electric during the charging process Pressure value Vp1 can be very close to voltage value Vcc.And third driving switch S33 is maintained at finally in the voltage value of input capacitance Ciss Steady-state value Vo is connected afterwards for a period of time, i.e. when time point t3 ' is connected, so that the voltage value of input capacitance Ciss drops to zero, adds The turn-off speed of fast power switch (not shown).Since the first equivalent capacity Ci of the present embodiment is by input capacitance Ciss, first The 4th parasitic capacitance Coss33 institute of the third parasitic capacitance Coss35 and third driving switch S33 of clamp circuit C35 are equivalent, Therefore the first equivalent capacity Ci of the present embodiment meets following equation (16) to (18) during the charging process:
Q1=(Coss31+Coss32) * Vo (16)
Q2=(Ciss+Coss33+Coss35) * (Vp1-VH) (17)
Q1≦Q2 (18)
Please refer to Figure 16 and cooperate Figure 14, wherein Figure 16 be fourth embodiment input capacitance in charging process with driving The timing diagram of another demonstration example of the corresponding running of switch.Compared to the charging process of fourth embodiment shown in figure 15, this implementation Example and previous embodiment the difference is that, when input capacitance Ciss need to be charged, the first driving switch S31 and third are driven Switch S33 is connected in time t0 to t1, drives the electric energy of input source by the first driving switch S31, inductance L31 and third Switch S33 is formed by circuit and charges to inductance L31, so that the electric current of inductance L31 is precharged to preset value.Second drives Dynamic switch S32 terminates and (i.e. time point t1 when the first driving switch S31 and third driving switch S33 cut-off in time t0 to t1 When) conducting, make the current discharge of inductance L31 to input capacitance Ciss.At this point, due to the electric current of inductance L31 be charged in advance it is pre- If value and can provide biggish charging current to input capacitance Ciss, therefore input capacitance Ciss can be obtained in this charging process Obtain faster charging rate.And the present embodiment is identical in the charging process of time t1 to t3 and the charging process of first embodiment, Therefore it is repeated no more in this.
Figure 17 is the electrical block diagram of the driving circuit of the power switch of the 5th embodiment of this case.As shown in figure 17, The framework of the driving circuit 1D of the present embodiment is similar to the embodiment of driving circuit shown in Figure 14 to element function and identical Element numbers represent identical structure, element and function, repeat no more in this.Compared to driving circuit 1C shown in Figure 14, originally Driving circuit 1C shown in the driving circuit 1D and Figure 14 of embodiment the difference is that, the driving circuit 1D of the present embodiment is also wrapped Direct current clamp power supply Vclamp is included, and the first end of the first clamp circuit C35 is changed to be electrically connected with direct current clamp power supply Vclamp.
Please refer to Figure 18 and cooperate Figure 17, wherein Figure 18 be the 5th embodiment input capacitance in charging process with driving The timing diagram of one demonstration example of the corresponding running of switch.Compared to the charging process of fourth embodiment, the present embodiment and the 4th is implemented Example the difference is that, direct current clamps voltage value of the power supply Vclamp for input capacitance Ciss in input capacitance Ciss charging process The voltage value of clamper input capacitance Ciss is the overvoltage value (in time t1 ' to t2) when higher than an overvoltage value, wherein should Overvoltage value is the voltage value of direct current clamp power supply Vclamp in this present embodiment, and in other words, input capacitance Ciss was charging Voltage value can clamp the voltage value of power supply Vclamp very close to direct current in journey.
Figure 19 is the electrical block diagram of the driving circuit of the power switch of this case sixth embodiment.The drive of the present embodiment The framework of dynamic circuit 1E is similar to the embodiment of driving circuit shown in Figure 17 to element function, and identical element numbers represent phase Same structure, element and function, repeats no more in this.Compared to driving circuit 1D shown in Figure 17, the driving electricity of the present embodiment Driving circuit 1D shown in road 1E and Figure 17 the difference is that, the driving circuit 1E of the present embodiment is by the first clamp circuit S35 It is replaced into the 4th driving switch S35.
Please refer to Figure 20 and cooperate Figure 19, wherein Figure 20 be sixth embodiment input capacitance in discharge process with driving The timing diagram of one demonstration example of the corresponding running of switch.When input capacitance Ciss need to be discharged, the second driving switch S32 and Four driving switch S35 in time t0 to t1 be connected, make direct current clamp power supply Vclamp electric energy by the 4th driving switch S35, Inductance L31 and the second driving switch S32 is formed by circuit and charges to inductance L31, so that the electric current of inductance L31 is preparatory Charge to preset value.First driving switch S31 terminates and the second driving switch S32 and the 4th driving switch in time t0 to t1 It is connected (when time point t1) when S35 ends, makes the current discharge of input capacitance Ciss to input source.At this point, due to inductance L31 Electric current be charged to preset value in advance, therefore input capacitance Ciss can obtain the faster velocity of discharge in this discharge process. In addition, third driving switch S33 (time t1 ') when the tension discharge of input capacitance Ciss is to zero is connected, inputted with clamper The voltage value of capacitor Ciss is zero.
Figure 21 is the electrical block diagram of the driving circuit of the power switch of the 7th embodiment of this case.In the present embodiment In, driving circuit 2A includes inductance L41, the first driving switch S41, the second driving switch S42 and resistance R, and capacitor Ciss For the input capacitance of power switch (not shown).The first end of inductance L41 is electrically connected with input source, the second end of inductance L41 with The first end of first driving switch S41 and the electrical connection of the first end of the second driving switch S42, the second of the second driving switch S42 End is electrically connected with the first end of resistance R, and the second end of resistance R is electrically connected with input capacitance Ciss, and the of the first driving switch S41 Two ends are electrically connected with ground terminal.In addition, in this present embodiment, the first driving switch S41 and the second driving switch S42 actually can It is respectively the first parasitic capacitance Coss41 and the second parasitic capacitance Coss42 with parasitic parameter.
The charging and discharging of the input capacitance Ciss of the present embodiment further described below operate.Driving circuit 2A passes through The on or off of first driving switch S41 and the second driving switch S42 operate to control the charging of input capacitance Ciss and put Electricity.
Please refer to Figure 22 and cooperate Figure 21, Figure 22 be the 7th embodiment input capacitance in charging process with driving switch The timing diagram of one demonstration example of corresponding running.When input capacitance Ciss need to be charged, the first driving switch S41 is in time t0 It is connected to t1, the electric energy of input source is made to charge by the first driving switch S41 be connected to inductance L41.Second driving is opened Close S42 in time t0 to t1 terminate and the first driving switch S41 end when (i.e. when time point t1) be connected, make the electricity of inductance L41 Stream is discharged to input capacitance Ciss, and then input capacitance Ciss is made to charge.Second driving switch S42 is in the electric current of inductance L41 When zero (when time point t2) end, so that input capacitance Ciss is charged to voltage value Vp1, and at this time voltage value Vp1 can be higher than it is defeated Enter the voltage value Vcc in source.In time point t2, due to the charging process of above-mentioned driving circuit 2A, the first parasitic capacitance Coss41 Voltage value Vp1 identical with input capacitance Ciss is charged to, and the voltage value of the second parasitic capacitance Coss42 is zero.In time t2 When to t3, the second parasitic capacitance Coss42 can carry out resonance by inductance L41 and input capacitance Ciss, make input capacitance Ciss Voltage value Vp1 can reach a final steady-state value Vo, wherein final steady-state value Vo can be more than or equal to voltage value Vcc, and second is posted Voltage on raw capacitor Coss42 then can resonance to equal than final steady-state value Vo and voltage value Vcc on input capacitance Ciss electricity Pressure difference, the voltage of the first parasitic capacitance Coss41 are voltage value Vcc.Due to input capacitance Ciss's and the second driving switch S42 Parasitic capacitance Coss42 is series relationship, therefore when time t2 to t3, input capacitance Ciss is from voltage value Vp1 to final stable state The charge that value Vo is released can be equal to the charge Q 1 that the second parasitic capacitance Coss42 changes to Vcc-Vo from voltage value zero.Due to function The voltage value on input capacitance Ciss that rate switch needs is higher than the first setting voltage value VH, institute when reaching final steady-state value Vo With in time t2 to t3, input capacitance Ciss changes to the charge variation amount Q2 of the first setting voltage value VH from voltage value Vp1 The electricity of the second parasitic capacitance Coss42 when input capacitance Ciss changes to final steady-state value Vo from voltage value Vp1 need to be greater than or equal to Lotus variable quantity Q1.Therefore, following equation (19) to (21) are met in input capacitance Ciss charging process:
Q1=Coss42* (Vo-Vcc) (19)
Q2=Ciss* (Vp1-VH) (20)
Q1≦Q2 (21)
Please refer to Figure 23 and cooperate Figure 21, Figure 23 be the 7th embodiment input capacitance in discharge process with driving switch The timing diagram of one demonstration example of corresponding running.When input capacitance Ciss need to be discharged, the second driving switch S42 is in time t4 It is connected to t5, increases input capacitance Ciss to the electric current of input source electric discharge inductance L41 by inductance L41.Second driving is opened It closes S42 to end (i.e. when time point t5) when the electric current of inductance L41 increases to certain value, and the first driving switch S41 connecting is led It is logical, make inductance L41 continue to discharge to input source, the voltage value of input capacitance Ciss is down to voltage value Vp2 because of electric discharge at this time, right It should be such as time t5 to t6.First driving switch S41 more ends (i.e. when time point t6) when the electric current of inductance L41 is zero.When Between point t6 when, since the discharge process of above-mentioned driving circuit 2A can make the first parasitic capacitance Coss41 be discharged to zero, and second The voltage value of parasitic capacitance Coss42 is Vp2, therefore when time t6 to t7, the second parasitic capacitance Coss42 can pass through inductance L41 and with input capacitance Ciss carry out resonance, make the voltage value Vp2 of input capacitance Ciss that can reach a final steady-state value Vo, and The final steady-state value Vo's of voltage meeting resonance to equal than voltage value Vcc and input capacitance Ciss on second parasitic capacitance Coss42 Voltage difference, the voltage on the first parasitic capacitance Coss41 are voltage value Vcc.Due to input capacitance Ciss and the second driving switch The second parasitic capacitance Coss42 of S42 is series relationship, therefore when time t6 to t7, input capacitance Ciss is from voltage value Vp2 The charge being filled with to final steady-state value Vo can be equal to the electricity that the second parasitic capacitance Coss42 changes to Vcc-Vo from voltage value Vp2 Lotus Q3.The voltage value on input capacitance Ciss needed due to power switch is when reaching final steady-state value Vo lower than the second setting Voltage value VL, so input capacitance Ciss changes to the electricity of the second setting voltage value VL from voltage value Vp2 in time t6 to t7 Lotus variable quantity Q4 need to be greater than or equal to the second parasitic capacitance when input capacitance Ciss changes to final steady-state value Vo from voltage value Vp2 The charge variation amount Q3 of Coss42.Therefore, following equation (22) to (24) are met in input capacitance Ciss discharge process:
Q3=Coss42* (Vp2+Vcc-Vo) (22)
Q4=Ciss* (Vp2-VL) (23)
Q3≦Q4 (24)
In above-described embodiment, the MOSFET of body diode in parallel is can also be used in the first driving switch S41, can be reduced The control difficulty of first driving switch S41 when input capacitance Ciss discharges, wherein the second driving switch S42 must use two-way opened Close, if only using the MOSFET for individually having body diode in parallel, input capacitance Ciss electric discharge after the completion of can be recharged to Voltage value is more than or equal to the state of voltage value Vcc.In addition, the preferred plan of voltage value Vp2 in this present embodiment is zero.If second Driving switch S42 turn-on time is too long, and the body second level body conducting of the first driving switch S41 or input capacitance Ciss can be made reversely to fill Electricity, and make voltage value Vp2 less than zero, cause the shock range of voltage on input capacitance Ciss excessive, and increase loss.
The driving circuit 2A of the present embodiment can also be equivalent to the equivalent circuit 2 such as Fig. 9, wherein the first equivalent capacity Ci reflects The input capacitance Ciss of power switch, equivalent inductance L include the inductance L41 of driving circuit 2A, and the second equivalent capacity Coss is anti- Reflect the second parasitic capacitance Coss42 of the second driving switch S42.
Figure 24 is the electrical block diagram of the driving circuit of the power switch of the 8th embodiment of this case.As shown in figure 24, The framework of the driving circuit 2B of the present embodiment is similar to element function to embodiment illustrated in fig. 21, and identical element numbers represent Identical structure, element and function, repeat no more in this.Compared to driving circuit 2A shown in Figure 21, the driving of the present embodiment Driving circuit 2A shown in circuit 2B and Figure 21 the difference is that, the driving circuit 2B of the present embodiment further includes that third driving is opened It closes S43 and direct current clamps power supply Vclamp, wherein third driving switch S43 has third parasitic capacitance Coss43, third driving The first end of switch S43 is electrically connected between the second end of the second driving switch S42 and the first end of resistance R, and direct current clamps Power supply Vclamp is connected between the second end and ground terminal of third driving switch S43.
In this present embodiment, driving circuit 2B can also be equivalent to the equivalent circuit 2 such as Fig. 9, so with driving circuit 2A etc. Effect the difference is that, the first equivalent capacity Ci reflect power switch input capacitance Ciss and reflection third driving switch S43 Third parasitic capacitance Coss43.
It please refers to Figure 25 and cooperates Fig. 9 and Figure 24, wherein Figure 25 is the input capacitance of the 8th embodiment in charging and discharging The timing diagram of a demonstration example of running corresponding with driving switch in the process.Compared to the charging process of the 7th embodiment, this implementation The driving circuit 2B of example makes direct current clamp power supply Vclamp release electric energy in charging by the conducting of third driving switch S43 It charges to input capacitance Ciss, corresponding such as time to t1, in this way, which the charging rate of input capacitance Ciss can be promoted. And discharge process is identical as the 7th embodiment that therefore, not repeat them here.Since the first equivalent capacity Ci of the present embodiment is by input capacitance The third parasitic capacitance Coss43 institute of Ciss and third driving switch S43 is equivalent, therefore the first equivalent capacity Ci of the present embodiment Meet following equation (25) to (27) during discharge:
Q3=Coss42* (Vp2+Vcc-Vo) (25)
Q4=(Ciss+Coss43) * (Vp2-VL) (26)
Q3≦Q4 (27)
Figure 26 is the electrical block diagram of the driving circuit of the power switch of the 9th embodiment of this case.As shown in figure 26, The framework of the driving circuit 2C of the present embodiment is similar to element function to embodiment illustrated in fig. 21, and identical element numbers represent Identical structure, element and function, repeat no more in this.Compared to driving circuit 2A shown in Figure 21, the driving of the present embodiment Driving circuit 2A shown in circuit 2C and Figure 21 the difference is that, the driving circuit 2C of the present embodiment further includes the first clamper electricity Road C43 and direct current clamp power supply Vclamp, wherein the first clamp circuit C43 has third parasitic capacitance Coss43, the first clamper The first end of circuit C43 is electrically connected between the second end of the second driving switch S42 and the first end of resistance R, direct current clamp electricity Source Vclamp is electrically connected between the second end and ground terminal of the first clamp circuit C43.
In this present embodiment, driving circuit 2C can also be equivalent to the equivalent circuit 2 such as Fig. 9, so with driving circuit 2A etc. Effect the difference is that, the first equivalent capacity Ci reflect power switch input capacitance Ciss and reflection the first clamp circuit C43 Third parasitic capacitance Coss43.
It please refers to Figure 27 and cooperates Fig. 9 and Figure 26, wherein Figure 27 is the input capacitance of the 9th embodiment in charging process The timing diagram of one demonstration example of running corresponding with driving switch.Compared to the charging process of the 7th embodiment, the present embodiment and The charging processes of seven embodiments the difference is that, the first clamp circuit C43 of the driving circuit 2C of the present embodiment is in input capacitance (in time t1 ' when the voltage value of input capacitance Ciss is higher than the voltage value of direct current clamp power supply Vclamp in Ciss charging process When to t2) voltage value of clamper input capacitance Ciss is voltage value that direct current clamps power supply Vclamp, makes on input capacitance Ciss Voltage will not Yin Taigao and damage power switch, thus also reduce charging process in the second driving switch S42 control difficulty. Due to the present embodiment the first equivalent capacity Ci by input capacitance Ciss and the first clamp circuit C43 third parasitic capacitance Coss43 institute is equivalent, therefore the first equivalent capacity Ci of the present embodiment meets following equation (28) to (30) during the charging process:
Q1=Coss42* (Vo-Vcc) (28)
Q2=(Ciss+Coss43) * (Vclamp-VH) (29)
Q1≦Q2 (30)
Figure 28 is the electrical block diagram of the driving circuit of the power switch of the tenth embodiment of this case.As shown in figure 28, The framework of the driving circuit 2D of the present embodiment is similar to element function to embodiment illustrated in fig. 21, and identical element numbers represent Identical structure, element and function, repeat no more in this.Compared to driving circuit 2A shown in Figure 21, the driving of the present embodiment Driving circuit 2A shown in circuit 2D and Figure 21 the difference is that, the driving circuit 2D of the present embodiment is opened with more third driving S43 is closed, wherein third driving switch S43 has third parasitic capacitance Coss43, and the first end of third driving switch S43 is electrically connected Between the second end of the second driving switch S42 and the first end of resistance R, the second end of third driving switch S43 is electrically connected to Ground terminal.Driving circuit 2D controls input capacitance Ciss electric discharge by the conducting of third driving switch S43, to promote input The velocity of discharge of capacitor Ciss.
In this present embodiment, driving circuit 2D can also be equivalent to the equivalent circuit 2 such as Fig. 9, so with driving circuit 2A etc. Effect the difference is that, the first equivalent capacity Ci reflect power switch input capacitance Ciss and reflection third driving switch S43 Third parasitic capacitance Coss43.
Figure 29 is the electrical block diagram of the driving circuit of the power switch of the 11st embodiment of this case.Such as Figure 29 institute Show, the framework of the driving circuit 2E of the present embodiment is similar to element function to embodiment illustrated in fig. 26, and identical element numbers Identical structure, element and function are represented, is repeated no more in this.Compared to driving circuit 2C shown in Figure 26, the present embodiment Driving circuit 2C shown in driving circuit 2E and Figure 26 the difference is that, driving circuit 2E has more third driving switch S43, Wherein third driving switch S43 has the 4th parasitic capacitance Coss44, the first end of third driving switch S43 and the first clamper electricity The first end of the first end of road C43, the second end of the second driving switch S42 and resistance R is electrically connected, third driving switch S43's Second end is electrically connected with ground terminal.Compared to driving circuit 2C shown in Figure 26, the driving circuit 2E of the present embodiment not only has and makes Voltage on input capacitance Ciss will not Yin Taigao and the advantages of damage power switch outside, driving circuit 2E can also be driven by third It moves the conducting of switch S43 and controls input capacitance Ciss electric discharge, to promote the velocity of discharge of input capacitance Ciss.
In this present embodiment, driving circuit 2E can also be equivalent to the equivalent circuit 2 such as Fig. 9, so with driving circuit 2C etc. Effect the difference is that, the first equivalent capacity Ci reflect the input capacitance Ciss of power switch, the first clamp circuit C43 of reflection the Trixenie capacitor Coss43 and the 4th parasitic capacitance Coss44 for reflecting third driving switch S43.Due to the of the present embodiment One equivalent capacity Ci is by input capacitance Ciss, the third parasitic capacitance Coss43 of the first clamp circuit C43 and third driving switch Under the 4th parasitic capacitance Coss44 institute of S43 is equivalent, therefore the first equivalent capacity Ci of the present embodiment meets during the charging process Column formula (31) to (33):
Q1=Coss42* (Vo-Vcc) (31)
Q2=(Ciss+Coss43+Coss44) * (Vclamp-VH) (32)
Q1≦Q2 (33)
Figure 30 is the electrical block diagram of the driving circuit of the power switch of the 12nd embodiment of this case.In the present embodiment In, driving circuit 3A includes inductance L51, the first driving switch S51, the second driving switch S52, third driving switch S53, the 4th Driving switch S54 and resistance R, and capacitor Ciss is the input capacitance of power switch (not shown).First driving switch S51's First end is electrically connected with input source, the first end and inductance of the second end of the first driving switch S51 and the second driving switch S52 The first end of L51 is electrically connected, and the second end of the second driving switch S52 is electrically connected with ground terminal, and the first of the 4th driving switch S54 End is electrically connected with the first end of resistance R, and the second end of the 4th driving switch S54 is opened with second end and the third driving of inductance L51 The first end electrical connection of S53 is closed, the second end of third driving switch S53 is electrically connected with ground terminal, the second end and input of resistance R Capacitor Ciss electrical connection.In addition, in this present embodiment, the first driving switch S51, the second driving switch S52, third driving switch It is respectively the first parasitic capacitance Coss51, the second parasitic capacitance that S53, the 4th driving switch S54, which can actually have parasitic parameter, Coss52, third parasitic capacitance Coss53, the 4th parasitic capacitance Coss54.
The charging and discharging of the input capacitance Ciss of the present embodiment further described below operate.Driving circuit 3A passes through The on or off of first driving switch S51, the second driving switch S52, third driving switch S53 and the 4th driving switch S54 It operates to control the charging and discharging of input capacitance Ciss.
It please refers to Figure 31 and cooperates Figure 30, Figure 31 is that the input capacitance of the 12nd embodiment is opened in charging process with driving Close the timing diagram of a demonstration example of corresponding running.When input capacitance Ciss need to be charged, the first driving switch S51 and third Driving switch S53 is connected in time t0 to t1, makes first driving switch S51 and third driving of the electric energy of input source by conducting Switch S53 charges to inductance L51.Second driving switch S52 and the 4th driving switch S54 in time t0 to t1 terminate and It is connected (when time point t1) when one driving switch S51 and third driving switch S53 ends, makes the current discharge of inductance L51 extremely Input capacitance Ciss, and then input capacitance Ciss is made to charge.Second driving switch S52 and the 4th driving switch S54 are in inductance L51 Electric current end when being zero (i.e. when time point t2), so that input capacitance Ciss is charged to voltage value Vp1.In time point t2, by In the voltage in the charging process of above-mentioned driving circuit 3A, the first parasitic capacitance Coss51, third parasitic capacitance Coss53 be zero, Voltage is voltage value Vcc on second parasitic capacitance Coss52, and voltage value is Vp1 on the 4th parasitic capacitance Coss54.In time t2 When to t3, the first parasitic capacitance Coss51 and the second parasitic capacitance Coss52 can pass through inductance L51 and third parasitic capacitance The in parallel of the 4th parasitic capacitance Coss54 of Coss53 and input capacitance Ciss series connection carries out resonance, makes the voltage of input capacitance Ciss Value Vp1 can reach a final steady-state value Vo, and the voltage on the second parasitic capacitance Coss52 can resonance to equal than the parasitic electricity of third Hold the voltage on Coss53.Since input capacitance Ciss connects with the 4th parasitic capacitance Cosse54 of the 4th driving switch S54, Then in parallel with the third parasitic capacitance Coss53 of third driving switch S53, then the first driving switch S51, second drive again The first parasitic capacitance Coss51, the second parasitic capacitance Coss52 of switch S52 is series relationship, therefore when time t2 to t3, Charge that input capacitance Ciss is released from voltage value Vp1 to final steady-state value Vo, third parasitic capacitance Coss53 power on buckling Stable state, the second parasitic capacitance Coss52 can be changed to from Vcc equal to the first parasitic capacitance Coss51 by changing the sum of released charge Change from zero to the sum of the charge of stable state Q1.The voltage value on input capacitance Ciss needed due to power switch is reaching final It is higher than one first setting voltage value VH when steady-state value Vo, so input capacitance Ciss becomes from voltage value Vp1 in time t2 to t3 Changing to the sum of charge variation amount caused by voltage change on the first setting voltage value VH and third parasitic capacitance Coss53 Q2 needs greatly The first parasitic capacitance Coss51 and second is posted when input capacitance Ciss changes to final steady-state value Vo from voltage value Vp1 The sum of the charge variation amount of raw capacitor Coss52 Q1.Therefore, meet in input capacitance Ciss charging process following equation (34) To (36):
Q1=(Coss51+Coss52) * [VH- (Vp1-Vo) * (Ciss/Coss54)] (34)
Q2=(Coss53+Coss54) * (Vp1-VH) * (Ciss/Coss54)+Coss53* (Vp1-VH)
(35)
Q1≦Q2 (36)
In above-described embodiment, in order to reduce the control precision of the second driving switch S52, the 4th driving switch S54, if the One driving switch S51, the second driving switch S52, third driving switch S53, the 4th driving switch S54 are used with body two The MOSFET of pole pipe, then the second parasitic capacitance Coss52, third are parasitic electric under stable state after input capacitance Ciss charging complete The voltage held on Coss53 is lower than voltage value Vcc, i.e. when Vo- (Vp1-Vo) * (Ciss/Coss54) < Vcc, then meets following public affairs Formula (37) to (39):
Q1=(Coss51+Coss52) * [Vo- (Vp1-Vo) * (Ciss/Coss54)] (37)
Q2=(Coss53+Coss54) * (Vp1-VH) * (Ciss/Coss54)+Coss53* (Vp1-VH)
(38)
Q1≦Q2 (39)
If the second parasitic capacitance Coss52, third parasitic capacitance under stable state after input capacitance Ciss charging complete Voltage on Coss53 by the body diode clamper of the first driving switch S51 to voltage value Vcc when, then meet following equation (40) To (42):
Q1=Coss54* (VH-Vcc) (40)
Q2=Ciss* (Vp1-VH) (41)
Q1≦Q2 (42)
It please refers to Figure 32 and cooperates Figure 30, Figure 32 is that the input capacitance of the 12nd embodiment is opened in discharge process with driving Close the timing diagram of a demonstration example of corresponding running.When input capacitance Ciss need to be discharged, the second driving switch S52 and the 4th Driving switch S54 in time t4 to t5 be connected, make input capacitance Ciss by inductance L51 discharge inductance L51 electric current increase. First driving switch S51 and third driving switch S53 is when the voltage value of input capacitance Ciss reaches Vp2 (i.e. when time point t5) Cut-off discharges the energy of inductance L51 to input source, corresponding such as time t5 to t6, and the first driving switch S51 and third driving Switch S53 more ends (i.e. when time point t6) when inductance L51 electric discharge is down to zero.In time point t6, due to above-mentioned driving electricity The discharge process on road 1, the voltage of the first parasitic capacitance Coss51 are zero, and the voltage of the second parasitic capacitance Coss52 is voltage value Vcc.When time t6 to t7, the first parasitic capacitance Coss51 and the second parasitic capacitance Coss52 can pass through inductance L51 and The in parallel of the 4th parasitic capacitance Coss54 of trixenie capacitor Coss53 and input capacitance Ciss series connection carries out resonance, makes input capacitance The voltage value Vp2 of Ciss can reach a final steady-state value Vo, and voltage on the second parasitic capacitance Coss52 can resonance to equal than Voltage on third parasitic capacitance Coss53.Due to the 4th parasitic capacitance of input capacitance Ciss and the 4th driving switch S54 Coss54 series connection, it is then in parallel with the third parasitic capacitance Coss53 of third driving switch S53, then again with the first driving switch S51, the first parasitic capacitance Coss51 of the second driving switch S52, the second parasitic capacitance Coss52 be series relationship, therefore in when Between t6 to t7 when, charge that input capacitance Ciss is filled with from voltage value Vp2 to final steady-state value Vo can be equal to the first parasitic electricity Hold the sum of the charge Q3 that Coss51 changes from zero to stable state, the second parasitic capacitance Coss52 changes to stable state from voltage value Vcc.By In the voltage value on the input capacitance Ciss that power switch needs when reaching final steady-state value Vo lower than the second setting voltage value VL, so input capacitance Ciss changes to the second setting voltage value VL from voltage value Vp2 and third is parasitic in time t6 to t7 The sum of charge variation amount Q4 caused by voltage change need to be greater than or equal to input capacitance Ciss from voltage value Vp2 on capacitor Coss53 The sum of charge variation amount of first parasitic capacitance Coss51 and the second parasitic capacitance Coss52 Q3 when changing to final steady-state value Vo. Therefore, following equation (43) to (45) are met in input capacitance Ciss discharge process:
Q3=(Coss51+Coss52) * [Vcc- (Vo-Vp2) * (Ciss/Coss54)] (43)
Q4=(Coss53+Coss54) * (VL-Vp2) * (Ciss/Coss54)+Coss53* (VL-Vp2)
(44)
Q3≦Q4 (45)
In above-described embodiment, the optimal scheme of voltage value Vp2 is zero.If the second driving switch S52, the 4th driving are opened It is too long to close S54 turn-on time, input capacitance Ciss reverse charging can be made, and voltage value Vp2 causes input capacitance Ciss less than zero The shock range of upper voltage is excessive, and increases loss.
In addition, in order to reduce the control precision of the first driving switch S51, third driving switch S53, if the first driving switch S51, the second driving switch S52, third driving switch S53, the 4th driving switch S54 are used with body diode MOSFET, then when input capacitance Ciss electric discharge after the completion of stable state under the second parasitic capacitance Coss52, third parasitic capacitance When voltage on Coss53 is lower than the final steady-state value Vo, i.e. (Vo-Vp2) * (1+Ciss/Coss54) < Vo of input capacitance Ciss, Then meet following equation (46) to (48):
Q3=(Coss51+Coss52) * [Vcc- (Vo-Vp2) * (Ciss/Coss54)] (46)
Q4=(Coss53+Coss54) * (VL-Vp2) * (Ciss/Coss54)+Coss53* (VL-Vp2)
(47)
Q3≦Q4 (48)
If the second parasitic capacitance Coss52, third parasitic capacitance under the stable state after the completion of input capacitance Ciss electric discharge Voltage on Coss53 to final steady-state value Vo, then meets following equation by the body diode clamper of the 4th driving switch S54 (49) to (51):
Q3=(Coss51+Coss52) * (Vcc-VL) (49)
Q4=Ciss* (VL-Vp2) (50)
Q3≦Q4 (51)
The driving circuit 3A of the present embodiment can also be equivalent to the equivalent circuit 2 such as Fig. 9, wherein the first equivalent capacity Ci reflects The input capacitance Ciss of power switch, the third parasitic capacitance Coss53 and the 4th driving switch S54 of third driving switch S53 4th parasitic capacitance Coss54, equivalent inductance L include the inductance L51 of driving circuit 3A, and the second equivalent capacity Coss reflection the The first parasitic capacitance Coss51 of one driving switch S51 and the second parasitic capacitance Coss52 for reflecting the second driving switch S52.
Figure 33 is the electrical block diagram of the driving circuit of the power switch of the 13rd embodiment of this case.In the present embodiment In, driving circuit 4A includes inductance L61, the first driving switch S61 and resistance R, and capacitor Ciss is that power switch (is not schemed Show) input capacitance.The first end of first driving switch S61 is electrically connected with the second end of inductance L61, the first driving switch S61 Second end be electrically connected with the first end of resistance R, the first end of inductance L61 is electrically connected with input source, the second end of resistance R with it is defeated Enter capacitor Ciss electrical connection.In addition, in this present embodiment, the first driving switch S61 can actually have parasitic parameter for parasitism Capacitor Coss61.
The charging and discharging of the input capacitance Ciss of the present embodiment further described below operate.Driving circuit 4A passes through The on or off of first driving switch S61 operates to control the charging and discharging of input capacitance Ciss.
It please refers to Figure 34 and cooperates Figure 33, Figure 34 is that the input capacitance of the 13rd embodiment is opened in charging process with driving Close the timing diagram of a demonstration example of corresponding running.When input capacitance Ciss need to be charged, the first driving switch S61 is in the time T0 to t1 conducting, makes the electric energy of input source charge by the first driving switch S61 be connected to input capacitance Ciss, simultaneously The electric current of inductance L61 can first increase and decline afterwards.First driving switch S61 terminates in time t0 to t1 and the electric current of inductance L61 drops End when to zero.In time point t1, the charging process of above-mentioned driving circuit 4A can make the voltage value of input capacitance Ciss Vp1 is higher than the voltage value Vcc of input source and is less than or equal to 2*Vcc, and when time t1 to t2, parasitic capacitance Coss61 can pass through Inductance L61 and input capacitance Ciss carries out resonance, makes the voltage value Vp1 of input capacitance Ciss that can reach a final steady-state value Vo, And the sum of voltage and voltage value Vcc on parasitic capacitance Coss61 meeting resonance to parasitic capacitance Coss61 is equal to input capacitance Voltage on Ciss.Since the parasitic capacitance Coss61 of input capacitance Ciss and the first driving switch S61 are series relationship, When time t1 to t2, the charge that input capacitance Ciss is released from voltage value Vp1 to final steady-state value Vo can be equal to parasitic electricity Hold the charge Q 1 that Coss61 changes from zero to Vo-Vcc.The voltage on input capacitance Ciss needed due to power switch is final It is greater than the first setting voltage value VH when steady-state value Vo, so input capacitance Ciss changes from voltage value Vp1 in time t1 to t2 Charge variation amount Q2 to the first setting voltage value VH need to be changed to finally more than or equal to input capacitance Ciss from voltage value Vp1 The charge variation amount Q1 of parasitic capacitance Coss61 when steady-state value Vo.Therefore, meet in input capacitance Ciss charging process following Formula (52) to (54):
Q1=Coss61* (Vo-Vcc) (52)
Q2=Ciss* (Vp1-VH) (53)
Q1≦Q2 (54)
It please refers to Figure 35 and cooperates Figure 33, Figure 35 is that the input capacitance of the 13rd embodiment is opened in discharge process with driving Close the timing diagram of a demonstration example of corresponding running.When input capacitance Ciss need to be discharged, the first driving switch S61 is in the time T0 to t1 conducting, makes input capacitance Ciss discharge by inductance L61, and the electric current of inductance L61 can first increase and decline afterwards.First drives Dynamic switch S61 is when the electric current that input capacitance Ciss reaches voltage value Vp2 and inductance L61 is down to zero (i.e. when time point t1) section Only.In time point t1, since the discharge process of above-mentioned driving circuit 4A can make voltage value on input capacitance Ciss be Vp2, Wherein optimal scheme is zero to voltage value Vp2 in this present embodiment, and the voltage value of parasitic capacitance Coss61 is zero, thus in when Between t1 to t2 when, parasitic capacitance Coss61 can carry out resonance by inductance L61 and input capacitance Ciss, make input capacitance Ciss's Voltage value Vp2 can reach a final steady-state value Vo, and the voltage on parasitic capacitance Coss61 understands resonance to voltage value Vcc-Vo.By In the parasitic capacitance Coss61 of input capacitance Ciss and the first driving switch S61 be series relationship, therefore when time t1 to t2, Input capacitance Ciss, which changes to the charge that final steady-state value Vo is filled with from voltage value Vp2, can be equal to parasitic capacitance Coss61 from zero Change to the sum of the charge of Vcc-Vo Q3.The voltage on input capacitance Ciss needed due to power switch is in final steady-state value Vo When less than second setting voltage value VL, so input capacitance Ciss changes to second from voltage value Vp2 and sets in time t1 to t2 The charge variation amount Q4 of constant voltage value VL need to be greater than or equal to input capacitance Ciss and change to final steady-state value Vo from voltage value Vp2 When parasitic capacitance Coss61 charge variation amount Q3.Therefore, meet in input capacitance Ciss discharge process following equation (55) To (57):
Q3=Coss61* (Vcc-Vo) (55)
Q4=Ciss* (Vp2-VL) (56)
Q3≦Q4 (57)
The driving circuit 4A of the present embodiment can also be equivalent to the equivalent circuit 2 such as Fig. 9, wherein the first equivalent capacity Ci reflects The input capacitance Ciss of power switch, equivalent inductance L include the inductance L61 of driving circuit 4A, and the second equivalent capacity Coss is anti- Reflect the parasitic capacitance Coss61 of the first driving switch S61.
In conclusion this case is a kind of driving circuit of power switch, the inductance in driving circuit is made to be not required to provide perseverance In the case where the electric current in stream source, the energy loss of resistance is similarly smaller, in this way, which the driving circuit of this case can use feeling Measure smaller, small volume inductance.
This case appointed as those skilled in the art apply craftsman think and be it is all as modify, it is so neither de- as attached claim is intended to protect Shield person.

Claims (31)

1. a kind of driving circuit, to drive a power switch, which is characterized in that the driving circuit includes:
One inductance；And
An at least driving switch is electrically connected with the inductance；
Wherein, the driving circuit and the power switch are equivalent at an equivalent circuit, which includes:
One first equivalent capacity at least reflects an input capacitance of the power switch；
One equivalent inductance includes the inductance, and is connected in series with first equivalent capacity；And
One second equivalent capacity, reflects the parasitic parameter of an at least driving switch, and with first equivalent capacity and this is equivalent Inductance is connected in series and forms a charging and discharging circuit, first equivalent capacity is charged or be put by the charging and discharging circuit Electricity running；
It wherein, is zero to be to the voltage value of the input capacitance from the electric current of the inductance in the first equivalent capacity charging process One first setting voltage value is zero to the input capacitance from the electric current of the inductance or in the first equivalent capacity discharge process Voltage value be one second setting voltage value, the charge variation amount in first equivalent capacity is greater than or equal to the electricity from the inductance Stream is the charge variation amount in zero second equivalent capacity when reaching a final steady-state value to the voltage value of the input capacitance；
Wherein, the maximum value in a threshold voltage range of the grid which is greater than the power switch, should Minimum value in one threshold voltage range of the grid that the second setting voltage value is less than the power switch.
2. driving circuit as described in claim 1, which is characterized in that an at least driving switch be one first driving switch and One first end of one second driving switch, first driving switch is electrically connected with an input source, and the one of first driving switch Two ends are electrically connected with a first end of a first end of second driving switch and the inductance, and the one second of second driving switch End is electrically connected with a ground terminal, and a second end of the inductance is electrically connected with a first end of a resistance, a second end of the resistance It is electrically connected with the input capacitance, and the parasitic parameter of an at least driving switch includes one first parasitism of first driving switch One second parasitic capacitance of capacitor and second driving switch.
3. driving circuit as claimed in claim 2, which is characterized in that the driving circuit by first driving switch and this The on or off of two driving switch controls the charging and discharging of the input capacitance.
4. driving circuit as claimed in claim 3, which is characterized in that first equivalent capacity is the input capacitance, and this One equivalent capacity meets following equation in charging process:
Q1=Coss31*Vo+Coss32*Vo
Q2=Ciss* (Vp1-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss31 are first parasitism Capacitor, Coss32 are second parasitic capacitance, and Ciss is the input capacitance, and Vo is the final steady-state value, and are first parasitism Capacitor and second parasitic capacitance from the electric current of inductance be zero reach the final steady-state value to the voltage value of the input capacitance when Voltage variety, Vp1 are voltage value of the input capacitance when the electric current of the inductance is zero in charging process, and VH is that this first sets Constant voltage value.
5. driving circuit as claimed in claim 3, which is characterized in that first equivalent capacity is the input capacitance, and this One equivalent capacity meets following equation in discharge process:
Q3=(Coss31+Coss32) * (Vcc-Vo)
Q4=Ciss* (Vp2-VL)
Q3≦Q4
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q3, which is in the first equivalent capacity discharge process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q4, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is one second setting voltage value in first equivalent capacity, Coss31 are first driving First parasitic capacitance of switch, Coss32 are second parasitic capacitance of second driving switch, and Ciss is the input capacitance, Vo is the final steady-state value, and Vcc is the voltage value of the input source, and Vcc-Vo is first parasitic capacitance and second parasitic capacitance From the electric current of inductance be zero reach the final steady-state value to the voltage value of the input capacitance when voltage variety, Vp2 is electric discharge Voltage value of the input capacitance when the electric current of the inductance is zero in the process, VL are the second setting voltage value.
6. driving circuit as claimed in claim 2, which is characterized in that the driving circuit further includes a third driving switch, should Third driving switch have a third parasitic capacitance, a first end of the third driving switch be electrically connected to the inductance this second The first end of end and the resistance, a second end of the third driving switch are electrically connected with the ground terminal, and the driving circuit is logical It crosses the on or off of first driving switch and second driving switch and controls the charging of first equivalent capacity, the driving Circuit controls input capacitance electric discharge by the conducting of the third driving switch.
7. driving circuit as claimed in claim 6, which is characterized in that first equivalent capacity include the input capacitance and this Trixenie capacitor, and first equivalent capacity meets following equation in charging process:
Q1=(Coss31+Coss32) * Vo
Q2=(Ciss+Coss33) * (Vp1-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss31 are first driving First parasitic capacitance of switch, Coss32 are second parasitic capacitance of second driving switch, and Ciss is the input capacitance, Coss33 is the third parasitic capacitance of the third driving switch, and Vo is the final steady-state value, and for first parasitic capacitance and Second parasitic capacitance from the electric current of inductance be zero reach the final steady-state value to the voltage value of the input capacitance when voltage become Change amount, Vp1 are voltage value of the input capacitance when the electric current of the inductance is zero in charging process, and VH is the first setting voltage Value.
8. driving circuit as claimed in claim 3, which is characterized in that the driving circuit further includes one first clamp circuit and one Second clamp circuit, first clamp circuit have a third parasitic capacitance, which has one the 4th parasitic electricity Hold, the first end of first clamp circuit is electrically connected with the first end of first driving switch and the input source, first pincers The first end of the second end and the second end of the inductance, the first end of second clamp circuit and the resistance of position circuit is electrically connected It connects, the second end of second clamp circuit is electrically connected with the ground terminal, and first clamp circuit is in the voltage of the input capacitance The voltage value of the clamper input capacitance is the overvoltage value when value is higher than an overvoltage value, and second clamp circuit is in input electricity The voltage value of the clamper input capacitance is the under-voltage value when voltage value of appearance is lower than a under-voltage value.
9. driving circuit as claimed in claim 8, which is characterized in that first equivalent capacity of the driving circuit includes that this is defeated Enter capacitor, the third parasitic capacitance of first clamp circuit and the 4th parasitic capacitance of second clamp circuit, and this One equivalent capacity meets following equation in charging process:
Q1=(Coss31+Coss32) * Vo
Q2=(Ciss+Coss34+Coss35) * (Vp1-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss31 are first driving First parasitic capacitance of switch, Coss32 are second parasitic capacitance of second driving switch, and Ciss is the input capacitance, Coss35 is the third parasitic capacitance of first clamp circuit, and Coss34 is the 4th parasitic electricity of second clamp circuit Hold, Vo is the final steady-state value, and be first parasitic capacitance with second parasitic capacitance from the electric current of inductance be zero defeated to this Enter the voltage variety when voltage value of capacitor reaches the final steady-state value, Vp1 be in charging process the input capacitance in the electricity The voltage value when electric current of sense is zero, VH are the first setting voltage value.
10. driving circuit as claimed in claim 8, which is characterized in that first equivalent capacity of the driving circuit includes should Input capacitance, the third parasitic capacitance of first clamp circuit and the 4th parasitic capacitance of second clamp circuit, and should First equivalent capacity meets following equation in discharge process:
Q3=(Coss31+Coss32) * (Vcc-Vo)
Q4=(Ciss+Coss34+Coss35) * (Vp2-VL)
Q3≦Q4
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q3, which is in the first equivalent capacity discharge process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q4, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is one second setting voltage value in first equivalent capacity, Coss31 are first driving First parasitic capacitance of switch, Coss32 are second parasitic capacitance of second driving switch, and Ciss is the input capacitance, Coss35 is the third parasitic capacitance of first clamp circuit, and Coss34 is the 4th parasitic electricity of second clamp circuit Appearance, Vo are the final steady-state value, and Vcc is the voltage value of the input source, and Vcc-Vo is first parasitic capacitance and second parasitism Capacitor from the electric current of inductance be zero reach the final steady-state value to the voltage value of the input capacitance when voltage variety, Vp2 is Voltage value of the input capacitance when the electric current of the inductance is zero in discharge process, VL are the second setting voltage value.
11. driving circuit as claimed in claim 3, which is characterized in that the driving circuit further include one first clamp circuit and One third driving switch, first clamp circuit have a third parasitic capacitance, which has one the 4th parasitism Capacitor, the first end of first clamp circuit are electrically connected with the first end of first driving switch and the input source, this first The second end of clamp circuit and the second end, a first end of the third driving switch, the first end of the resistance of the inductance Electrical connection, a second end of the third driving switch are electrically connected with the ground terminal, and first clamp circuit is in the input capacitance The voltage value of the clamper input capacitance is the overvoltage value when voltage value is higher than an overvoltage value, and passes through the third driving switch Conducting and control the input capacitance electric discharge.
12. driving circuit as claimed in claim 11, which is characterized in that first equivalent capacity of the driving circuit includes should Input capacitance, the third parasitic capacitance of first clamp circuit and the 4th parasitic capacitance of the third driving switch, and should First equivalent capacity meets following equation in charging process:
Q1=(Coss31+Coss32) * Vo
Q2=(Ciss+Coss33+Coss35) * (Vp1-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss31 are first driving First parasitic capacitance of switch, Coss32 are second parasitic capacitance of second driving switch, and Ciss is the input capacitance, Coss35 is the third parasitic capacitance of first clamp circuit, and Coss33 is the 4th parasitic electricity of the third driving switch Hold, Vo is the final steady-state value, and be first parasitic capacitance with second parasitic capacitance from the electric current of inductance be zero defeated to this Enter the voltage variety when voltage value of capacitor reaches the final steady-state value, Vp1 be in charging process the input capacitance in the electricity The voltage value when electric current of sense is zero, VH are the first setting voltage value.
13. driving circuit as described in claim 1, which is characterized in that an at least driving switch is one first driving switch And one second driving switch, a first end of the inductance are electrically connected with an input source, a second end of the inductance and this first drive The first end electrical connection of the first end and second driving switch of dynamic switch, a second end and one for second driving switch One first end of resistance is electrically connected, and a second end of the resistance is electrically connected with the input capacitance, and the one the of first driving switch Two ends are electrically connected with a ground terminal.
14. driving circuit as claimed in claim 13, which is characterized in that the driving circuit is by first driving switch and is somebody's turn to do The on or off of second driving switch and the charging and discharging for controlling the input capacitance.
15. driving circuit as claimed in claim 14, which is characterized in that first equivalent capacity is the input capacitance, and should Second equivalent capacity is one second parasitic capacitance of second driving switch, under meeting in the first equivalent capacity charging process Column formula:
Q1=Coss42* (Vo-Vcc)
Q2=Ciss* (Vp1-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss42 are second driving Second parasitic capacitance of switch, Ciss are the input capacitance, and Vo is the final steady-state value, and Vcc is the voltage value of the input source, Vo-Vcc be second parasitic capacitance from the electric current of inductance be zero reach the final steady-state value to the voltage value of the input capacitance when Voltage variety, Vp1 is voltage value of the input capacitance when the electric current of the inductance is zero in charging process, VH be this first Set voltage value.
16. driving circuit as claimed in claim 14, which is characterized in that first equivalent capacity is the input capacitance, and should Second equivalent capacity is one second parasitic capacitance of second driving switch, under meeting in the first equivalent capacity discharge process Column formula:
Q3=Coss42* (Vp2+Vcc-Vo)
Q4=Ciss* (Vp2-VL)
Q3≦Q4
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q3, which is in the first equivalent capacity discharge process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q4, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is one second setting voltage value in first equivalent capacity, Coss42 are second driving Second parasitic capacitance of switch, Ciss are the input capacitance, and Vo is the final steady-state value, and Vcc is the voltage value of the input source, Vp2 is voltage value of the input capacitance when the electric current of the inductance is zero in discharge process, and Vp2+Vcc-Vo is second parasitism Capacitor from the electric current of the inductance be zero reach the final steady-state value to the voltage value of the input capacitance when voltage variety, VL is The second setting voltage value.
17. driving circuit as claimed in claim 13, which is characterized in that the driving circuit further include a third driving switch and One direct current clamps power supply, which has a third parasitic capacitance, and a first end of the third driving switch is electrically connected It is connected between the second end of second driving switch and the first end of the resistance, direct current clamp power supply is connected to the third Between the second end and the ground terminal of driving switch, wherein direct current clamp power supply is when the third driving switch is connected to this Input capacitance charges, and when the input capacitance is discharged pass through the cut-off of the third driving switch and by this first The on or off of driving switch and second driving switch and control the input capacitance electric discharge.
18. driving circuit as claimed in claim 13, which is characterized in that the driving circuit further include one first clamp circuit and One direct current clamps power supply, which has a third parasitic capacitance, and a first end of first clamp circuit is electrically connected Be connected between the second end of second driving switch and the first end of the resistance, the direct current clamp power electric connection in this Between the second end and the ground terminal of one clamp circuit, and first clamp circuit is higher than this in the voltage value of the input capacitance The voltage value of the clamper input capacitance is the voltage value that the direct current clamps power supply when direct current clamps the voltage value of power supply Vclamp.
19. driving circuit as claimed in claim 13, which is characterized in that the driving circuit further includes a third driving switch, The third driving switch has a third parasitic capacitance, and a first end of the third driving switch is electrically connected to second driving and opens Between the first end of the second end and the resistance for closing, a second end of the third driving switch is electrically connected to the ground terminal, Wherein the driving circuit controls input capacitance electric discharge by the conducting of the third driving switch.
20. the driving circuit as described in any one of claim 17 to 19, which is characterized in that first equivalent capacity includes should Input capacitance and the third parasitic capacitance, second equivalent capacity include one second parasitic capacitance of first driving switch, and First equivalent capacity meets following equation in charging process:
Q1=Coss42* (Vo-Vcc)
Q2=(Ciss+Coss43) * (Vclamp-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss42 are second driving Second parasitic capacitance of switch, Ciss are the input capacitance, and Coss43 is the third parasitic capacitance, and Vo is the final stable state Value, Vcc are the voltage value of the input source, Vo-Vcc be second parasitic capacitance from the electric current of inductance be zero to the input capacitance Voltage value reaches voltage variety when the final steady-state value, Vclamp be in charging process the input capacitance in the electricity of the inductance Voltage value when stream is zero, VH are the first setting voltage value.
21. the driving circuit as described in any one of claim 17 to 19, which is characterized in that first equivalent capacity includes should Input capacitance and the third parasitic capacitance, second equivalent capacity include one second parasitic capacitance of first driving switch, and First equivalent capacity meets following equation in discharge process:
Q3=Coss42* (Vp2+Vcc-Vo)
Q4=(Ciss+Coss43) * (Vp2-VL)
Q3≦Q4
Wherein, it is that zero to the voltage value of the input capacitance, to reach this final steady that Q3, which is first equivalent capacity from the electric current of the inductance, Charge variation amount when state value in second equivalent capacity, Q4 be from the electric current of the inductance be zero to the input capacitance voltage value Charge variation amount when for one second setting voltage value in first equivalent capacity, Coss42 be second driving switch this Two parasitic capacitances, Ciss are the input capacitance, and Coss43 is the third parasitic capacitance, and Vo is the final steady-state value, and Vcc is that this is defeated Enter the voltage value in source, Vp2 is voltage value of the input capacitance when the electric current of the inductance is zero, Vp2+Vcc-Vo in discharge process For second parasitic capacitance from the electric current of the inductance be zero reach the final steady-state value to the voltage value of the input capacitance when electricity Variable quantity is pressed, VL is the second setting voltage value.
22. driving circuit as claimed in claim 18, which is characterized in that the driving circuit also has a third driving switch, The third driving switch has one the 4th parasitic capacitance, and the of a first end of the third driving switch and first clamp circuit The first end of one end, the second end of second driving switch and the resistance is electrically connected, and the one second of the third driving switch End is electrically connected with the ground terminal.
23. driving circuit as claimed in claim 22, which is characterized in that first equivalent capacity includes the input capacitance, is somebody's turn to do Third parasitic capacitance and the 4th parasitic capacitance, second equivalent capacity include one second parasitic electricity of first driving switch Hold, and first equivalent capacity meets following equation in charging process:
Q1=Coss42* (Vo-Vcc)
Q2=(Ciss+Coss43+Coss44) * (Vclamp-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss42 are second driving Second parasitic capacitance of switch, Ciss are the input capacitance, and Coss43 is the third parasitic capacitance, and Coss44 posts for the 4th Raw capacitor, Vo are the final steady-state value, and Vcc is the voltage value of the input source, and Vo-Vcc is second parasitic capacitance from inductance Electric current is zero voltage variety when reaching the final steady-state value to the voltage value of the input capacitance, and Vclamp is in charging process Voltage value of the input capacitance when the electric current of the inductance is zero, VH are the first setting voltage value.
24. driving circuit as described in claim 1, which is characterized in that an at least driving switch includes that one first driving is opened Pass, one second driving switch, a third driving switch and one the 4th driving switch, a first end and one for first driving switch The one the of input source electrical connection, a second end of first driving switch and a first end of second driving switch and the inductance One end electrical connection, a second end of second driving switch are electrically connected with a ground terminal, a first end of the 4th driving switch It is electrically connected with the first end of a resistance, a second end of the 4th driving switch and the second end of the inductance and the third are driven The first end electrical connection of dynamic switch, a second end of the third driving switch are electrically connected with the ground terminal, the resistance this Two ends are electrically connected with the input capacitance.
25. driving circuit as claimed in claim 24, which is characterized in that the driving circuit passes through first driving switch, is somebody's turn to do Second driving switch, the on or off of the third driving switch and the 4th driving switch and control the charging of the input capacitance And electric discharge.
26. driving circuit as claimed in claim 25, which is characterized in that first equivalent capacity includes the input capacitance, is somebody's turn to do One third parasitic capacitance of third driving switch and one the 4th parasitic capacitance of the 4th driving switch, and second equivalent capacity One second parasitic capacitance of one first parasitic capacitance comprising first driving switch and second driving switch, in this first etc. Meet following equation during effect capacitor charging:
Q1=(Coss51+Coss52) * [VH- (Vp1-Vo) * (Ciss/Coss54)]
Q2=(Coss53+Coss54) * (Vp1-VH) * (Ciss/Coss54)+Coss53* (Vp1-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss51 are first driving First parasitic capacitance of switch, Coss52 are second parasitic capacitance of second driving switch, and Ciss is the input capacitance, Coss53 is the third parasitic capacitance of the third driving switch, and Coss54 is the 4th parasitic electricity of the 4th driving switch Hold, Vo is the final steady-state value, and Vp1 is voltage value of the input capacitance when the electric current of the inductance is zero, VH in charging process For the first setting voltage value.
27. driving circuit as claimed in claim 25, which is characterized in that first equivalent capacity includes the input capacitance, is somebody's turn to do One third parasitic capacitance of third driving switch and one the 4th parasitic capacitance of the 4th driving switch, and second equivalent capacity One second parasitic capacitance of one first parasitic capacitance comprising first driving switch and second driving switch, in this first etc. Meet following equation in effect capacitor discharge process:
Q3=(Coss51+Coss52) * [Vcc- (Vo-Vp2) * (Ciss/Coss54)]
Q4=(Coss53+Coss54) * (VL-Vp2) * (Ciss/Coss54)+Coss53* (VL-Vp2)
Q3≦Q4
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q3, which is in the first equivalent capacity discharge process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q4, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is one second setting voltage value in first equivalent capacity, Coss51 are first driving First parasitic capacitance of switch, Coss52 are second parasitic capacitance of second driving switch, and Ciss is the input capacitance, Coss53 is the third parasitic capacitance of the third driving switch, and Coss54 is the 4th parasitic electricity of the 4th driving switch Hold, Vo is the final steady-state value, and Vcc is the voltage value of the input source, and Vp2 is the input capacitance in discharge process in the inductance Voltage value when electric current is zero, VL are the second setting voltage value.
28. driving circuit as claimed in claim 2, which is characterized in that an at least driving switch is one first driving switch, One first end of first driving switch is electrically connected with the second end of the inductance, a second end and one for first driving switch The first end of resistance is electrically connected, and the first end of the inductance is electrically connected with an input source, and a second end of the resistance is defeated with this Enter capacitor electrical connection, and the parasitic parameter of an at least driving switch is a parasitic capacitance of first driving switch.
29. driving circuit as claimed in claim 28, which is characterized in that the driving circuit is led by first driving switch Logical or cut-off and the charging and discharging for controlling the input capacitance, and the input capacitance is first equivalent capacity, this is first equivalent Capacitor meets following equation in charging process:
Q1=Coss61* (Vo-Vcc)
Q2=Ciss* (Vp1-VH)
Q1≦Q2
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q1, which is in the first equivalent capacity charging process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q2, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is the first setting voltage value in first equivalent capacity, Coss61 are first driving The parasitic capacitance of switch, Ciss are the input capacitance, and Vo is the final steady-state value, and Vcc is the voltage value of the input source, Vp1 For voltage value of the input capacitance when the electric current of the inductance is zero in charging process, VH is the first setting voltage value.
30. driving circuit as claimed in claim 28, which is characterized in that the driving circuit is led by first driving switch Logical or cut-off and the charging and discharging for controlling the input capacitance, and the input capacitance is first equivalent capacity, this is first equivalent Capacitor meets following equation in discharge process:
Q3=Coss61* (Vcc-Vo)
Q4=Ciss* (Vp2-VL)
Q3≦Q4
Wherein, it from the electric current of the inductance is zero to reach to the voltage value of the input capacitance that Q3, which is in the first equivalent capacity discharge process, Charge variation amount when to the final steady-state value in second equivalent capacity, it is zero to input electricity that Q4, which is from the electric current of the inductance, Charge variation amount when the voltage value of appearance is one second setting voltage value in first equivalent capacity, Coss61 are first driving The parasitic capacitance of switch, Ciss are the input capacitance, and Vo is the final steady-state value, and Vcc is the voltage value of the input source, Vp2 For voltage value of the input capacitance when the electric current of the inductance is zero in discharge process, VL is the second setting voltage value.
31. driving circuit as claimed in claim 2, which is characterized in that from the inductance in the input capacitance charging process Electric current is zero when reaching the final steady-state value to the voltage value of the input capacitance, and resistance selection is greater than the final steady-state value The resistance value of 0.5* (Vp1+Vmax), wherein Vp1 is voltage of the input capacitance when the electric current of the inductance is zero in charging process Value, Vmax are voltage value needed for the input capacitance keeps power switch conducting when circuit shakes；Wherein in input electricity During discharge capacitor from the electric current of the inductance be zero reach the final steady-state value to the voltage value of the input capacitance when, resistance choosing With the resistance value for making the final steady-state value be less than 0.5* (Vp2+Vmin), wherein Vp2 is the input capacitance in discharge process in the electricity The voltage value when electric current of sense is zero, Vmin are electricity needed for the input capacitance keeps power switch shutdown when circuit shakes Pressure value.
CN201510867765.XA 2015-12-01 2015-12-01 Driving circuit Active CN106817020B (en)

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TW105113087A TWI587615B (en) 2015-12-01 2016-04-27 Driving circuit for power switch
US15/332,623 US10483949B2 (en) 2015-12-01 2016-10-24 Driving circuit for power switch
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US20170155377A1 (en) 2017-06-01
US10483949B2 (en) 2019-11-19

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