CN106130384A - Induction electric energy based on auxiliary induction transmission circulation control circuit system - Google Patents

Abstract

The invention provides a kind of induction electric energy based on auxiliary induction transmission circulation control circuit system, between the outfan and described former limit resonant network of described high-frequency inversion network, be provided with an auxiliary induction L₁, for damping the rate of climb and the peak value of circulation, and in each PWM cycle of pulse generating circuit, all there is the time T that described first switch S1, second switch S2, the 3rd switch S3 and the 4th switch S4 simultaneously turn on_OV, i.e. the overlapping conducting time, on the one hand give filter inductance L_dcThere is provided current loop, on the other hand so that auxiliary induction L₁On electric current steadily commutate, this system realize approximation zero current turning-on, zero voltage turn-off, reduce circulation peak value, reduce the switching loss of switching tube, it is suppressed that the bigger circulation between resonant network and inversion network.

Description

Induction electric energy based on auxiliary induction transmission circulation control circuit system

Technical field

The present invention relates to inductive electric energy transmission system circulation and control technical field, be specifically related to a kind of based on auxiliary induction Induction electric energy transmission circulation control circuit system.

Background technology

Induction electric energy transmission (Inductively Power Transfer, IPT) technology is a kind of novel electric energy transmission Technology, is a kind of based on electromagnetic induction coupling principle, comprehensive utilization modern power electronics technology, high-power high-frequency converter technique, Magnetic field coupling technique, by modern control theory and strategy, it is achieved one or more electrical equipments are in the way of non-electrical contact The technology of electric energy is obtained from electric power system.This technology solves tradition power supply mode and due to the problem of electrical connection generation and lacks Fall into, it is possible to achieve the safety of electric energy, flexible access.In IPT system, switching tube can be led in resonant capacitor voltage non-zero points switching Cause the appearance of circulation.Circulation can make the voltage at resonant capacitance two ends be distorted, and causes the generation of electromagnetic interference, and switch damages Consumption increases, and affects the stable operation of system, reduces the efficiency of transmission of system.

Summary of the invention

The application is by providing a kind of induction electric energy based on auxiliary induction transmission circulation control circuit system, it is achieved approximation Zero current turning-on, zero voltage turn-off, reduce circulation peak value, reduces the switching loss of switching tube, it is suppressed that resonant network with Bigger circulation between inversion network.

The application is achieved by the following technical solutions:

A kind of induction electric energy based on auxiliary induction transmission circulation control circuit system, including by the DC source E connected_in With filter inductance L_dcThe quasi-current source of composition, pulse generating circuit, high-frequency inversion network, former limit resonant network, secondary Resonance Neural Network Network, rectifying and wave-filtering network and load, wherein, described quasi-current source is connected with described high-frequency inversion network, for described high-frequency inversion Network provides unidirectional current, and described pulse generating circuit is connected with described high-frequency inversion network, and output control pulse controls described The output waveform of high-frequency inversion network, described high-frequency inversion network is connected with described former limit resonant network, and output square wave current is given Described former limit resonant network, described secondary resonant network receives the sinusoidal current of described former limit resonant network output, described secondary Resonant network is connected with load by described rectifying and wave-filtering network, is exported by sinusoidal current to load, institute after rectifying and wave-filtering State high-frequency inversion network and include the first switch S1, second switch S2, the 3rd switch S3 and the 4th switch S4, at described high-frequency inversion It is provided with an auxiliary induction L between outfan and the described former limit resonant network of network₁, for damping the rate of climb of circulation And peak value, and in each PWM cycle of pulse generating circuit, all there is described first switch S1, second switch S2, the 3rd open Close the time T that S3 and the 4th switch S4 simultaneously turns on_OV, i.e. the overlapping conducting time, on the one hand give filter inductance L_dcOffer electric current returns Road, on the other hand so that auxiliary induction L₁On electric current steadily commutate.

Further, described first switch S1 includes MOSFET pipe Q1 and antiparallel diode D1, described second switch S2 includes that MOSFET pipe Q2 and antiparallel diode D2, described 3rd switch S3 include MOSFET pipe Q3 and antiparallel two poles Pipe D3, described 4th switch S4 include MOSFET pipe Q4 and antiparallel diode D4, wherein, the source electrode of described MOSFET pipe Q1 Drain electrode with described MOSFET pipe Q2 is connected, and the source electrode of described MOSFET pipe Q3 is connected with the drain electrode of described MOSFET pipe Q4, institute The drain electrode stating MOSFET pipe Q1 is connected with the drain electrode of described MOSFET pipe Q3, the source electrode of described MOSFET pipe Q1 and described MOSFET The drain electrode of pipe Q4 connects, and the positive pole of all diodes all connects with the source electrode of corresponding MOSFET pipe, and the negative pole of all diodes is equal Drain electrode with corresponding MOSFET pipe connects, and the grid of described MOSFET pipe is all connected with described pulse generating circuit, described The source electrode of MOSFET pipe Q1 is as the first outfan of described high-frequency inversion network, and the source electrode of described MOSFET pipe Q3 is as described Second outfan of high-frequency inversion network, described former limit resonant network includes the resonant capacitance C of parallel connection_pWith resonant inductance L_p, and two The sys node of person is as the input of former limit resonant network, and the first outfan of described high-frequency inversion network is by described auxiliary Inductance L₁Being connected with the input of described former limit resonant network, the second outfan of described high-frequency inversion network is humorous with described former limit Another input of vibrating network is connected.

Alternatively preferred technical scheme, described first switch S1, second switch S2, the 3rd switch S3 and the 4th Switch S4 can be selected for IGBT insulated gate bipolar transistor.

Further, (1) system operating frequency is met more than ZVS frequency, i.e. f when simultaneously_s＞ f_ZVS；(2) all switching tubes Need at t₁～t₃Time period in turn off；And (3) are at overlapping conducting time T_OVStage, auxiliary induction L₁On electric currentMust Must be more than filter inductance L_dcOn electric current these three under the conditions of, be divided into following mode during described circulation control circuit stable state:

Mode 0: at t₀Before moment, auxiliary induction L₁On electric currentUnidirectional current equal to the output of described quasi-current source i_{in_dc}Negative value, i.e.Resonant capacitor voltageFor negative value, second switch S2, the 3rd switch S3 are on State, the first switch S1, the 4th switch S4 are off state, filter inductance L_dcOn electric current by second switch S2, the 3rd Switch S3 and former limit resonant network constitute primary Ioops；

Mode 1:t₀～t₁Time period, t₀Moment first switchs S1 and the 4th switch S4 conducting, auxiliary induction L₁On electric currentAt resonant capacitor voltageEffect under just become from negative, until at t₁Moment is equal to i_{in_dc}, at electric currentFor time negative, lead to Cross second switch S2-diode D4, the 3rd switch S3-diode D1 forms loop, at electric currentBecome timing, open by first Close S1-diode D3, the 4th switch S4-diode D2 forms loop, and circulation first is switching S1, second switch S2, the 3rd opening Close in the loop that S3 and the 4th switch S4 is constituted and flow, in this mode, filter inductance L_dcOn electric current directly by first switch S1-second switch S2, the 3rd switch S3-the 4th switch S4 constitute loop, without former limit resonant network；

Mode 2:t₁～(t₁+T_OV) time period, t₁Moment resonant capacitor voltageIt is still negative value, electric currentContinue to increase, t₂Moment isZero crossing, now, electric currentReach maximum, afterwards, electric currentStart to reduce, in this mode, circulation Flow, at t in the loop that first switch S1-the 4th switch S4 is constituted₁+T_OVIn the moment, second switch S2 and the 3rd switch S3 closes Disconnected, in this mode, filter inductance L_dcOn electric current directly by first switch S1-second switch S2, the 3rd switch S3-the 4th Switch S4 constitutes loop, without former limit resonant network；

Mode 3:(t₁+T_OV)～t₃Time period, in this mode, second switch S2 and the 3rd switch S3 turns off, and circulation exists Flow in the loop that first switch S1-diode D3, the 4th switch S4-diode D2 are constituted, originally second switch S2, the 3rd In switch S3, the electric current of flowing has been transferred to the diode D2 of its correspondence, diode D3 so that second switch S2, the 3rd switch S3 Carving voltage when off is approximation 0, it is achieved that ZVS, in this mode, and filter inductance L_dcOn electric current by the first switch S1, the Four switch S4 and former limit resonant network constitute loop, electric current i_L1For the electric current on filter inductance and loop current sum, at t₃Time Carve, electric current i_L1Unidirectional current i equal to the output of described quasi-current source_{in_dc}, loop current reduces to 0, and circulation flow path no longer exists, ring Stream disappears；

Mode 4:t₃～t₄Time period, the first switch S1 and the 4th switch S4 are in the conduction state, second switch S2 and the 3rd Switch S3 is off state, filter inductance L_dcOn electric current by the first switch S1, second switch S2 and former limit Resonance Neural Network Network constitutes primary Ioops；

t₄～t₅Time period is the lower half cycle of this circulation control circuit, corresponding, the first switch, the 4th switch are turning off Shi Shixian ZVS.

Compared with prior art, the technical scheme that the application provides, the technique effect or the advantage that have be: reduces circulation Peak value, it is possible to realize approximation zero current turning-on, zero voltage turn-off, reduce switching tube spoilage.

Accompanying drawing explanation

Fig. 1 is circulation control circuit figure；

Fig. 2 is the stable state oscillogram of circulation control circuit；

Fig. 3 a is the equivalent circuit diagram of mode 0；

Fig. 3 b is the equivalent circuit diagram of mode 1；

Fig. 3 c is the equivalent circuit diagram of mode 2；

Fig. 3 d is the equivalent circuit diagram of mode 3；

Fig. 3 e is the equivalent circuit diagram of mode 4；

Fig. 4 is overlapping conducting phase circulation equivalent circuit diagram；

Fig. 5 is the input of circulation control circuit, output waveform figure.

Detailed description of the invention

The embodiment of the present application is by providing a kind of induction electric energy based on auxiliary induction transmission circulation control circuit system, real Now approximate zero current turning-on, zero voltage turn-off, reduce circulation peak value, reduce the switching loss of switching tube, it is suppressed that resonance Bigger circulation between network and inversion network.

In order to be better understood from technique scheme, below in conjunction with Figure of description and specific embodiment, right Technique scheme is described in detail.

Embodiment

A kind of induction electric energy based on auxiliary induction transmission circulation control circuit system, as it is shown in figure 1, include by connecting DC source E_inWith filter inductance L_dcComposition quasi-current source, pulse generating circuit, high-frequency inversion network, former limit resonant network, Secondary resonant network, rectifying and wave-filtering network and load, wherein, described quasi-current source is connected with described high-frequency inversion network, for institute Stating high-frequency inversion network and provide unidirectional current, described pulse generating circuit is connected with described high-frequency inversion network, output control pulse Controlling the output waveform of described high-frequency inversion network, described high-frequency inversion network is connected with described former limit resonant network, output Square wave current gives described former limit resonant network, and described secondary resonant network receives the sinusoidal electricity of described former limit resonant network output Stream, described secondary resonant network by described rectifying and wave-filtering network with load be connected, by sinusoidal current after rectifying and wave-filtering defeated Going out to load, described high-frequency inversion network includes the first switch S1, second switch S2, the 3rd switch S3 and the 4th switch S4, It is provided with an auxiliary induction L between outfan and the described former limit resonant network of described high-frequency inversion network₁, for damping ring The rate of climb of stream and peak value, and in each PWM cycle of pulse generating circuit, all there is described first switch S1, second open Close S2, the 3rd switch S3 and the 4th switchs the time T that S4 simultaneously turns on_OV, i.e. the overlapping conducting time, on the one hand give filter inductance L_dcThere is provided current loop, on the other hand so that auxiliary induction L₁On electric current steadily commutate (from+i_{in_dc}It is converted into-i_{in_dc}, or Person is from-i_{in_dc}It is converted into+i_{in_dc})。

Wherein, described first switch S1 includes MOSFET pipe Q1 and antiparallel diode D1, described second switch S2 bag Include MOSFET pipe Q2 and antiparallel diode D2, described 3rd switch S3 and include MOSFET pipe Q3 and antiparallel diode D3, described 4th switch S4 include MOSFET pipe Q4 and antiparallel diode D4, wherein, the source electrode of described MOSFET pipe Q1 with The drain electrode of described MOSFET pipe Q2 connects, and the source electrode of described MOSFET pipe Q3 is connected with the drain electrode of described MOSFET pipe Q4, described The drain electrode of MOSFET pipe Q1 is connected with the drain electrode of described MOSFET pipe Q3, and the source electrode of described MOSFET pipe Q1 is managed with described MOSFET The drain electrode of Q4 connects, the positive pole of all diodes all with the source electrode connection of corresponding MOSFET pipe, the negative pole of all diodes all with The drain electrode of corresponding MOSFET pipe connects, and the grid of described MOSFET pipe is all connected with described pulse generating circuit, described MOSFET The source electrode of pipe Q1 is as the first outfan of described high-frequency inversion network, and the source electrode of described MOSFET pipe Q3 is inverse as described high frequency Becoming the second outfan of network, described former limit resonant network includes the resonant capacitance C of parallel connection_pWith resonant inductance L_p, and both are also Interlink point passes through described auxiliary induction L as the input of former limit resonant network, the first outfan of described high-frequency inversion network₁ It is connected with the input of described former limit resonant network, the second outfan of described high-frequency inversion network and described former limit resonant network Another input be connected.

The oscillogram of system when Fig. 2 show stable state, Fig. 3 (a), Fig. 3 (b), Fig. 3 (c), Fig. 3 (d), Fig. 3 (e) are respectively The equivalent circuit diagram of each mode during stable state.

Mode 0: at t₀Before moment, auxiliary induction L₁On electric currentUnidirectional current equal to the output of described quasi-current source i_{in_dc}Negative value, i.e.Resonant capacitor voltageFor negative value, second switch S2, the 3rd switch S3 are on State, the first switch S1, the 4th switch S4 are off state, filter inductance L_dcOn electric current by second switch S2, the 3rd Switch S3 and former limit resonant network constitute primary Ioops；

Mode 1:t₀-t₁Time period, t₀Moment first switchs S1 and the 4th switch S4 conducting, auxiliary induction L₁On electric currentAt resonant capacitor voltageEffect under just become from negative, until at t₁Moment is equal to i_{in_dc}, at electric currentFor time negative, lead to Cross second switch S2-diode D4, the 3rd switch S3-diode D1 forms loop, at electric currentBecome timing, open by first Close S1-diode D3, the 4th switch S4-diode D2 forms loop, and owing in MOSFET, electric current can be with two-way flow, and it is led Logical pressure drop is generally below its body diode, therefore circulation switchs S1, second switch S2, the 3rd switch S3 and the 4th switch S4 first Flow in the loop constituted, in this mode, filter inductance L_dcOn electric current directly by the first switch S1-second switch S2, the Three switch S3-the 4th switch S4 constitute loop, without former limit resonant network；

Mode 2:t₁-(t₁+T_OV) time period, t₁Moment resonant capacitor voltageIt is still negative value, electric currentContinue to increase, t₂ Moment isZero crossing, now, electric currentReach maximum, afterwards, electric currentStarting to reduce, in this mode, circulation exists Flow, at t in the loop that first switch S1-the 4th switch S4 is constituted₁+T_OVIn the moment, second switch S2 and the 3rd switch S3 turns off, In this mode, filter inductance L_dcOn electric current directly by first switch S1-second switch S2, the 3rd switch S3-the 4th open Close S4 and constitute loop, without former limit resonant network；

Mode 3:(t₁+T_OV)-t₃Time period, in this mode, second switch S2 and the 3rd switch S3 turns off, and circulation is the Flow in the loop that one switch S1-diode D3, the 4th switch S4-diode D2 are constituted, originally at second switch S2, the 3rd open Close the electric current of flowing in S3 and be transferred to the diode D2 of its correspondence, diode D3 so that second switch S2, the 3rd switch S3 exist Turning off moment voltage is approximation 0, it is achieved that ZVS, in this mode, and filter inductance L_dcOn electric current by first switch S1, the 4th Switch S4 and former limit resonant network constitute loop, electric currentFor the electric current on filter inductance and loop current sum, at t₃Moment, Electric currentUnidirectional current i equal to the output of described quasi-current source_{in_dc}, loop current reduces to 0, and circulation flow path no longer exists, and circulation disappears Lose；

Mode 4:t₃-t₄Time period, the first switch S1 and the 4th switch S4 are in the conduction state, second switch S2 and the 3rd Switch S3 is off state, filter inductance L_dcOn electric current by the first switch S1, second switch S2 and former limit Resonance Neural Network Network constitutes primary Ioops；

t₄-t₅Time period is the lower half cycle of this circulation control circuit, corresponding, the first switch, the 4th switch are when off Realize ZVS.

Knowable to the analysis of each mode above, it is achieved the condition of above-mentioned mode of operation has a three below:

(1) if owing to this main circuit suppresses first kind circulation, so, system operating frequency is more than ZVS frequency, i.e. f_s＞ f_ZVS；(2) all switching tubes need at t₁～t₃Turn off in time period, i.e. overlapping conducting time T_OVHave certain limitations.If switch Pipe is at t₁Front shutoff, due to i_L1Less than i_{in_dc}, auxiliary induction L₁Upper electric current i_L1To improve within a very short time to i_{in_dc}, produce Due to voltage spikes can add to turn off switching tube two ends, may damage switching tube；

(3) at overlapping conducting time T_OVStage, auxiliary induction L₁On electric current i_L1Have to be larger than filter inductance L_dcOn electricity Stream, otherwise cannot realize ZVS and turn off.As auxiliary induction L₁Electric current i_L1At overlapping conducting time T_OVInside it is consistently less than i_{in_dc}Time, The most there is not t₁～t₃In this stage, this just will necessarily produce the highest due to voltage spikes.

When above three condition all meets, circulation amplitude is suppressed, and four switching tubes all can realize ZVS and turn off.

Due in IPT system, the most former and deputy limit equal approximate resonance of resonant network, and Q-value is higher.Therefore, at weight Folded ON time T_OVIn, can be by former limit parallel resonance electric capacity C_pIt is approximately an alternating-current voltage source.Its voltage expression is:

Fig. 4 is circulation equivalent circuit diagram in overlapping ON time, can list following formula

$\begin{array}{c}{U}_{L_1}\left(t\right)=-U_{C_P}\left(t\right)=L_1\frac{{\mathrm{di}}_{L_1}\left(t\right)}{dt}\\ i_{L_1}\left(t\right)={\∫}_{t_0}^t\frac{-U_{C_P}\left(t\right)}{L_1}\·dt-i_{in\_dc}=U_{C_P\_peak}\frac{\cos (\mathrm{\ω}t-{\mathrm{\ωt}}_2)-\cos (-{\mathrm{\ωt}}_2)}{{\mathrm{\ωL}}_1}-i_{in\_dc}\end{array}---\left(2\right)$

At t₂Moment,i_L1Reach peak value:

$i_{L_1\_peak}=i_{L_1}\left(t_2\right)=U_{C_P\_peak}\frac{1-\cos (-{\mathrm{\ωt}}_2)}{{\mathrm{\ωL}}_1}-i_{in\_dc}---\left(3\right)$

From condition (3), i_{L1_peak}Have to be larger than i_{in_dc}, from formula (3), reduce L₁Size, can directly increase Big i_{L1_peak}.Therefore, it can by suitably choosing L₁Value meet condition (3).

One important feature of this circulation control circuit is constant voltage no-load voltage ratio.Circuit diagram 5 show circulation control circuit Input, output waveform figure, when system reaches stable state, power supply input power is:

The output of high-frequency inversion network is:

$\begin{array}{c}{P}_{inv\_out}=\frac{2}{T}{\∫}_{\mathrm{\θ}1}^{\mathrm{\θ}2}{i}_{in\_dc}{U}_{inv\_out\_peak}\sin \mathrm{\ω}t\·dt\\ =\frac{1}{\mathrm{\π}}{\∫}_{\mathrm{\θ}1}^{\mathrm{\θ}2}{i}_{in\_dc}{U}_{inv\_peak}\sin \mathrm{\θ}\·d\mathrm{\θ}=\frac{1}{\mathrm{\π}}{i}_{in\_dc}\·(-U_{inv\_out\_peak}\cos \mathrm{\θ}{|}_{\mathrm{\θ}1}^{\mathrm{\θ}2})\\ =\frac{1}{\mathrm{\π}}{i}_{in\_dc}{U}_{inv\_out\_peak}\·({\mathrm{cos\θ}}_1+\cos (\mathrm{\π}-{\mathrm{\θ}}_2\left)\right)\end{array}---\left(5\right)$

θ in formula₁、θ₂The initial phase angle being not zero for half period medium-high frequency inversion network output voltage and end phase angle, with Resonant capacitor voltagePhase angle is reference.

Ignore the loss of high-frequency inversion network breaker in middle pipe, L_dcLoss, then the output of high-frequency inversion network is with straight Stream power supply input power is equal.

$\begin{array}{c}{P}_{\sup ple\_in}=P_{inv\_out}\\ U_{inv\_out\_peak}=E_{in}\frac{\mathrm{\π}}{({\mathrm{cos\θ}}_1+\cos (\mathrm{\π}-{\mathrm{\θ}}_2\left)\right)}\end{array}---\left(6\right)$

At [θ₁,π-θ₂Time between], high-frequency inversion net output voltage is directly output to resonant capacitance two ends.It is also contemplated that θ₁、π-θ₂Less, therefore typically have following formula to set up:

U_{Cp_peak}=U_{inv_out_peak} (7)

To auxiliary induction L₁For former limit resonant network below, owing to former limit resonant network is near resonant frequency, Its energy is the overwhelming majority transmitted by first-harmonic, and therefore, the input power of former limit resonant network is expressed as:

$P_{res\_in}=\frac{{\left(U_{Cp\_peak}\right)}^2}{2\left|Z_{parallel}\right|}cos\mathrm{\θ}---\left(8\right)$

In formula (8), θ is resonant network input impedance angle, is alsoAnd i_L1Fundamental harmonic wave between phase contrast, Z_parallelIt it is the total impedance (series resonant network of secondary use herein) of former limit resonant network and late-class circuit thereof.

$Z_{parallel}=({\mathrm{j\ωL}}_P+\frac{{\mathrm{\ω}}^2{M}^2}{{\mathrm{j\ωL}}_S+\frac{1}{{\mathrm{j\ωC}}_S}+R_{L\_eq}})//\frac{1}{{\mathrm{j\ωC}}_S}=\frac{1}{\frac{1}{({\mathrm{j\ωL}}_P+\frac{{\mathrm{\ω}}^2{M}^2}{{\mathrm{j\ωL}}_S+\frac{1}{{\mathrm{j\ωC}}_S}+R_{L\_eq}})}+{\mathrm{j\ωC}}_S}$

In formula (9)

Convolution (6), (7), (8), the input power of resonant network is:

$P_{res\_in}=\frac{{\mathrm{\π}}^2{E}_{in}^2}{2{({\mathrm{cos\θ}}_1+\cos (\mathrm{\π}-{\mathrm{\θ}}_2\left)\right)}^2}\·\frac{\cos \mathrm{\θ}}{\left|Z_{parallel}\right|}---\left(10\right)$

In real system, due to L in real system₁The least, t₀～t₃Time period accounts for the least of whole cycle Point, therefore θ₁、π-θ₂For the whole cycle the least, can ignore, then (10) formula can be reduced to:

$P_{res\_in}\≈\frac{{\mathrm{\π}}^2{E}_{in}^2}{8}\·\frac{cos\mathrm{\θ}}{\left|Z_{parallel}\right|}---\left(11\right)$

Ignore L_dc、L₁With the loss on each switching tube, the most former limit resonant network input power is equal with power supply input power.

$E_{in}{i}_{in\_dc}=\frac{{\mathrm{\π}}^2{E}_{in}^2}{8}\·\frac{cos\mathrm{\θ}}{\left|Z_{parallel}\right|}---\left(12\right)$

Therefore,

Next the voltage change ratio of lower whole system will be analyzed.For high-frequency inversion network, its voltage change ratio is:

$M_1=\frac{U_{inv\_out\_peak}}{E_{in}}=\frac{\mathrm{\π}}{({\mathrm{cos\θ}}_1+\cos (\mathrm{\π}-{\mathrm{\θ}}_2\left)\right)}---\left(14\right)$

Due to θ₁、π-θ₂It is all higher than 0, but value is less, typically has 1 ＜ (cos θ₁+cos(π-θ₂)) ＜ 2, therefore, high frequency is inverse The voltage change ratio becoming network only changes in smaller range.

For former limit in parallel resonant network, its voltage change ratio is

$M_2=\frac{U_{R_L}}{U_{inv\_out\_peak}}=\frac{j\mathrm{\ω}M}{({\mathrm{j\ωL}}_p+R_{L_p})+\frac{({\mathrm{j\ωL}}_p+R_{L_p})({\mathrm{j\ωL}}_s+R_{L_s}+\frac{1}{{\mathrm{j\ωC}}_s})+{\mathrm{\ω}}^2{M}^2}{R_L}}---\left(15\right)$

As load R_LRelatively big andWhen can ignore, (15) formula can abbreviation be

$M_2\≈\frac{j\mathrm{\ω}M}{({\mathrm{j\ωL}}_p+R_{L_p})}\≈\frac{M}{L_p}---\left(16\right)$

Now M₂No longer change, approximately constant with frequency and the change of load.

Then the voltage change ratio of whole system is

$M_{sys}=M_1{M}_2\≈\frac{\mathrm{\π}}{({\mathrm{cos\θ}}_1+\cos (\mathrm{\π}-{\mathrm{\θ}}_2\left)\right)}\frac{M}{L_p}---\left(17\right)$

Consider further that θ₁、π-θ₂For the whole cycle the least, can ignore, then the voltage change ratio of whole system is:

$M_{sys}\≈\frac{\mathrm{\π}}{2}\frac{M}{L_p}---\left(18\right)$

By formula (18) it can be seen that the voltage change ratio of this system is when loading value and being bigger, basic with load and frequency without Close.Therefore, constant voltage no-load voltage ratio is one critically important feature of this system, in the occasion that some is the highest to voltage request, and can not Need to add extra voltage regulator, it becomes possible to realize the output of metastable voltage.And this system to operating frequency also without Requirement, when conversion frequency, system output characteristics is without significant change, during real system work, can be by selecting suitable work Working frequency, makes working state of system reach optimum.

Selecting in terms of switching tube, need this circuit is opened switch tube voltage, current stress and switch, shutoff moment State is analyzed.

The symmetry run in view of system in the cycle, the voltage of some switching tube derived, current stress It is the voltage of four switching tubes, current stress.Mainly for t₀～t₄Time period is analyzed.

Switching tube S2, S3 are at t₃～t₄Stage is off state, and bears forward voltage.The drain-source of its switching tube The voltage that two ends are born is equal toSo the maximum voltage that switching tube drain-source two ends are born isThis value Can be determined by formula (6), (7).

Switching tube S1, S4 are at t₀～t₄Time period is on the stage all the time, in non-overlapped conducting phase t₃～t₄, on it The electric current flow through is i_{in_dc}。

At overlapping conducting stage t₀～t₃, the electric current that all switching tubes flow through is synthesized by two parts electric current, and Part I is L_dcOn electric current, owing to this stage all switching tubes are both turned on, so current uniform, the electric current that all switching tubes flow through isPart II is L₁On electric current, the first switching tube S1, the 4th switching tube S4 upstream overcurrent areSecond switch Pipe S2, the 3rd switching tube S3 upstream overcurrent are

To sum up, in the overlapping conducting stage, the electric current that the first switching tube S1, the 4th switching tube S4 flow through isThe The electric current flow through on two switching tube S2, the 3rd switching tube S3 is

The maximum of the electric current then flow through on the first switching tube S1, the 4th switching tube S4 isBut due toValue cannot accurately calculate, therefore current stress cannot determine in advance, can only rely on experimental data.

Further, when selecting switching tube, also need to consider practical devices current changing rateRestriction.Because leading in overlap Logical stage current rate of change is relatively big, may be beyond the maximum current slew rate of some devices.

First switching tube S1, the 4th switching tube S4 are at t₀Moment is open-minded, and after opening, the electric current that it flows through isDue to nowEqual to-i_{in_dc}, it is possible to realize zero current turning-on characteristic.

Second switch pipe S2, the 3rd switching tube S3 are at t₃Moment turns off, and has no progeny in pass, and its anti-paralleled diode turns on, therefore, It is capable of zero voltage turn-off characteristic.

In sum, the first switch S1, second switch S2, the 3rd switch S3 and the 4th switch S4 are capable of zero current and open Logical, zero voltage turn-off characteristic.

Alternatively preferred technical scheme, described first switch S1, second switch S2, the 3rd switch S3 and the 4th Switch S4 can be selected for IGBT insulated gate bipolar transistor, because the characteristic of its zero voltage turn-off, when can eliminate IGBT shutoff Current tail phenomenon.

In above-described embodiment of the application, by providing a kind of induction electric energy based on auxiliary induction transmission circulation to control electricity Road system, is provided with an auxiliary induction L between the outfan and described former limit resonant network of described high-frequency inversion network₁, For damping the rate of climb and the peak value of circulation, and in each PWM cycle of pulse generating circuit, all have described first open Close the time T that S1, second switch S2, the 3rd switch S3 and the 4th switch S4 simultaneously turn on_OV, i.e. the overlapping conducting time, on the one hand To filter inductance L_dcThere is provided current loop, on the other hand so that auxiliary induction L₁On electric current steadily commutate, this system realizes near Like zero current turning-on, zero voltage turn-off, reduce circulation peak value, reduce the switching loss of switching tube, it is suppressed that resonant network And the bigger circulation between inversion network.

It should be pointed out that, described above is not limitation of the present invention, the present invention is also not limited to the example above, Change, modification that those skilled in the art are made in the essential scope of the present invention, add or replace, also should Belong to protection scope of the present invention.

Claims (4)

1. induction electric energy based on an auxiliary induction transmission circulation control circuit system, including by the DC source E connected_inWith Filter inductance L_dcComposition quasi-current source, pulse generating circuit, high-frequency inversion network, former limit resonant network, secondary resonant network, Rectifying and wave-filtering network and load, wherein, described quasi-current source is connected with described high-frequency inversion network, for described high-frequency inversion network Thering is provided unidirectional current, described pulse generating circuit is connected with described high-frequency inversion network, and output control pulse controls described high frequency The output waveform of inversion network, described high-frequency inversion network is connected with described former limit resonant network, and output square wave current is given described Former limit resonant network, described secondary resonant network receives the sinusoidal current of described former limit resonant network output, described secondary resonance Network is connected with load by described rectifying and wave-filtering network, is exported by sinusoidal current to load, its feature after rectifying and wave-filtering Being, described high-frequency inversion network includes the first switch S1, second switch S2, the 3rd switch S3 and the 4th switch S4, described It is provided with an auxiliary induction L between outfan and the described former limit resonant network of high-frequency inversion network₁, for damping circulation The rate of climb and peak value, and in each PWM cycle of pulse generating circuit, all there is described first switch S1, second switch The time T that S2, the 3rd switch S3 and the 4th switch S4 simultaneously turn on_OV, i.e. the overlapping conducting time, on the one hand give filter inductance L_dc There is provided current loop, on the other hand so that auxiliary induction L₁On electric current steadily commutate.

Induction electric energy based on auxiliary induction the most according to claim 1 transmission circulation control circuit system, its feature exists In, described first switch S1 includes that MOSFET pipe Q1 and antiparallel diode D1, described second switch S2 include that MOSFET manages Q2 and antiparallel diode D2, described 3rd switch S3 include MOSFET pipe Q3 and antiparallel diode D3, the described 4th Switch S4 includes MOSFET pipe Q4 and antiparallel diode D4, wherein, the source electrode of described MOSFET pipe Q1 and described MOSFET The drain electrode of pipe Q2 connects, and the source electrode of described MOSFET pipe Q3 is connected with the drain electrode of described MOSFET pipe Q4, described MOSFET pipe Q1 Drain electrode be connected with the drain electrode of described MOSFET pipe Q3, the drain electrode of the source electrode of described MOSFET pipe Q1 and described MOSFET pipe Q4 is even Connecing, the positive pole of all diodes all connects with the source electrode of corresponding MOSFET pipe, the negative pole of all diodes all with corresponding MOSFET The drain electrode of pipe connects, and the grid of described MOSFET pipe is all connected with described pulse generating circuit, the source electrode of described MOSFET pipe Q1 As the first outfan of described high-frequency inversion network, the source electrode of described MOSFET pipe Q3 is as the of described high-frequency inversion network Two outfans, described former limit resonant network includes the resonant capacitance C of parallel connection_pWith resonant inductance L_p, and both sys node conducts The input of former limit resonant network, the first outfan of described high-frequency inversion network passes through described auxiliary induction L₁With described former limit The input of resonant network is connected, and another of the second outfan of described high-frequency inversion network and described former limit resonant network is defeated Enter end to be connected.

Induction electric energy based on auxiliary induction the most according to claim 1 transmission circulation control circuit system, its feature exists In, described first switch S1, second switch S2, the 3rd switch S3 and the 4th switch S4 can be selected for IGBT insulated gate bipolar crystal Pipe.

Induction electric energy based on auxiliary induction the most according to claim 2 transmission circulation control circuit system, its feature exists In, meet (1) system operating frequency more than ZVS frequency, i.e. f when simultaneously_s＞ f_ZVS；(2) all switching tubes need at t₁～t₃'s Turn off in time period；And the time T that (3) turn at the same time_OVThe auxiliary induction L in stage₁On electric currentHave to be larger than filtering Inductance L_dcOn electric current these three under the conditions of, achieve following mode during described circulation control circuit stable state:

Mode 0: at t₀Before moment, auxiliary induction L₁On electric currentUnidirectional current i equal to the output of described quasi-current source_{in_dc}'s Negative value, i.e.Resonant capacitor voltageFor negative value, second switch S2, the 3rd switch S3 are in the conduction state, the One switch S1, the 4th switch S4 are off state, filter inductance L_dcOn electric current by second switch S2, the 3rd switch S3 with And former limit resonant network constitutes primary Ioops；

Mode 1:t₀～t₁Time period, t₀Moment first switchs S1 and the 4th switch S4 conducting, auxiliary induction L₁On electric current? Resonant capacitor voltageEffect under just become from negative, until at t₁Moment is equal to i_{in_dc}, at electric currentFor time negative, by Two switch S2-diode D4, the 3rd switch S3-diode D1 form loop, at electric currentBecome timing, by the first switch S1-diode D3, the 4th switch S4-diode D2 form loop, and circulation switchs S1, second switch S2, the 3rd switch first Flow in the loop that S3 and the 4th switch S4 is constituted, in this mode, filter inductance L_dcOn electric current directly by first switch S1- Second switch S2, the 3rd switch S3-the 4th switch S4 constitute loop, without former limit resonant network；

Mode 2:t₁～(t₁+T_OV) time period, t₁Moment resonant capacitor voltageIt is still negative value, electric currentContinue to increase, t₂Time Quarter isZero crossing, now, electric currentReach maximum, afterwards, electric currentStarting to reduce, in this mode, circulation is the Flow, at t in the loop that one switch S1-the 4th switch S4 is constituted₁+T_OVIn the moment, second switch S2 and the 3rd switch S3 turns off, In this mode, filter inductance L_dcOn electric current directly by first switch S1-second switch S2, the 3rd switch S3-the 4th switch S4 constitutes loop, without former limit resonant network；

Mode 3:(t₁+T_OV)～t₃Time period, in this mode, second switch S2 and the 3rd switch S3 turns off, and circulation is opened first Close in the loop of S1-diode D3, the 4th switch S4-diode D2 composition and flow, originally at second switch S2, the 3rd switch S3 The electric current of middle flowing has been transferred to the diode D2 of its correspondence, diode D3 so that second switch S2, the 3rd switch S3 are turning off Moment voltage is approximation 0, it is achieved that ZVS, in this mode, and filter inductance L_dcOn electric current by first switch S1, the 4th switch S4 and former limit resonant network constitute loop, electric currentFor the electric current on filter inductance and loop current sum, at t₃Moment, electric currentUnidirectional current i equal to the output of described quasi-current source_{in_dc}, loop current reduces to 0, and circulation flow path no longer exists, and circulation disappears；

Mode 4:t₃～t₄Time period, the first switch S1 and the 4th switch S4 are in the conduction state, second switch S2 and the 3rd switch S3 is off state, filter inductance L_dcOn electric current by the first switch S1, second switch S2 and former limit resonant network structure Become primary Ioops；

t₄～t₅Time period is the lower half cycle of this circulation control circuit, corresponding, the first switch, the 4th switch are real when off Existing ZVS.