CN104578806A - Cascade bilateral soft switch DC/DC circuit topology - Google Patents

Cascade bilateral soft switch DC/DC circuit topology Download PDF

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Publication number
CN104578806A
CN104578806A CN201410836076.8A CN201410836076A CN104578806A CN 104578806 A CN104578806 A CN 104578806A CN 201410836076 A CN201410836076 A CN 201410836076A CN 104578806 A CN104578806 A CN 104578806A
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connected
switch
circuit
dc
vt
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CN201410836076.8A
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CN104578806B (en
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万晓凤
谌新
余运俊
胡伟
康利平
郑博嘉
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南昌大学
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    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00Conversion of dc power input into dc power output
    • H02M3/22Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/337Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00Details of apparatus for conversion
    • H02M2001/0048Circuits or arrangements for reducing losses
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00Details of apparatus for conversion
    • H02M2001/0048Circuits or arrangements for reducing losses
    • H02M2001/0054Transistor switching losses
    • H02M2001/0058Transistor switching losses by employing soft switching techniques, i.e. commutation of transistor when voltage applied to it is zero and/or when current flowing through it is zero
    • YGENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02BCLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion
    • Y02B70/14Reduction of losses in power supplies
    • Y02B70/1416Converters benefiting from a resonance, e.g. resonant or quasi-resonant converters
    • Y02B70/1433Converters benefiting from a resonance, e.g. resonant or quasi-resonant converters in galvanically isolated DC/DC converters
    • YGENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02BCLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion
    • Y02B70/14Reduction of losses in power supplies
    • Y02B70/1491Other technologies for reduction of losses, e.g. non-dissipative snubbers, diode reverse recovery losses minimisation, zero voltage switching [ZVS], zero current switching [ZCS] or soft switching converters

Abstract

The invention discloses a cascade bilateral soft switch DC/DC circuit topology. The cascade bilateral soft switch DC/DC circuit topology comprises a preceding stage boosted circuit, an auxiliary circuit, a post-stage push pull transformer and a full-bridge circuit, which are connected in series in sequence, wherein the auxiliary circuit comprises a resonant inductor Lr, a resonant capacitor Cr2, an auxiliary switch VT2 containing an anti-parallel body diode VD2, fast recovery diodes VD9 and VD10, and a relay K; one end of the resonant inductor Lr is connected with the negative electrode of the fast recovery diode VD9; the other end of the resonant inductor Lr is respectively connected with the positive electrode of the fast recovery diode VD10 and the drain electrode of the auxiliary switch VT2; the source electrode of the auxiliary switch VT2 is connected with the anode of the fast recovery diode VD10; the negative electrode of the fast recovery diode VD10 is connected with one end of the relay K; the other end of the relay K is respectively connected with the negative electrode of the resonant capacitor Cr2 and the anode of the fast recovery diode VD9. The cascade bilateral soft switch DC/DC circuit topology is simple and reliable in control, simple in circuit structures, easy to realize, low in device cost, low in switch loss, low in voltage stress of the switch, high in conversion efficiency and low in circuit conduction loss.

Description

级联双向软开关DC/DC电路拓扑 Cascaded bidirectional soft switching DC / DC circuit topology

技术领域 FIELD

[0001 ] 本发明属于电动汽车技术领域,特别涉及电动汽车电路拓扑。 [0001] The present invention belongs to the technical field of electric vehicles, electric vehicles and more particularly to circuit topology. 技术背景 technical background

[0002] 目前双向DC/DC变换器的电路拓扑一般分为两类:一类是非隔离型,主要特点是变换器结构简单,体积小,重量轻,功率小,效率高,但是只适用于低功率无需电气隔离的场合;另一类则是隔离型,通过引入变压器不仅解决了低压侧与高压侧的电气隔离,而且使得变换器的功率大幅度提高,但是大功率场合往往产生开关管应力大、开关损耗严重、电磁性能差等问题难以解决。 [0002] It's circuit topology bidirectional DC / DC converter is generally divided into two categories: a non-isolated, the main converter is characterized by simple structure, small size, light weight, low power, high efficiency, but only for low where no electrical isolation of power; the other is isolated, not only solved by the introduction of low-voltage side of the transformer and electrically isolated from the high pressure side, and such that the power converter is greatly improved, but high power applications tend to generate large stress switch , switching loss is serious, and poor electromagnetic properties difficult to solve.

发明内容 SUMMARY

[0003] 本发明目的是提供一种结构简单,易于实现,开关损耗少,器件成本低的适用于电动汽车的级联双向软开关DC/DC电路拓扑。 [0003] The object of the present invention is to provide a simple structure, easy to implement, low switching losses, low-cost device suitable for an electric vehicle cascaded bidirectional soft switching DC / DC circuit topology.

[0004] 本发明是通过以下技术方案实现的。 [0004] The present invention is achieved by the following technical solutions.

[0005] 本发明所述的级联双向软开关DC/DC电路拓扑,它包括前级升压电路、辅助电路、 后级推挽变压器、全桥电路,它们之间依次串接。 [0005] the soft switch cascaded bidirectional DC / DC circuit topology of the present invention, which includes a front-stage booster circuit, auxiliary circuit, the push-pull transformer stage, a full bridge circuit, in turn connected in series therebetween. 其特征是所述的辅助电路包括谐振电感L,,谐振电容(;2,内含反并联体二极管VD2的辅助开关管VT2,快恢复二极管VD9、VD1(I,继电器K;其中,谐振电感L,的一端连于快恢复二极管VD9的阴极,谐振电感L,的另一端分别与谐振电容(;2的正极、辅助开关管VT2的漏极相连,辅助开关管VT2的源极与快恢复二极管VD1Q 的阳极相连,快恢复二极管VD1(I的阴极连于继电器K的一端,继电器K的另一端分别与谐振电容(;2的负极、快恢复二极管VD9的阳极相连。 Wherein said auxiliary circuit includes a resonant inductor L ,, resonant capacitor (; 2, containing the anti-parallel body diode VD2 auxiliary switch VT2, fast recovery diodes VD9, VD1 (I, K relay; wherein resonant inductor L , one end connected to the cathode of the fast recovery diode VD9, L, of the other end of the resonant inductor and resonant capacitor, respectively (; source of positive electrode 2, the drain is connected to the auxiliary switch VT2, VT2 pole auxiliary switch and fast recovery diode VD1Q an anode connected to the fast recovery diodes VD1 (I connected to one end of a cathode K of the relay, the other end of the relay K respectively and the resonant capacitor (; a negative electrode 2, the anode of the fast recovery diode is connected VD9.

[0006] 所述的前级升压电路包括低压侧直流电源%,滤波电容Ci,升压电感U,内含反并联体二极管VDi的主开关管VTi,钳位电容Crt; [0006] The front-stage booster circuit includes a low-side DC power supply%, smoothing capacitor Ci, the boost inductor U, containing the primary anti-parallel body diode of switch VDi the VTi, clamp capacitor Crt;

[0007] 其中,低压侧直流电源%的正极与升压电感Li的一端相连,升压电感L亦另一端连于主开关管VI\的漏极,主开关管VTi的源极与低压侧直流电源的负极相连,滤波电容Q正向并联于低压侧直流电源i^,钳位电容正向并联于主开关管VT:的漏源极,主开关管VI\的漏极作为前级升压电路的正极输出端,主开关管源极作为前级升压电路的负极输出端。 [0007] wherein the low pressure is connected to the positive electrode side of the DC power supply% Li and one end of the boost inductor, L is also connected to the other end of the boost inductor main switch Vl \ a drain, a source electrode of the main switch VTi and the low-side DC is connected to the negative power supply filter capacitor connected in parallel with the forward Q low voltage side of the DC power source i ^, the forward clamping capacitor connected in parallel to the main switch VT: drain-source main switch Vl \ pre-stage of the booster circuit as the drain the positive output terminal of the main switch of the source output of the preceding stage as the negative booster circuit.

[0008] 所述的辅助电路包括谐振电感Ly谐振电容(;2,内含反并联体二极管乂仏的辅助开关管VT2,快恢复二极管VD9、VD1Q,继电器K; Auxiliary circuit [0008] The resonant inductor Ly comprises a resonant capacitor (; 2, containing the anti-parallel body diode of the auxiliary switch qe Fo VT2, fast recovery diodes VD9, VD1Q, relay K;

[0009] 其中,谐振电感L的一端作为辅助电路的正极输入端,连于前级升压电路的正极输出端,谐振电感L,的另一端分别与谐振电容C,2的正极、辅助开关管VT2的漏极相连,辅助开关管VT2的源极作为辅助电路的负极输入端,分别与前级升压电路的负极输出端、快恢复二极管VD1(I的阳极相连,快恢复二极管VD1(|的阴极连于继电器K的一端,继电器K的另一端分别与谐振电容(;2的负极、快恢复二极管VD9的阳极相连,快恢复二极管VD9的阴极连于前级升压电路的正极输出端,并作为辅助电路的正极输出端,快恢复二极管VD1(I的阳极作为辅助电路的负极输出端。 [0009] where, L is the inductance end of the resonance circuit as an auxiliary input terminal of the positive electrode, is connected to the front stage of the positive output terminal of the booster circuit, resonant inductor L, respectively, and the other end of the resonant capacitor C, the positive electrode 2, the auxiliary switch VT2 is connected to the drain of the auxiliary switching tube VT2 source electrode as the negative input terminal of the auxiliary circuit, respectively, and a negative output terminal of the preceding stage booster circuit, fast recovery diodes VD1 (I connected to the anode of the fast recovery diode VD1 (| a connected to the end of the cathode K of the relay, the other end of the relay K respectively and the resonant capacitor (; negative electrode 2 is connected to the anode of the fast recovery diode VD9, VD9 fast recovery diode connected to the cathode of the front-stage booster circuit of the positive electrode output terminal, and as the positive output terminal of the auxiliary circuit, the fast recovery diode VD1 (I anode as the negative terminal of the auxiliary output circuit.

[0010] 所述的后级推挽变压器包括内含反并联体二级管VD3的功率开关管VT3,内含反并联体二级管VD4的功率开关管VT4,原边三端口(两个同名端)、副边两端口(一个同名端) 的变压器; [0010] The rear stage push-pull transformer comprising a diode anti-parallel VD3 inclusion body power switch tube VT3, containing anti-parallel body diode of the power switch VT4 VD4, primary three-port (two with the same name end), two secondary ports (a dotted terminal) of the transformer;

[0011] 其中,变压器原边中间的同名端作为后级推挽变压器的正极输入端,与辅助电路的正极输出端相连,功率开关管冗3的漏极连于变压器原边的另一同名端,功率开关管VT3 的源极作为后级推挽变压器的负极输入端,分别与辅助电路的负极输出端、功率开关管VT4 的源极相连,功率开关管VT4的漏极连于变压器原边的非同名端,功率开关管VT3、¥1'4组成一对推挽开关管,变压器副边的同名端作为后级推挽变压器的正极输出端,变压器副边的非同名端作为后级推挽变压器的负极输出端。 [0011] wherein, the dot end of the primary side of the transformer as an intermediate positive input of the subsequent stage push-pull transformer, is connected to the positive output terminal of the auxiliary circuit, the drain of the power switch 3 is connected to the other redundant dotted terminal of the primary side of the transformer , the power source switch of VT3 electrode as a negative electrode input terminal of the rear stage push-pull transformer, respectively, and the negative terminal of the auxiliary output circuit, a power source switch is connected to the source VT4, VT4 power switch drain connected to the primary side of the transformer non-dot end, the power switch tube VT3, ¥ 1'4 form a push-pull switch, the dot end of the secondary side of the transformer as a positive electrode output terminal of the rear stage push-pull transformer, the non-dot end of the secondary side of the transformer as a push-pull stage after the negative output of the transformer.

[0012] 所述的全桥电路包括饱和电感1^2,继电器K,隔直电容C2,内含反并联体二极管VD5、输出结电容C5的功率开关管VT5,内含反并联体二极管VD6、输出结电容C6的功率开关管VT6,内含反并联体二极管VD7、输出结电容C7的功率开关管VT7,内含反并联体二极管VD8、 输出结电容C8的功率开关管VT8,滤波电容Q,高压侧直流电源uH; [0012] The full bridge circuit comprises a saturable inductor 1 ^ 2, relay K, blocking capacitor C2, diode VD5 intron, the output node of the capacitor C5 anti-parallel power switch tube VT5 body, containing the anti-parallel body diode VD6, the output junction capacitance of the power switch C6 VT6, containing the anti-parallel body diode VD7, capacitor C7 the output node of the power switch VT7, containing the anti-parallel body diode VD8, the output junction capacitance of the power switch C8 VT8, filter capacitor Q, uH Tolerance high side DC power supply;

[0013] 其中,饱和电感L2的一端作为全桥电路的正极输入端,与后级推挽变压器的正极输出端相连,饱和电感L2的另一端连于隔直电容(:2的正极,继电器K并联于饱和电感1^2,隔直电容C2的负极分别与功率开关管VT5的源极、功率开关管VT7的漏极相连,功率开关管VT5 的漏极分别与功率开关管VT6的漏极、滤波电容q的正极、高压侧直流电源uH的正极相连, 功率开关管VT7的源极分别与功率开关管VT8的源极、滤波电容C^的负极、高压侧直流电源%的负极相连,功率开关管VT8的漏极作为全桥电路的负极输入端,分别与后级推挽变压器的负极输出端、功率开关管VT6的源极相连,功率开关管VT5、VT7组成全桥电路的超前桥臂, 功率开关管VT5、VT7组成全桥电路的滞后桥臂。 [0013] wherein, as a full bridge circuit, the positive input end of the saturable inductor L2, and the positive output terminal connected to the subsequent stage push-pull transformer, saturable inductor L2 is connected to the other end of the blocking capacitor (: positive electrode 2, the relay K in parallel with the saturable inductor 1 ^ 2, the anode compartment, respectively, blocking capacitor C2 and the source VT5 pole power switch, the power switch connected to the drain VT7, the drain of the power switch and the power switch VT5 are the drain of VT6, positive filter capacitor of q, the positive high voltage side of the DC power supply uH is connected to a source VT7 power switch poles are poles of the source power switch VT8, the filter capacitor C ^ negative, high voltage side of the DC power supply% of the negative electrode is connected to the power switch VT8 drain tube as the negative input terminal of the full bridge circuit, respectively, and the negative output terminal of the rear stage push-pull transformer, the power switch is connected to the source electrode of VT6, power switch VT5, VT7 composition lead leg full bridge circuit, power switch VT5, VT7 composition lagging leg full bridge circuit.

[0014] 本发明的特点和技术效果: [0014] The technical features and effects of the invention:

[0015] 1、电路中的所有开关管均为PWM控制方式,低压侧驱动电路无需电气隔离,控制简单可靠; [0015] 1, all tubes are switching circuit PWM control, low side driver circuit without electrical isolation, control is simple and reliable;

[0016] 2、辅助电路仅由一个开关管和简单的无源器件组成,复杂程度大大降低,整个电路结构简单,易于实现,器件成本低; [0016] 2, the auxiliary circuit switch only by a simple passive devices and compositions, greatly reduces the complexity, the overall circuit configuration is simple, easy to implement, low cost devices;

[0017] 3、电路中的所有开关管均能实现软开关,不仅降低了开关损耗,减小了开关管的电压应力,还有效提尚了变换效率; [0017] 3, all switching circuit tube can achieve soft switching, not only reduces the switching losses, reducing the switch voltage stress, further still effectively improve the conversion efficiency;

[0018] 4、升压变换时,主开关管VI\和推挽开关管VT3、VT4三者在任意时刻仅有一个导通,且辅助开关管工作时间极短,所以电路的通态损耗也较小。 [0018] 4, the step-up transformation, the main switch Vl \ and push-pull switch VT3, VT4 three at any one time only one is turned on, and the auxiliary switch working time is extremely short, so the on-state loss of the circuit is also small.

附图说明 BRIEF DESCRIPTION

[0019] 图1为本发明级联双向软开关DC/DC电路拓扑。 [0019] FIG 1 cascaded bidirectional soft switching DC / DC circuit topology of the present invention.

[0020] 图2为升压变换时的电路拓扑。 [0020] FIG. 2 is a circuit topology when upconverting.

[0021] 图3为升压变换时的工作波形。 [0021] FIG. 3 is a waveform when the working upconverting.

[0022] 图4为降压压变换时的电路拓扑。 [0022] FIG. 4 is a circuit topology when the buck voltage conversion.

[0023] 图5为降压变换时的工作波形。 [0023] FIG. 5 is an operation waveform when the step-down conversion.

具体实施方式 Detailed ways

[0024] 本发明所述的级联双向软开关DC/DC电路拓扑参见附图1,它在实际应用中分为升压变换时的正向工作状态和降压变换时的逆向工作状态,当升压变换时,高压侧直流电源%须转换为负载形式,即电动机的阻抗;当降压变换时,低压侧直流电源h须转换为负载形式,即蓄电池的阻抗。 [0024] Soft cascaded bidirectional switch according to the present invention, DC / DC circuit topology Referring to Figure 1, in practical applications it is divided into the reverse operation state when a working condition when the down conversion and upconverting, when when boost conversion, high side DC power is converted to% be supported form, i.e., the impedance of the motor; when the down conversion, low-side DC power supply to be converted to a load in the form of h, i.e., the impedance of the battery. 为便于理解,在此统一将负载形式作空载处理。 For ease of understanding, this unified processing load will be supported form.

[0025] 下面结合附图和工作原理对本发明的具体实施方式进行详细说明。 [0025] The following specific embodiments of the present invention will be described in detail in conjunction with the accompanying drawings and works.

[0026] 具体的升压变换原理如下所述。 [0026] Specifically upconverting the principle is as follows.

[0027] 当汽车在启动、加速或爬坡时,控制器关闭高压侧VT5〜VT8的驱动信号,继电器K闭合,使饱和电感L2被短路,低压侧的辅助电路被导通,参见附图2。 [0027] When the car start, acceleration or climbing, the controller closes VT5~VT8 high side driving signal, the relay K is closed, so that the saturable inductor L2 is short-circuited, a low pressure side of the auxiliary circuit is turned on, see FIG. 2 . C2作为隔直电容,抑制升压电路的偏磁效应。 C2 as a DC blocking capacitor bias magnetic effect, suppression of the booster circuit. 低压侧电压先通过主开关管和升压电感Li构成的升压电路升压到一定值,然后推挽变压器再次升压,最后由VD5〜VD8全桥整流输出。 First low-side voltage boosted by the booster circuit to a certain value and the main switch of the boost inductor Li configuration, push-pull transformer and then boosted again, and finally by VD5~VD8 full bridge rectifier output.

[0028] 为简化分析,做如下假设:所有元件均为理想状态;忽略变压器的漏感。 [0028] To simplify the analysis, the following assumptions: All components are ideal; ignore leakage inductance of the transformer. 变换器升压变换时的工作波形参见附图3,半个周期可分为8个模态,后半个周期的工作过程与前半个周期基本相同,只是换到另一个推挽管工作的区别而已,故只介绍前半个周期。 Work transition waveform converter boosting Referring to Figure 3, a half cycle can be divided into 8 modes, during operation of the front half cycle after half cycle is substantially the same, but another change to the difference of the push-pull pipe work only, it only describes the first half of the cycle.

[0029] 模态1 (tQ〜tJ:令tQ时刻之前,开关管VTpVT#VT4关断,VT3导通,系统处于稳定状态,且升压电路经推挽管VT3将功率传送至全桥整流电路中。t^时刻,辅助电路中VT2 的电流IVT2为零,在k的作用下VT2实现ZCS开通。此阶段,流经k的电流I&开始从零线性增大,而VT3的电流IVT3逐渐减小。 [0029] Mode 1 (tQ~tJ: Order before tQ time, switch off VTpVT # VT4, VT3 conduction, the system is stable, and the booster circuit is a push-pull tube VT3 will deliver power to full bridge rectifier circuit .t ^ in time, the auxiliary current in the circuit is zero IVT2 VT2, under the effect of the k VT2 achieve ZCS turn. this stage, the current flowing through the I & k starts to increase linearly from zero, and gradually decreases VT3 current IVT3 .

Figure CN104578806AD00061

[0032] 式中:uH为变换器高压侧两端电压,为变换器低压侧两端电压,n为变压器变比。 [0032] wherein: uH is the voltage across the high voltage side of the converter, the voltage across the low voltage side of the converter, the transformer ratio n-is.

[0033] 模态2(ti〜t2) 4时刻,之间发生谐振,Crt放电,I&继续增大。 4 at time [0033] Mode 2 (ti~t2), resonance occurs between, Crt discharge, I & continues to increase. 直到七2时亥lj,放电为零,IVT3也下降为零。 2 until seven Hai lj, discharge is zero, IVT3 also drops to zero. I&达到最大值,并等于Li的电流Iu。 I & reaches a maximum, and Li equal current Iu.

Figure CN104578806AD00062

[0036] 模态3 (t2〜t3) :t2时刻,谐振结束,I经反并联二极管VDi、VD3和VD4导通续流, 此阶段电流保持恒定。 [0036] Mode 3 (t2~t3): t2 in time, the end of the resonator, the I by anti-parallel diode VDi, VD3 and VD4 turned freewheeling current remains constant at this stage. ¥1\因两端电压被钳位为零,故可实现ZVS开通;又VT3的电流IVT3已为零,所以VT3能实现ZCS关断。 ¥. 1 \ zero voltage is clamped by both ends, it can realize ZVS turn; IVT3 and VT3 has a current zero, VT3 off ZCS can be realized.

[0037] 模态4(t3〜t4) :t3时刻,I&因k的作用不能突变为零,但LJI乎分担了VT2* 部电压,所以在这一瞬间¥!\的ZVS开通对VT2有零电压钳位的作用,VT2能实现ZVS关断。 [0037] Mode 4 (t3~t4):! T3 time, I & k by the action of the mutation can not be zero, but almost LJI share the voltage VT2 * portion, so that the moment ¥ \ ZVS turn of zero to VT2 voltage clamp action, VT2 achieve ZVS turn-off. 此阶段,由Lr、CjPVD9形成谐振回路,C^开始充电。 At this stage, it is formed by the resonant circuit Lr, CjPVD9, C ^ begins charging. 经过四分之一的的谐振周期,即14时亥lj,L为零,充满电。 After a quarter of the resonant period, i.e. 14 is Hai lj, L is zero, full power.

Figure CN104578806AD00063

[0039] 模态5 (t4〜t5):之后(;2开始放电,并和Lr、VVVDi。构成谐振回路,I&从零开始反方向增大。t5时刻,放电为零,L经VT1、¥02导通续流,谐振结束,持续时间与134相等。 [0039] Mode 5 (t4~t5): After (; 2 begins to discharge, and and Lr, VVVDi constitute a resonance circuit, I & .t5 scratch time is increased in the reverse direction, the discharge is zero, L by VT1, ¥. freewheel 02 is turned, the end of the resonator, and the duration is equal to 134.

Figure CN104578806AD00071

[0041] 模态6 (t5〜16):此阶段只有个开关管是导通状态,辅助电路停止工作,低压侧电池向U充电。 [0041] Mode 6 (t5~16): This stage is only one switch is conductive state, the auxiliary circuit is inactive, the low-voltage side battery charge U.

[0042] 模态7(t6〜t7) :t6时刻,由于缓冲电的电压不能突变,VI\实现了ZVS关断。 [0042] Mode 7 (t6~t7): t6 time, the voltage buffer circuit can not change suddenly, Vl \ achieve ZVS turn-off. 且被充电,在升压电感1^的作用下,充电电流IUS本不变。 And is charged, under the action of the boost inductor ^ 1, this constant charging current IUS. 又因为VT4的两端电压被VDjf位为零,所以VT:在ZVS关断时VT4立即ZVS开通,为L:提供续流通路。 And because the voltage across VT4 is zero VDjf bits, VT: VT4 immediately upon ZVS ZVS turn off to L: provides the path.

[0043] 模态8(t7〜t8):此阶段为普通升压变换器的工作过程,即电池和升压电感U共同向高压侧提供能量。 [0043] Mode 8 (t7~t8): This stage is common during operation of the boost converter, i.e., the battery and the boost inductor to provide energy to the high pressure common U side.

[0044] 具体的降压变换原理如下所述。 [0044] Specifically the down conversion principle is as follows.

[0045] 当汽车在减速、刹车或空转时,控制器关闭低压侧开关管VI\〜VT4的驱动信号,继电器K断开,使饱和电感L2串入高压侧,辅助电路不工作,参见附图4。 [0045] When the vehicle is decelerating or braking idle, the controller closes the low-side switch driving signal VI \ ~VT4, the relay K are turned off, the saturable inductor L2. The high voltage side of the secondary circuit does not work, see FIG. 4. C5〜C8为开关管的输出结电容,开关管VT5〜VT8以移相模式工作,L2和C2能有效扩大负载范围并减少副边占空比丢失,输出经二极管VD#PVD4全波整流,滤波电感Li实现能量的回收利用和对低压侧蓄电池的充电。 C5~C8 output junction capacitance of the switch, the switch mode VT5~VT8 phase shift of work, L2 and C2 can effectively expand the range and reduce side load duty cycle loss, the output through diode VD # PVD4 full wave rectifier, filter inductor Li implement charge recycling and energy of the low-voltage side of the battery.

[0046] 为简化分析,假设如下:所有元件均为理想状态,且LWiVn2。 [0046] To simplify the analysis, it is assumed as follows: All components are ideal, and LWiVn2. 变换器降压变换时的工作波形参见附图5,up为变压器原边电压,Ip为变压器原边电流,为变压器副边电压,半个周期可分为6个模态,后半个周期的工作过程与前半个周期完全对称,故只介绍前半个周期。 Work buck converter waveform converting Referring to the drawings 5, up transformer primary voltage, the primary current Ip of the transformer as a secondary voltage of the transformer, a half cycle can be divided into six modes, in the latter half cycle the first half cycle working process completely symmetrical, so only the first half cycle described.

[0047] 模态1 (tQ〜tJ:令在tQ时刻之前,开关管VT5和VT8处于导通,I5线性上升,副边二极管VD3和VD4均导通,处于换流过程。t。时刻,换流结束,VD4关断,VT5和VT8继续导通,Ip开始对电容C2充电,其电压11。2呈线性变化。h时刻,关断VT5,IP达到最大值。此阶段有: [0047] Mode 1 (tQ~tJ: Order before time tQ, the switch is turned VT8 and VT5, I5 rises linearly secondary diode VD3 and VD4 are turned on, in the commutation process .t time change. end of stream, VD4 off, and VT5 VT8 continues to conduct, Ip starts charging the capacitor C2, the voltage changes linearly 11.2 .h time, off VT5, IP reaches its maximum at this stage are:

Figure CN104578806AD00072

[0050] 模态2匕〜12) :VT5关断后,并联电容C5、(:7与L2、Llk、Q发生谐振,C7开始放电, C5充电,15则从VT5转移到C5、C7中。 [0050] Mode 2 dagger ~12): VT5 turned off, shunt capacitance C5, (: 7 and L2, Llk, Q resonance occurs, C7 discharge starts, C5 charging, proceeds to VT5 15 from C5, C7 are.

Figure CN104578806AD00073

[0052] 由于U相对足够大,可近似认为Ip=I/n恒定不变,I。 [0052] Since the U phase is sufficiently large, it can be approximated that Ip = I / n constant, I. 为二次侧输出电流。 Output current of the secondary side. u。 u. 7在Ip的作用下线性下降, 7 role downline Ip decreases,

Figure CN104578806AD00074

[0054] 由式(10)可知up随着1!。 [0054] From formula (10) can be seen as an up !. 7不断下降而减小,直到t2时刻Uc;7=0,Ip开始经反并联二极管vd7导通续流。 7 declining and decreases until time t2, Uc; 7 = 0, Ip begins by conducting anti-parallel diode vd7 freewheeling.

Figure CN104578806AD00081

[0056] 模态3(t2〜t3) :t2时刻,由于VD7导通,开关管VT7的电压钳位为零,实现了ZVS开通。 [0056] Mode 3 (t2~t3): t2 time, since VD7 conducting, switch voltage clamping VT7 zero achieve ZVS turn.

[0057] 模态4(t3〜t4) :t3时刻,VT8在并联电容(:6、(:8的缓冲作用下ZVS关断。此后,原边电流15和副边电流I。均开始下降。当I。小于输出滤波电感电流Iu时,Iu中多余的电流向VD4流动。在换流过程中,整流二极管VD3和VD4同时导通,两侧电压都为零,变压器相当于短路,故一次侧的C6、(:8与Llk、L2发生谐振,C8充电,C6放电。 [0057] Mode 4 (t3~t4): t3 time, VT8 the shunt capacitance (: 6, (: ZVS turn-off buffer 8 under Thereafter, the primary current and the secondary current I. 15 were started to decline. I. when the output filter inductor current is less than Iu, Iu excess current flows to VD4. commutation process, the rectifying diodes VD3 and VD4 are simultaneously turned on, both voltages are zero, corresponding to a short-circuit transformer, the primary side so the C6, (: 8 and Llk, L2 resonance occurs, C8 charging, C6 discharge.

Figure CN104578806AD00082

[0059] 由式(12)可知Ip不断减小的同时,u。 [0059] by formula (12) can be seen simultaneously decreasing Ip, u. 8不断增大。 8 increasing. 直到14时亥I」,Ip= 0,则 Until 14:00 Hai I ", Ip = 0, then

Figure CN104578806AD00083

[0061] 模态5(t4〜t5) :t4时刻,二极管VD6导通续流。 [0061] Mode 5 (t4~t5): t4 time, conducting the freewheeling diode VD6. (:2的电压极性因与Ip相同而成为反向阻断电压源,L2退出饱和状态,阻碍15反向增大,使其维持在零状态。从而开关管VT6 实现ZCS开通。直到t5时刻,二极管VD6和VD7自然关断,15开始反向增大。 (: 2 due to the voltage polarity becomes the same as the Ip reverse blocking voltage source, L2 out of saturation, the reverse obstruction 15 increases, so that it is maintained in zero state switch VT6 achieve ZCS turn until time t5. , diode VD6 and VD7 off naturally, reverse 15 starts to increase.

[0062] 模态6(t5〜16) :t6时刻,I5达到反向最大值,二极管VD3中的电流下降到零而关断,电流Iu全部转移到VD4中,换流过程结束。 [0062] Mode 6 (t5~16): t6 time, I5 reaches maximum reverse diode current drops to zero VD3 is turned off, all current Iu transferred to VD4, the commutation process ends.

[0063] 为实现本发明的实施例,将通过以下的软开关条件分析和参数设计作进一步说明。 [0063] To achieve the embodiments of the present invention, the analysis and design parameters will be further illustrated by the following soft switching conditions.

[0064] 升压变换的软开关条件如下。 [0064] upconverting soft switching conditions are as follows.

[0065] 为了实现¥!\的ZVS开通,两端的电压不能上升过快,g卩t彡t,一般取(2〜 3) (t#为主开关管VTi的关断时间),需满足以下条件: [0065] In order to achieve ¥! \ ZVS is opened, the voltage across the not rise too fast, g t San Jie t, and generally (2~ 3) (t # main switch off time of the VTi), subject to the following condition:

Figure CN104578806AD00084

[0069] 为了不影响升压电路PWM的工作方式和辅助开关管软开关,必须对VT2的工作时间进行限制,即h〜t3时间段不宜过长,一般不超过10%的开关周期,故谐振电感需满足: [0069] In order not to affect the booster circuit and the PWM work soft switching auxiliary switch must be restricted to working hours VT2, i.e. h~t3 not too long period of time, generally not more than 10% of the switching period, so that the resonant inductance must meet:

Figure CN104578806AD00085

[0071] 式中:1~2为VT2的开关周期。 [0071] Formula: 1 2 VT2 switching period. 此外,VTi要实现ZVS关断,那13〜15时间段的谐振过程必须保证(;2放电为零,故谐振电容则需满足: Further, the VTi to achieve ZVS turn-off, and that 13~15 resonance process must ensure that the time period (; 2 discharge zero, so the resonant capacitor is required to satisfy:

Figure CN104578806AD00086

[0073] 降压变换的软开关条件如下。 [0073] The soft switching buck conversion conditions are as follows.

[0074] 为了实现超前桥臂开关管的ZVS,变压器的初级电压应在死区时间内下降为零。 [0074] In order to achieve ZVS switching tubes leading leg, the transformer primary voltage should drop to zero during the dead time. 所以开关管VTjPVT7的ZVS只需开关管导通与关断的时间间隔大于t' 12即可: Therefore, ZVS switching transistor VTjPVT7 simply turned on and switch off time interval is greater than t '12 to:

Figure CN104578806AD00091

[0076] 对于滞后桥臂开关管的ZCS,则要求存储在饱和电感1^2和阻断电容C2中的能量足够使变压器原边电流复位为零。 [0076] For lagging arm ZCS switch tube, 1 ^ 2 requires storage of energy and blocking capacitor C2 is sufficient to saturation in the transformer primary side inductor current is reset to zero. 所以: and so:

Figure CN104578806AD00092

[0080] 电路拓扑的参数设计如下。 Design Parameters [0080] The circuit topology is as follows.

[0081] (1)变压器的匝数及变比:降压变换时取高压侧电压纹波在10%以内,则变压器原边的绕组匝数Np: [0081] (1) and the transformer turns ratio: taking down the high side voltage ripple within 10% conversion, the number of turns of the transformer primary winding Np:

Figure CN104578806AD00093

[0084] 式中:Kf表示波形系数,一般取4. 44 (正弦波)或4 (方波);fs为移相全桥开关管的开关频率;Bm为最大磁感应密度;AJ%磁芯中心柱截面积;n表示变换效率,取〇. 9 ;S为导线电流密度系数,一般为2. 0A/mm2;Km为磁芯窗口的铜填充系数,取0. 5 ;K。 [0084] wherein: Kf represents a coefficient of a waveform, and generally 4.44 (sine wave) or 4 (square); FS phase-shifted full bridge switching frequency of the switch; Bm is the maximum flux density; AJ% core center sectional area of ​​the column; n-represents the conversion efficiency, take the square 9;. S is the conductor current density factor, generally 2. 0A / mm2; Km is the core window copper fill factor, taking 0. 5; K. 为铁芯填充系数,取1 ;PT为额定功率。 Fill factor for the core, take 1; PT is the rated power. 考虑到移相全桥变换器的占空比丢失问题,先假设副边最大占空比Dmax为0. 9,则副边要求输出的最小电压u_为: Taking into account the minimum voltage u_ duty cycle shift full-bridge converter relative loss problem, assume that the maximum duty ratio Dmax of the secondary side 0.9, the secondary side output is required:

Figure CN104578806AD00094

[0086] 式中:U_XS副边最大输出电压;vD为整流管正向压降;vu为滤波电感的直流压降。 [0086] wherein: U_XS secondary maximum output voltage; vD forward voltage drop is a rectifier; Vu is a DC voltage drop filter inductor. 变压器的匝比n为: The transformer turns ratio n:

Figure CN104578806AD00095

[0088] 式中:八&为变压器原边的开关管、饱和电感和隔直电容等总的压降。 [0088] wherein: & eight primary side of a transformer switch, blocking saturable inductor and capacitance of the total pressure drop. 故得出变压器副边的绕组匝数Ns=Np/n。 Therefore derived secondary transformer winding turns Ns = Np / n. 此外,变压器参数还必须符合升压变换,令升压电路完成一次升压的输入电压值为uin,输出电压值为u。 Furthermore, parameters must also conform to the boosting transformer transformation, so that complete a boosting circuit boosting the input voltage UIN is, the output voltage value of u. ,关系如下: The relationship is as follows:

Figure CN104578806AD00096

[0090] 式中:DT为推挽管的占空比。 [0090] wherein: DT is the duty cycle of the push-pull tubes. 令升压变换时电路的管压降、电容压降、绕组压降等为Av2,验证方法可认为是在uin最小时,得到所需的输出电压就能满足任一情况下的升压变比关系,由式(15)推知: Making the step of converting the circuit voltage drop, capacitance drop, the pressure drop as the winding Av2, the authentication method can be considered the most UIN hours, to obtain a desired output voltage can be boosted to meet in the case of any ratio relationship by the formula (15) inferred:

Figure CN104578806AD00097

[0092] (2)升压电感L1:升压电路中升压电感直接决定了输入电流的纹波AU的大小。 [0092] (2) boost inductor L1: booster circuit directly determine the size of the boost inductor AU input ripple current. 当升压输出功率最大,输入电压最小时,AL最大,Li的值也最大。 When the maximum, minimum input voltage, AL maximum value of the boost power output, Li is also the maximum.

Figure CN104578806AD00101

[0095] 式中:TS为主开关管VI\的开关周期。 [0095] where: TS-based switching cycle switch Vl \ a. 由于1^在降压时要作滤波电感,所以还需考虑降压时的电感数值。 Since during depressurization to 1 ^ for filter inductor, the need to consider the value of the inductance at the step-down. 降压时输出电路为全波整流电路,故副边电流脉动频率为原边开关管的2倍。 The output circuit is a buck full-wave rectifying circuit, so the secondary current ripple frequency is twice the primary side switch. 关系如下: Relationship is as follows:

Figure CN104578806AD00102

[0097] 所以结合式(18)、(19)综合考虑可得L1的值。 [0097] Therefore, binding of formula (18), (19) Considering the available value L1.

[0098] (3)滤波电容Q、Q:为了满足整流电压和高低频纹波的要求,一般取输出电压的交流纹波Av〇= 50mv。 [0098] (3) filter capacitor Q, Q: In order to meet the requirements of the rectified voltage and high frequency ripple, and generally Av〇 AC ripple output voltage = 50mv. 升压变换时,输出省去了滤波电感,仅通过(V滤除纹波。设电容电流为输出电流的20%,则有: When Boost conversion, eliminating the output filter inductor, only by (V filtering out the ripple current capacitor provided 20% of the output current, there are:

Figure CN104578806AD00103

[0102] (4)饱和电感L2:为了实现移相全桥的ZVZCS,L2的高频损耗和散热都会较大,所以。 [0102] (4) saturated inductance L2: To achieve the phase-shifted full bridge ZVZCS, L2 of the high-frequency loss and heat will be large,. 的伏秒积无需设计过高,这样占空比丢失就很小。 The volt-second product design without having too high, so the duty cycle of loss is very small. 求解公式如下: Solving formula is as follows:

Figure CN104578806AD00104

[0105] 式中:D、T分别为滞后桥臂开关管的占空比和开关周期,AT为滞后桥臂中两个开关管导通和关断的时间间隔。 [0105] wherein: D, T and the duty cycle of each switching cycle hysteresis switch bridge arm tube, AT two hysteresis switch is turned on and off time intervals bridge arm.

[0106] (5)隔直电容(:2:由于变换器的输出脉宽不一致、反馈回路不对称等不可能完全消除,所以偏磁现象必然存在,并且升压变换时推挽结构的偏磁更为严重。在此取升压变换时的电容值。 [0106] (5) blocking capacitor (: 2: due to inconsistencies in the output pulse of the inverter, the feedback loop can not completely eliminate the asymmetry, the bias magnet phenomena must exist, and when the push-pull configuration bias magnet upconverting more serious. when this capacitance value for step-up transformation.

Figure CN104578806AD00105

Claims (5)

1. 一种级联双向软开关DC/DC电路拓扑,包括前级升压电路、辅助电路、后级推挽变压器、全桥电路,它们之间依次串接,其特征是所述的辅助电路包括谐振电感L,谐振电容(; 2, 内含反并联体二极管VD2的辅助开关管VT 2,快恢复二极管VD9、VDltl,继电器K ;其中,谐振电感L的一端连于快恢复二极管VD 9的阴极,谐振电感k的另一端分别与谐振电容Crt的正极、辅助开关管VT 2的漏极相连,辅助开关管VT 2的源极与快恢复二极管VD 1(|的阳极相连,快恢复二极管VDltl的阴极连于继电器K的一端,继电器K的另一端分别与谐振电容Q 2的负极、快恢复二极管VD9的阳极相连。 A cascaded bidirectional soft switching DC / DC circuit topology, including the pre-stage booster circuit, auxiliary circuit, the push-pull transformer stage, a full bridge circuit, sequentially connected therebetween, characterized in that said auxiliary circuit includes a resonant inductor L, a resonance capacitor (; 2, containing the anti-parallel body diode of the auxiliary switch of the VT 2 VD2, fast recovery diodes VD9, VDltl, relay K; wherein, L is attached to one end of the resonant inductor fast recovery diode VD 9 of a cathode, the other end of the resonant inductor and k are positive resonant capacitor Crt, a drain VT auxiliary switch 2 is connected to the auxiliary switch VT source electrode 2 and the fast recovery diode VD 1 (| connected to the anode of the fast recovery diode VDltl a cathode connected to one end of the relay K, respectively, the other end of the relay K Q 2 and the negative electrode of the resonant capacitor, VD9 fast recovery diode is connected to the anode.
2. 根据权利要求1所述的级联双向软开关DC/DC电路拓扑,其特征是所述的前级升压电路包括低压侧直流电源%,滤波电容C1,升压电感L 1,内含反并联体二极管VD1的主开关管VT1,钳位电容Crt;其中,低压侧直流电源的正极与升压电感L 1的一端相连,升压电感1^的另一端连于主开关管VT i的漏极,主开关管VT i的源极与低压侧直流电源的负极相连,滤波电容C1正向并联于低压侧直流电源uy钳位电容Crt正向并联于主开关管VT ^勺漏源极,主开关管VT1的漏极作为前级升压电路的正极输出端,主开关管VT ^勺源极作为前级升压电路的负极输出端。 2. cascaded bidirectional soft switching DC / DC circuit topology according to claim 1, wherein said front-stage booster circuit includes a low-side DC power supply%, filter capacitor C1, the boost inductor L 1, containing the body of the anti-parallel diode VD1 main switch VT1, clamp capacitor Crt; wherein L is connected to one end of a low pressure side of the DC power supply 1, the positive electrode and the boost inductor, a boost inductor connected to the other end of ^ the main switch of the VT i the drain, source VT i of the main switch and the negative electrode of the DC power supply is connected to a low pressure side, forward filtering capacitor C1 connected in parallel with the low-pressure side of the DC power supply uy forward in parallel with the clamp capacitor Crt main switch VT ^ spoon drain and source, the drain pipe of the main switch VT1 as a positive electrode output terminal of the preceding stage of the booster circuit, a main switch VT ^ spoon source as the negative output terminal of the preceding stage booster circuit.
3. 根据权利要求1所述的级联双向软开关DC/DC电路拓扑,其特征是所述的辅助电路包括谐振电感L,谐振电容Crf,内含反并联体二极管VD 2的辅助开关管VT 2,快恢复二极管VD9、VDltl,继电器K ;其中,谐振电感Ij勺一端作为辅助电路的正极输入端,连于前级升压电路的正极输出端,谐振电感k的另一端分别与谐振电容C rf的正极、辅助开关管VT 2的漏极相连,辅助开关管VT2的源极作为辅助电路的负极输入端,分别与前级升压电路的负极输出端、快恢复二极管VD ltl的阳极相连,快恢复二极管VD 1Q的阴极连于继电器K的一端,继电器K的另一端分别与谐振电容(;2的负极、快恢复二极管VD 9的阳极相连,快恢复二极管VD 9的阴极连于前级升压电路的正极输出端,并作为辅助电路的正极输出端,快恢复二极管VDltl 的阳极作为辅助电路的负极输出端。 3. The soft switching cascaded bidirectional DC / DC circuit topology according to claim 1, wherein said auxiliary circuit includes a resonant inductor L, a resonance capacitor Crf, containing the anti-parallel body diode VD of the auxiliary switch VT 2 2, fast recovery diodes VD9, VDltl, relay K; wherein one end of the resonant inductor Ij spoon as a positive input terminal of auxiliary circuit, connected to the positive output terminal of the preceding stage booster circuit, the other end of the resonant inductor and resonant capacitor k are C rf positive electrode, the drain of the auxiliary switch VT 2 is connected to the auxiliary switch VT2 source electrode as a negative electrode input terminal of the auxiliary circuit, respectively, and a negative output terminal of the preceding stage booster circuit VD ltl fast recovery diode is connected to the anode, fast recovery diode VD 1Q cathode connected to one end of the relay K, and the other end of the relay K, respectively, and the resonant capacitor (; a negative electrode 2, the fast recovery diode VD is connected to the anode 9, the fast recovery diode VD cathode 9 is connected to the front stage liter positive output terminal voltage of the circuit, and as a positive electrode output terminal of the auxiliary circuit, the anode of diode VDltl fast recovery circuit as an auxiliary negative output terminal.
4. 根据权利要求1所述的级联双向软开关DC/DC电路拓扑,其特征是所述的后级推挽变压器包括内含反并联体二级管VD3的功率开关管VT 3,内含反并联体二级管乂仏的功率开关管VT4,原边三端口(两个同名端)、副边两端口(一个同名端)的变压器;其中,变压器原边中间的同名端作为后级推挽变压器的正极输入端,与辅助电路的正极输出端相连,功率开关管" 3的漏极连于变压器原边的另一同名端,功率开关管源极作为后级推挽变压器的负极输入端,分别与辅助电路的负极输出端、功率开关管VT 4的源极相连,功率开关管VT4的漏极连于变压器原边的非同名端,功率开关管VT 3、VT4组成一对推挽开关管,变压器副边的同名端作为后级推挽变压器的正极输出端,变压器副边的非同名端作为后级推挽变压器的负极输出端。 4. The soft switch cascaded bidirectional DC / DC circuit topology according to claim 1, wherein said push-pull transformer comprising a stage after diode VD3 antiparallel inclusion body power switch VT 3, containing qe Fo diode antiparallel VT4 body power switch, the primary three-port (two dotted terminal), two secondary ports (a dotted terminal) of the transformer; wherein, the dot end of the primary side of a transformer as an intermediate pushed-stage positive input pull transformer is connected to the positive output terminal of the auxiliary circuit, the power switch "drain 3 connected to the other end of the same name as the primary side of the transformer, the power switch as the source of the negative input terminal of the rear stage push-pull transformer , respectively, and a negative output terminal of the auxiliary circuit, the power source switch VT electrode 4 is connected to the drain of the power switch VT4 connected to the non-dot end of the primary side of the transformer, the power switch VT. 3, VT4 form a push-pull switch tube, the dot end of the secondary side of the transformer as a positive electrode output terminal of the rear stage push-pull transformer, the non-dot end of the secondary side of the transformer as the negative output terminal of the rear stage push-pull transformer.
5. 根据权利要求1所述的级联双向软开关DC/DC电路拓扑,其特征是所述的全桥电路包括饱和电感L2,继电器K,隔直电容C 2,内含反并联体二极管VD5、输出结电容(:5的功率开关管VT 5,内含反并联体二极管VD6、输出结电容C6的功率开关管VT 6,内含反并联体二极管VD7、输出结电容C7的功率开关管VT 7,内含反并联体二极管VD8、输出结电容C8的功率开关管VT 8,滤波电容Ctl,高压侧直流电源uH;其中,饱和电感L 2的一端作为全桥电路的正极输入端,与后级推挽变压器的正极输出端相连,饱和电感L2的另一端连于隔直电容(: 2的正极,继电器K并联于饱和电感L2,隔直电容C2的负极分别与功率开关管VT 5的源极、功率开关管VT7的漏极相连,功率开关管VT 5的漏极分别与功率开关管VT 6的漏极、滤波电容C ^的正极、 高压侧直流电源Uh的正极相连,功率开关管VT 7的源极分别与 The cascaded bidirectional soft switching DC / DC circuit topology according to claim 1, characterized in that the full bridge circuit comprises a saturable inductor L2, relay K, blocking capacitor C 2, containing the anti-parallel body diode VD5 , the output junction capacitance (: 5 5 power switch VT, containing anti-parallel body diode VD6, the output junction capacitance of the power switch VT C6. 6, containing the anti-parallel body diode VD7, capacitor C7 the output node of the power switch VT 7, containing anti-parallel body diode VD8, the output junction capacitance of the power switch C8 VT 8, Ctl filter capacitors, high voltage side of the DC power supply uH Tolerance; wherein, L 2 is an end saturable inductor as the positive input terminal of the full bridge circuit, and the positive output terminal of the transformer is connected to the push-pull stage, L2 saturable inductor and the other end connected to the blocking capacitor (: positive electrode 2, the relay in parallel with the K saturable inductor L2, DC blocking capacitor C2 and the negative electrode of the power source switch of the VT 5 the positive electrode, the high voltage side of the DC power supply Uh positive electrode, the drain tube VT7 power switch is connected to the drain of the power switch. 5 VT are a drain of the power switch VT, ^ smoothing capacitor C 6 is connected to the power switch VT the source electrode 7, respectively 率开关管VT 8的源极、滤波电容Q1的负极、高压侧直流电源u H的负极相连,功率开关管VT 8的漏极作为全桥电路的负极输入端,分别与后级推挽变压器的负极输出端、功率开关管VT6的源极相连,功率开关管VT 5、VT7组成全桥电路的超前桥臂,功率开关管VT 5、VT7组成全桥电路的滞后桥臂。 Source VT 8 of switch poles, a negative electrode of Q1 is connected to the filter capacitor, high-voltage side of the DC power supply negative u H, VT 8 drain of the power switch as a full bridge circuit negative input terminal, respectively, of the push-pull transformer stage the negative output terminal of the power switch VT6 source electrode connected to the power switch VT 5, VT7 composition lead leg full bridge circuit, the power switch VT 5, VT7 composition lagging leg full bridge circuit.
CN201410836076.8A 2014-12-29 2014-12-29 Soft switching cascaded bidirectional dc / dc circuit topology CN104578806B (en)

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