CN104115558B - 用于ac供电电子器件的辅助电源 - Google Patents
用于ac供电电子器件的辅助电源 Download PDFInfo
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- CN104115558B CN104115558B CN201380005991.6A CN201380005991A CN104115558B CN 104115558 B CN104115558 B CN 104115558B CN 201380005991 A CN201380005991 A CN 201380005991A CN 104115558 B CN104115558 B CN 104115558B
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Abstract
公开了一种用于将辅助电力提供给AC供电照明器件的技术。辅助电源可以用于例如将辅助电力提供给照明控制电路、LED驱动器或任何其它电子照明器件。在一些示例实施例中,线性调节器连接到受控于控制电路的开关,以使得仅当瞬时线路输入电压处于所述线性调节器具有稍微良好效率的特定范围中时,所述线性调节器操作。在这样的情况下,当线性调节器正在操作时,利用连接到线性调节器的输出的辅助电容器来存储能量。
Description
相关申请
本申请要求于2012年1月20日提交的美国临时申请No.61/588,838的优先权,通过对该申请整体进行引用而将其并入于此。
技术领域
本申请涉及照明驱动器电路,并且更具体地,涉及用于AC供电照明器件的辅助电源。
背景技术
将辅助电流源提供给照明驱动器电路可能牵涉:提供一个或更多个低电压DC电源。线性电压调节器可以提供这些辅助低电压DC提供电压。这样的辅助源牵涉大量不平凡的挑战。
附图说明
图1a示出用于包括将辅助电力提供给器件的其它电路的线性调节器的照明系统的电路设计。
图1b示出具有辅助电源的LED驱动器的另一电路设计。
图2图解根据本发明一个实施例的使用线性调节器直接馈离主AC电压线路的辅助电源的电路设计。
图3示出根据本发明一个实施例的图2的开关的随着时间的瞬时线路电压VLINE以及切换时段的曲线图。
图4a图解根据本发明一个实施例的用于控制线性调节器的开关的电路设计。
图4b示出根据本发明一个实施例的可以在用于线性调节器开关的控制件中使用的电路逻辑图。
图4c示出根据本发明一个实施例的图4a的晶体管的随着时间的瞬时线路电压VLINE以及切换时段的曲线图。
图5a图解根据本发明一个实施例的使用线性调节器直接馈送自主AC电压线路的辅助电源的电路设计。
图5b示出根据本发明一个实施例的在辅助电源的正常负载条件下的图5a的晶体管510的随着时间的瞬时线路电压VLINE以及辅助电压VAUX以及切换时段的曲线图。
图5c示出根据本发明一个实施例的在辅助电源的非常高的负载条件下的图5a的晶体管510的随着时间的瞬时线路电压VLINE以及辅助电压VAUX以及切换时段的曲线图。
图6图解根据本发明一个实施例的提供两个辅助电压的直接馈送自主AC电压线路的辅助电源的电路设计。
图7a-图7b图解根据本发明两个实施例的提供两个辅助电压的直接馈送自主AC电压线路的辅助电源的其它电路设计。
图8a图解根据本发明一个实施例的使用晶闸管直接馈送自主AC电压线路的辅助电源的电路设计。
图8b示出根据本发明一个实施例的在辅助电源的正常负载条件下的晶闸管的瞬时线路电压VLINE和切换时段的曲线图。
具体实施方式
公开了一种用于将辅助电力提供给AC供电照明器件的技术。辅助电源可以用于例如将辅助电力提供给照明控制电路、LED驱动器或任何另外电子照明器件。在一些示例实施例中,线性调节器连接到受控于控制电路的开关,从而仅当瞬时线路输入电压处于所述线性调节器具有稍微良好效率的特定范围中时,所述线性调节器操作。在这些情况下,当线性调节器正在操作时,以连接到线性调节器的输出的辅助电容器来存储能量。在一些实施例中,所述线性调节器被配置为:仅当所述线路电压处于所确定的上电压阈值与下电压阈值之间时才操作;而在其它情况下,所述线性调节器被配置为:仅当所述线路电压增加通过所述预定电压阈值值时才操作。在所述线路电压高于所述上阈值电压值的同时,如果所述辅助电容器放电,则仅当所述线路电压增加时才操作所述线性调节器避免了电流尖峰的可能性。除了提供具有稍微良好效率的辅助电力之外,还改进了照明器件关于切相调光的性能,这特别对于LED驱动器是非常期望的。
概述
如前期所述,在AC供电照明器件中提供辅助源牵涉大量不平凡的挑战。例如,即使线性调节器归因于其操作性质而将是理想组件,典型地用于提供这些辅助源的线性调节器中所耗散电力也可能产生明显的电力损耗。更详细地说,AC供电照明电路可能要求内部电力源来提供其自身的功能。这种内部电力源有时被称为辅助电源。照明电路可以包括例如LED驱动器、用于荧光照明系统的电子镇流器、白炽照明电路、用于控制另外照明电路或另外合适的照明电路的器件。现代驱动器同样可以并入附加能力(诸如通信、亮度和色彩控制)。此外,有时,现代LED驱动器将辅助电力提供给风扇,以用于冷却LED系统。即使风扇可能并非对于LED驱动器是“内部”的,辅助电源也可以提供用于这些风扇的电力。无论功能如何,为了对于整个照明电路实现高效率,高效率辅助电力源是期望的。图1a示出用于包括将辅助电力提供给LED驱动器的另外电路的线性调节器的LED照明系统的电路设计。如可见那样,在该特定示例中,电路的输入级包括AC源101,其将信号提供给电压整流器102,电压整流器102连接到电容器103。在该示例中,输入级将电压Vin提供给电流源110,电流源110提供通过LED串111的恒定电流ILED。在一些实施例中,电流源110可以是将电流提供给LED的开关模式转换器或线性调节器。在该示例中,输入级还连接到线性调节器,线性调节器表现为可变串联电阻,将期望的输出Vaux提供给其它电路,所述其它电路可以包括LED驱动器的控制电路(微控制器电路,电力级的控制件、与光管理系统/整体控制系统/建筑自动化系统的通信部件、其它普通电路等)。图1b示出用于基于非隔离恒定电流LED驱动器的LED照明系统的电路设计。如可见那样,AC源101将信号提供给电压整流器102和辅助电源,电压整流器102连接到电容器103。辅助电源是线性电压调节器,包括电容器104和109、齐纳二极管106、二极管107、电阻器105和晶体管108。晶体管108的输出将辅助电流Iaux和辅助电压Vaux提供给电流源110。该设计中的恒定电流源110仅要求单个辅助提供电压,并且提供通过LED串111的恒定电流。跨线性调节器的电压降乘以控制电路所下拉的辅助电流确定所耗散的电力,并且因此损耗在线性调节器中。尤其是在具有高输入电压的应用中(例如关闭(off)干线电力驱动器),所耗散的电力可能是大量的,并且可能减小LED驱动器的整体效率和/或热性能。如果图1b所示的电路的输入电容器103大,则电容器上的纹波电压将是小的。在此情况下,电容器电压Vin将接近峰值线路电压(例如,对于120Vac线路,标称地为170V)。假设辅助电源必须提供等于大约5V的辅助电压Vaux以及等于大约20mA的辅助电流Iaux,则理想线性调节器中的所耗散的电力将是(Vin – Vaux)*Iaux = (170V-5V)*20mA=3.3W。考虑到所提供的辅助电力仅为5V*20mA=0.1W,这是显著的电力损耗。在另一驱动器设计中,图1b所示的电路的输入电容器103小,从而整流器102的电压输出Vin以正弦形状在0V与170V之间变化。因此,辅助电源中的平均电力损耗并不如在更大电容器的情况下那样大,但仍然很显著,而现在电容器109必须具有足够高的电容,以在线路输入电压低于辅助电压(二极管107正在阻断)的同时提供辅助电流。为了缓解线性调节器的缺点,可以使用基于(单机)开关模式电力转换器的辅助电源。然而,由于开关模式电源通常比线性调节器更复杂,因此它们可能要求附加的设计努力、印制电路板上的更多空间,并且同时,它们可能将复杂度、潜在EMI问题以及附加成本加入到产品。
因此,并且根据本发明实施例,公开了用于通过利用线性调节器并且基于瞬时线路电压来配置线性调节器的被激活的间隔而更高效地将辅助电力提供给AC供电照明器件的电子器件的技术。在这样的示例中,当线性调节器将另外在显著高于其输出电压的输入电压操作时,线性调节器的选通避免了高电力损耗。在高输入电压的这些时间跨段期间,在低线路电压的时间时高效地充电的存储电容器提供辅助电力。在这样的示例中,电力直接取自线路,并且具有器件无须一定是LED驱动器的优点。这样的提供辅助电力的技术对于“AC LED”驱动器尤其有用。这样的驱动器并非基于开关模式概念,诸如在阻性(例如图1a和图1b所示的电路或“随机ZES”电路)或容性/感性电流限制的情况下被从干线断开驱动(driven off)的LED。在基于开关模式提供的LED驱动器中,通常可以通过在磁性组件上加入附加绕组来生成辅助电压。这在“AC LED”驱动器的情况下是不可能的,因为没有这样的磁性组件。
电路架构
图2图解根据本发明一个实施例的使用线性调节器直接馈离主AC电压线路的辅助电源的电路设计。如可见那样,该特定示例实施例包括AC电压源201和整流器202,整流器202将线路电压VLINE提供给第一线性调节器203。线路电压还被发送到控制件204,控制件204控制开关205,并且还连接到第一辅助电压VAUX1。第一线性调节器203的输出通过开关205连接到提供第一辅助电流IAUX1的节点、第一线性调节器所馈送的存储电容器206以及第二线性调节器207。第二线性调节器的输出连接到电容器208,并且提供第二辅助电流IAUX2和第二辅助电压VAUX2。在一个示例实施例中,控制件204控制开关,从而第一线性调节器仅在辅助电压VAUX1(VAUX1必须通过该电路被提供)的标称值接近瞬时线路电压VLINE时的时间期间被激活,以避免线性调节器中的大的电力损耗。在一个实施例中,当第一辅助电压上的电压纹波不可忍受时,第二线性调节器用作后调节器。在其它实施例中,可以省略第二线性调节器和电容器208。假设电容器206足够大并且IAUX1和IAUX2充分小,那么仅从VLINE到控制件的输入是有关的。从VAUX1到控制件204的输入将仅用于检测接近临界下阈值VTH1的VAUXI并且触发以接通开关,并且当VAUX1接近临界上阈值VTH2时关断开关。在另一示例实施例中,控制件204控制开关,从而第一线性调节器仅在辅助电压VAUX1是严重低(低于阈值电压VLow)或在辅助电压VAUX1标称值接近瞬时线路电压VLINE时的时间期间被激活。该特定实施例带有这样的优点:在高瞬时线路电压下(不可预见的)大电力要求的情况下,确保辅助电压不崩溃。确保辅助电压将停留在阈值电压VLow处或在其之上。因此,即使从效率观点来说这并不是重新对电容器206充电的好时间,从辅助电源供电的电路也继续工作。
对于理想组件而言,不存在用于电容器206的容量的最大允许容量Cmax。同样的情况对于最小允许容量Cmin成立。因为在一些应用中可能期望保持电容器206相对小,所以显著的电压纹波可能出现在辅助电压VAUX1上。在严格的电压纹波要求(例如,因为辅助电压用作用于模数转换器的基准电压)的情况下,可以通过将该第一辅助电压提供级与第二级进行级联来克服该问题。
图3示出根据本发明一个实施例的图2的开关205的随着时间的瞬时线路电压VLINE以及切换时段的曲线图。一旦图2的电路从120V/60Hz AC干线断开而被操作,线路峰值电压Vpk接近170V,并且T等于1/120Hz。在该曲线图中,瞬时线路电压被示出为当在间隔301期间增加时并且当在间隔302期间值减小时通过阈值电压VTH1和VTH2。在间隔303期间,线路电压高于上阈值电压值,而在间隔304期间,线路电压低于下阈值电压值。该曲线图将线路电压的峰值和下落示出两次。在一个示例实施例中,开关的切换时段可以被配置为使得:当线路电压在两个阈值电压VTH1与VTH2之间时(即在间隔301和302期间),闭合开关205。在这样的实施例中,线性调节器仅在高效率的时段期间操作。在线性调节器正在操作的间隔期间,流过线性调节器的显著电流出现,在AC供电照明器件的输入处看到该电流。在这样的实施例中,在低瞬时线路电压下从干线抽取的附加电流改进了照明器件关于切相调光的性能。当在馈送AC供电照明器件的AC线路中引入切相调光器时,比如闪烁光的问题通常是明显的;特别是,在低调光水平(低光水平)下,抽取不足的电流以保持通常基于TRIAC的调光器“活跃”。因此,所描述的辅助电源所抽取的附加电流改进切相调光性。
图4a图解根据本发明一个实施例的用于控制线性调节器的开关的电路设计。在该特定示例中,在虚线框内部示出单片集成电路内部的电路(被称为“控制IC”)。该电路包括电阻器401和405,用于缩放IC内部的VLINE的值。连同充当电压分压器并且其值确定(都在IC内部缩放的)下阈值电压VTH1和上阈值电压VTH2的电阻器402、403和404一起,还提供基准电压VREF。线路电压连接到比较器406和407,并且还连接到电阻器405。比较器的输出发送到AND门408,在该特定示例中,AND门的输出经由电阻器409发送到晶体管410。晶体管410经由电阻器411连接到大地,并且经由齐纳二极管412连接到晶体管413。在该示例实施例中,晶体管413的输出提供辅助电压VAUX,并且连接到电容器414和电阻器415。在该示例实施例中,电阻器415表示连接到辅助电源的负载。晶体管413的发射极连接到可选二极管416,在该特定实施例中,其保护413不受潜在过高的反向电压。二极管416连接到线路电压VLINE。在一个这样的实施例中,电阻器409和411连同晶体管410的电流增益β一起限制在启动时通过晶体管413的涌入电流(如果电容器414为空并且完全地放电),并且还限制在间隔302的开始时的电流尖峰。
在一些实施例中,如果辅助电容器(例如电容器206或414)在间隔303期间显著地放电,则在间隔302的开始时存在电流尖峰的可能性。因为这些电流尖峰,所以与当线路电压在间隔301中增加时相比,电路可能在间隔302期间更低效。因此,根据本发明一个实施例,线性调节器可以被控制,从而其仅在当线路电压在下阈值电压与上阈值电压之间增加时的间隔301期间操作(开关205仅闭合)。这样的示例避免在间隔302的开始时的高损耗。图4b示出根据本发明一个实施例的可以在用于线性调节器开关的控制件中使用的电路逻辑图。可以利用与如图4a所示的相似的电路来实现这样的实施例,其中仅AND门408由图4b所示的逻辑电路替代。更具体地说,比较器406和407的输出可以发送到AND门421的两个输入。比较器407的输出可以发送到S–R锁存420,其也由AND门421的输出馈送。S-R锁存420的输出发送到AND门421的第三输入,如所示的那样。
图4c示出当如上所述应用图4b的逻辑电路时图4a的晶体管413的随着时间的瞬时线路电压VLINE和切换时段的曲线图。如可见那样,开关仅在当瞬时线路电压在上阈值电压值与下阈值电压值之间的值中增加时的间隔430期间闭合。
图5a图解根据本发明一个实施例的使用线性调节器直接馈送自主AC电压线路的辅助电源的电路设计。如可见那样,该特定示例实施例包括AC电压源501和整流器502,整流器502将线路电压VLINE提供给电阻器503,电阻器503然后连接到第一线性调节器507。电阻器503还连接到具有电阻器504和505的电压分压器,并且在这些电阻器之间是缩减的线路电压VLINE1。该电压被缩减,以用于输入到稍后讨论的控制电路中。如参照图5a进一步可见那样,第一线性调节器507连接到电容器506、电阻器509和电阻器508。线性调节器507的输出连接到晶体管510,其在一个特定实施例中是P沟道耗尽模式MOSFET(其为正常导通的器件)。晶体管510连接到齐纳二极管512,并且还通过电阻器511连接到晶体管520。晶体管510的输出提供辅助电压VAUX,并且该辅助电压存储在辅助电容器515中。该电压也由包括电阻器513和514的电压分压器缩减到VAUX1。VAUX还发送到第二线性调节器516的输入,第二线性调节器516连接到电容器517,如图5a所示。线性调节器516的输出提供电压VAUX2,其由包括电阻器518和519的电压分压器缩减到基准电压VREF。
在该特定示例中,用于辅助电力源的控制电路如在图5a的下部的框中所示被配置,并且包括具有迟滞的两个比较器522和527。电阻器521和526调整迟滞量。晶体管520通过电阻器523连接到比较器522,并且通过二极管524连接到比较器527。比较器522的反相输入通过电阻器525连接到比较器527的反相输入,并且527的反相输入通过电阻器528连接到大地。比较器527的反相输入还通过电阻器526连接到其输出。比较器522的非反相输入连接到缩减的线路电压VLINE1以及电阻器521。由电压VAUX2提供比较器522的正电源。比较器522的反相输入连接到基准电压VREF。比较器527的非反相输入连接到缩减的辅助电压VAUX1。在此应注意,晶体管510充当被控制的开关,并且该被控制的开关放置于线性调节器之后。开关的这种放置与其中开关放置在线性调节器之前(例如,如图2所示)的更早描述的本发明一些其它实施例是不同的。然而,使得线性调节器在时间上仅在特定时段操作的原理仍然保持有效。在此情况下,“操作”意味着在线性调节器实际上能够将电力提供给VAUX节点的意义上(即使可以一直以电力对507的输入提供电力,507也置于空闲,仅提供由确定实际输出电压的电阻器508和509所消耗的非常少的输出电力,如对于LM317式线性调节器已知的那样。“智能”线性调节器507可以甚至检测除了定义电阻器分压器的输出电压之外没有所抽取的电力,并且将自身置于甚至休眠模式中)。
如更早所述那样,该特定实施例的晶体管510是正常到通的器件,并且因此除了控制电路通过接通晶体管520来主动关断510之外,线性调节器507进行操作。所示的控制电路被配置为:当线路电压高于上阈值但仅如果同时辅助电压VAUX不是严重低(低于阈值电压VLow)时,关断510。由于上面先前讨论的原因,比较器522可以用于监控线路电压并且去激活开关510,而比较器527负责监控辅助电压。归因于二极管524,无论比较器522的输出状态如何,比较器527都能够将520的栅极拉低(因此接通510)。该实施例带有这样的优点:在高瞬时线路电压下(不可预见的)大电力要求的情况下,确保辅助电压不崩溃。确保辅助电压将停留在阈值电压VLow处或在其之上。因此,即使从效率观点来说这可能不是重新对电容器充电的好时间,从辅助电源供电的电路也继续工作。
图5b和图5c示出根据本发明一个实施例的随着时间的晶体管510的瞬时线路电压VLINE以及辅助电压VAUX和切换时段的曲线图。在该特定实施例中,电阻器521被选取为十分高的值,导致几乎没有关于比较器522的动作的迟滞,并且为了简化解释,如果线路电压VLINE跨阈值电压VTH2,则比较器522可以被看作总是切换。通过选取特定基准电压VREF在电路设计期间定义阈值电压VTH2。图5b示出在辅助电源的正常负载条件下的电路操作,意味着VAUX绝不是严重低,因此,仅比较器522在线路周期的过程上改变其输出状态。在间隔550期间,晶体管510导通,这与线路电压小于阈值电压VTH2一致。从图5b可见,在一个间隔550内,存在两个间隔,其中,辅助电压增加,并且因此,线性调节器507对电容器515充电。电容器515的充电导致在AC供电照明器件的输入处看到的流过线性调节器的显著电流。在低瞬时线路电压下时取自干线的这种附加电流改进照明器件关于切相调光的性能。当在馈送AC供电照明器件的AC线路中引入切相调光器时,通常比如闪烁光的问题是明显的;特别是,在低调光水平(低光水平),抽取不足的电流以保持通常基于TRIAC的调光器活跃。因此,所描述的辅助电源所抽取的附加电流改进切相调光性。
图5c示出根据本发明一个实施例的在辅助电源的十分高的负载条件下的电路操作的示例。与图5b对照,出现附加间隔552,在附加间隔552中晶体管510导通。如果辅助电压VAUX落在临界阈值电压VLowL之下,则出现间隔552,这导致比较器527的输出变为低,因此接通晶体管510。这导致VAUX的上升,并且当VAUX达到VLowU时,比较器527改变为高,并且因此,间隔552完成。电阻器526所设置的比较器的迟滞定义VLowL和VLowU之间的电压摆动,而以电阻器525和528制成的电压分压器定义(VLowL+VLowU)/2。在该特定示例中,在两个相邻间隔550之间引入单个间隔552,然而,取决于辅助电源的负载,取决于辅助电源的负载,可以存在更多(在两个相邻间隔550之间的若干个间隔552)或更少(例如仅每若干间隔550的单个间隔552)间隔552。
图6图解根据本发明一个实施例的使用线性调节器直接馈送自AC电压线路(未示出的整流器)的辅助电源的另一电路设计。在该特定示例中,线路电压连接到电阻器601,电阻器601与齐纳二极管603和604串联连接。齐纳二极管604与电阻器605并联连接,并且其目的在于保护MOSFET的栅极不受高电压。线路电压还经由二极管607连接到第一线性调节器608,二极管607可以保护线性调节器不受反向电压。第一线性调节器连接到电阻器609以及充当电压分压器的电阻器610和611。晶体管606连接到两个齐纳二极管之间的节点,并且还连接到电阻器610与611之间的节点。第一线性调节器的输出提供第一辅助电压VAUX1。辅助电容器612连接到第一辅助电压和大地。如上面解释那样,第一辅助电压可能具有大量纹波,并且在一些实施例中,可以连同电容器614和615一起包括第二调节器613,以提供更稳定的第二辅助电压VAUX2。在一个示例实施例中,晶体管充当被控制的开关。其切换动作基于线路电压VLINE,并且这种切换动作与图5b所示的晶体管510的切换动作相似。与上更早描述的实施例不同,该实施例中的开关既不连接到线性调节器的输入也不连接到输出,但是却连接到基准端子,基准端子有时被称为接地端子。如果线路电压达到与达到MOSFET 510的栅极接通阈值一致的特定阈值水平,则晶体管510接通,并且由此减少LM317式线性调节器608的从例如VTH2到VLow的输出设置电压。因此,线性调节器不将任何电流提供给其输出,除非辅助电压落入(严重低的)电压阈值VLow,在该电压阈值,线性调节器在其输出处仅提供足够的电流,从而辅助电压将保持在VLow。并非取决于其栅极接通阈值电压以及其器件特定切换特性,该电路的一个实施例(未示出)并入有在其输入处连接到基准电压和线路电压的比较器,而其输出连接到晶体管606的栅极。
图7a图解根据本发明一个实施例的使用线性调节器直接馈离主AC电压线路的辅助电源的另一电路设计。在该特定示例中,线路电压连接到电阻器701和702,电阻器701和702与齐纳二极管703和704串联连接。在各二极管之间连接晶体管706,并且齐纳二极管704与电阻器705并联连接。线路电压还通过电阻器708和二极管720连接到晶体管709。电阻器708限制峰值电流,并且带走来自晶体管709的一些电力耗散。二极管720防止电流反向流过晶体管709,特别是,通过N沟道增强模式MOSFET晶体管709的固有体二极管。电阻器701和702充当电压分压器,并且在它们之间连接电阻器707,电阻器707还连接到晶体管709和齐纳二极管710。齐纳二极管710连接到齐纳二极管711和晶体管706。晶体管709的输出提供第一辅助电压VAUX1,并且VAUX1对辅助电容器712充电。第二线性调节器713连同可选电容器714和第二辅助电容器715一起可以连接到VAUX1,并且该附加电路可以提供具有更少电压纹波的第二辅助电压VAUX2。除了由具有其连接到近似恒定电压(由齐纳二极管710和711提供)的栅极的简单MOSFET(晶体管709)提供线性调节器的功能之外,图7a所图解的电路设计在功能上与如图6所图解的电路设计相似地进行提供。取决于执行与图6中的晶体管606相同的任务的晶体管706的切换状态,晶体管709的栅极电压改变。齐纳二极管710的齐纳电压确定VLow,而齐纳二极管710和711的齐纳电压之和确定VTH2。
图7b图解根据本发明一个实施例的使用线性调节器直接馈离主AC电压线路的辅助电源的另一电路设计。在该特定示例中,线路电压连接到电阻器701和702,电阻器701和702与齐纳二极管703和704串联连接。在一个实施例中,连接到大地的可选电容器(未示出)可以放置于电阻器701与702之间,创建具有电阻器701的低通滤波器并且抑制来自线路的噪声。在各二极管之间连接晶体管706,并且齐纳二极管704与电阻器705并联连接。线路电压还通过电阻器708和二极管720连接到晶体管709。电阻器708限制峰值电流,并且带走来自晶体管709的一些电力耗散。二极管720防止电流反向流过晶体管709,特别是,通过N沟道增强模式MOSFET晶体管709的固有体二极管。电阻器701和702充当电压分压器,并且在它们之间连接电阻器707,电阻器707还连接到晶体管709和TL431式或TS432式分流(shunt)电压基准719。晶体管706与电阻器716并联连接,并且还与电压分压器:电阻器717和718连接。在电阻器717与718之间是用于分流电压基准719的基准输入。晶体管709的输出提供第一辅助电压VAUX1,并且还与由VAUX1充电的第一辅助电容器712以及晶体管706连接。如参照图7a描述的那样,第二线性调节器713连同可选电容器714和第二辅助电容器715一起可以连接到VAUX1,并且该附加电路可以提供具有更少电压纹波的第二辅助电压VAUX2。图7b所图解的电路设计在功能上与图7a所图解的电路设计相似地进行提供,但具有改进的性能,包括改进的温度稳定性以及改进的关于组件耐受性的性能。
图8a图解根据本发明一个实施例的使用线性调节器直接馈离主AC电压线路的辅助电源的又一电路设计。该特定实施例仅图解单个辅助电压提供,而没有第二调节器来提供第二辅助电压。线路电压通过二极管801连接到电阻器804,电阻器804连接到晶体管805。线路电压还连接到电阻器803。电阻器803的输出提供基准电压VREF,并且连接到齐纳二极管808,齐纳二极管808连接到大地。电阻器803还连接到晶体管805以及晶体管806和807所形成的晶闸管的阳极。晶闸管的栅极连接到齐纳二极管812和电阻器810,电阻器810与电容器811并联连接。晶闸管的阴极连接到电阻器810和电容器811,其连接到齐纳二极管809。晶体管805的源极连接到齐纳二极管812的输出,并且提供第一辅助电压VAUX1,其对辅助电容器813充电。在一个实施例中,选取齐纳二极管812,从而只要看到VZ,812跨二极管812,晶闸管就触发。当VAUX1达到期望的上阈值电压VTH2并且让其关闭直到下一间隔301(见图3和图8b)发生时,这样的示例实施例在标称负载条件下关断线性调节器,由此避免更低效的间隔302(见图3)。图8b示出随着时间的晶闸管的瞬时线路电压VLINE和切换时段的曲线图。在该示例中,当VAUX1达到其期望的上电压阈值时,通过关断被点火(fire)的晶闸管或晶闸管布置而通过线路电压自身来完成“重置”。甚至在辅助电源的重负载下,也确保辅助电压VAUX在间隔301期间将保持高于或至少处于VLow。由齐纳二极管809确定电压VLow。
大量实施例将是显而易见的,并且可以通过任何数量的配置来组合在此所描述的特征。本发明的一个示例实施例提供一种辅助电源电路。所述辅助电源电路包括:线性调节器,其从AC电压源接收线路电压。所述提供电路还包括:开关,连接到所述线性调节器的输出,并且所述线性调节器被设计为仅当开关闭合时才操作。所述提供电路还包括:控制电路,其基于所述线路电压的瞬时值来闭合所述开关。在一些情况下,当所述线性调节器正在操作时,所述线性调节器的输出提供辅助电压。在一种这样的情况下,辅助电容器连接到所述线性调节器的输出。在一些情况下,所述控制电路被配置为:当所述辅助电压落在临界值之下时,激活所述开关。在一些情况下,所述控制电路被配置为:当所述瞬时线路电压增加到下阈值电压值时,闭合所述开关,并且当所述瞬时线路电压增加到上阈值电压值时,打开所述开关。在一种这样的情况下,基于所述线性调节器的操作效率来确定所述下阈值电压值和上阈值电压值。在另一种这样的情况下,所述控制电路被配置为:当所述瞬时线路电压减小到所述上阈值电压值时,再次闭合所述开关,并且当所述瞬时线路电压减小到所述下阈值电压值时,打开所述开关。在一些情况下,所述提供电路还包括:第二线性调节器,连接到所述辅助电压。在一些情况下,所述控制电路包括:晶闸管,被配置为:当所述瞬时线路电压达到阈值电压时接通,由此减少所述线性调节器的输出电压的设置值。
本发明的另一实施例提供一种创建辅助电力的方法。所述方法包括:将AC电压提供给线性调节器;监控所述AC电压的瞬时线路电压;以及基于所述瞬时线路电压来操作所述线性调节器。在一些情况下,操作所述线性调节器包括:在所述线性调节器的输出处提供辅助电压。在一种这样的情况下,所述方法还包括:利用所述辅助电压对辅助电容器充电。在另一种这样的情况下,所述方法还包括:将所述辅助电压输入到第二线性调节器中,由此在所述第二线性调节器的输出处提供第二辅助电压。在一些情况下,操作所述线性调节器包括:仅当所述瞬时线路电压在预定阈值电压值之内时才操作所述线性调节器。在一种这样的情况下,所述预定阈值值基于所述线性调节器的操作效率。在一些情况下,操作所述线性调节器包括:仅当所述瞬时线路电压在预定阈值电压值之内的值中增加时才操作所述线性调节器。在一种这样的情况下,操作所述线性调节器包括:当所述瞬时线路电压达到下阈值电压值时,接通晶闸管,并且当所述瞬时线路电压达到上阈值电压值时,关断所述晶闸管。
本发明另一实施例提供一种辅助电力系统。所述系统包括:线性调节器,被配置为:接收AC线路电压,并且当在操作中时在其输出处提供辅助电压。所述系统还包括:开关,被配置为:启用所述线性调节器,以使得仅当所述开关闭合时,所述线性调节器才操作。所述系统还包括:控制电路,被配置为:监控所述瞬时线路电压,并且基于所述瞬时线路电压的值来闭合所述开关。在一些情况下,所述控制电路被配置为:仅当所述瞬时线路电压在预定阈值电压值之内时才闭合所述开关。在一种这样的情况下,所述预定阈值电压值基于所述线性调节器的操作效率。在一种这样的情况下,所述控制电路被配置为:仅当所述瞬时线路电压在预定阈值电压值之内的值中增加时才闭合所述开关。
已经为了图解和描述的目的而提出本发明实施例的上述描述。并不意图穷举或将本发明限制于所公开的精确形式。根据本公开,很多修改和变化是可能的。意图不由该详细的描述而是由所附的权利要求来限制本发明的范围。
Claims (21)
1.一种辅助电源电路,包括:
线性调节器,被配置为:从AC电压源接收线路电压;
开关,连接到所述线性调节器,其中,所述线性调节器仅当所述开关被激活时才操作;以及
控制电路,被配置为:基于所述线路电压的瞬时值来闭合所述开关。
2.如权利要求1所述的电路,其中,当在操作中时,所述线性调节器的输出提供辅助电压。
3.如权利要求2所述的电路,还包括:辅助电容器,连接到所述线性调节器的输出。
4.如权利要求2所述的电路,其中,所述控制电路被配置为:当所述辅助电压落在临界值之下时,激活所述开关。
5.如权利要求1所述的电路,其中,所述控制电路被配置为:当瞬时线路电压增加到下阈值电压值时,激活所述开关,并且当瞬时线路电压增加到上阈值电压值时,去激活所述开关。
6.如权利要求5所述的电路,其中,基于所述线性调节器的操作效率来确定所述下阈值电压值和所述上阈值电压值。
7.如权利要求5所述的电路,其中,所述控制电路进一步被配置为:当所述瞬时线路电压减小到所述上阈值电压值时,闭合所述开关,并且当所述瞬时线路电压减小到所述下阈值电压值时,打开所述开关。
8.如权利要求2所述的电路,还包括:第二线性调节器,连接到所述辅助电压。
9.如权利要求1所述的电路,其中,所述控制电路包括:晶闸管,被配置为:当所述瞬时线路电压达到阈值电压时接通,由此减少所述线性调节器的输出电压的设置值。
10.一种创建辅助电力的方法,包括:
将AC电压提供给线性调节器;
监控所述AC电压的瞬时线路电压;以及
基于所述瞬时线路电压来操作所述线性调节器。
11.如权利要求10所述的方法,其中,操作所述线性调节器包括:在所述线性调节器的输出处提供辅助电压。
12.如权利要求11所述的方法,还包括:利用所述辅助电压对辅助电容器充电。
13.如权利要求11所述的方法,还包括:将所述辅助电压输入到第二线性调节器中,由此在所述第二线性调节器的输出处提供第二辅助电压。
14.如权利要求10所述的方法,其中,操作所述线性调节器包括:仅当所述瞬时线路电压处于预定阈值电压值内时才操作所述线性调节器。
15.如权利要求14所述的方法,其中,所述预定阈值值基于所述线性调节器的操作效率。
16.如权利要求10所述的方法,其中,操作所述线性调节器包括:仅当所述瞬时线路电压在预定阈值电压值内的值中增加时才操作所述线性调节器。
17.如权利要求16所述的方法,其中,操作所述线性调节器包括:当所述瞬时线路电压达到下阈值电压值时,接通晶闸管,并且当所述瞬时线路电压达到上阈值电压值时,关断所述晶闸管。
18.一种辅助电力系统,包括:
线性调节器,被配置为:接收AC线路电压,并且当在操作中时,在其输出处提供辅助电压;
开关,被配置为:启用所述线性调节器,以使得仅当所述开关闭合时,所述线性调节器才操作;以及
控制电路,被配置为:监控瞬时线路电压,并且基于所述瞬时线路电压的值来闭合所述开关。
19.如权利要求18所述的系统,其中,所述控制电路被配置为:仅当所述瞬时线路电压处于预定阈值电压值内时才闭合所述开关。
20.如权利要求19所述的系统,其中,所述预定阈值电压值基于所述线性调节器的操作效率。
21.如权利要求20所述的系统,其中,所述控制电路被配置为:仅当所述瞬时线路电压在所述预定阈值电压值内的值中增加时才闭合所述开关。
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US201261588838P | 2012-01-20 | 2012-01-20 | |
US61/588,838 | 2012-01-20 | ||
US61/588838 | 2012-01-20 | ||
PCT/US2013/022414 WO2013110038A1 (en) | 2012-01-20 | 2013-01-21 | Auxiliary power supply for ac powered electronics |
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CN104115558A CN104115558A (zh) | 2014-10-22 |
CN104115558B true CN104115558B (zh) | 2016-09-21 |
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US (1) | US9564828B2 (zh) |
EP (1) | EP2805576A1 (zh) |
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CN106797106A (zh) * | 2014-10-15 | 2017-05-31 | 株式会社藤仓 | 光发送器、有源光缆、以及光发送方法 |
JP6415265B2 (ja) * | 2014-11-19 | 2018-10-31 | キヤノン株式会社 | 保護回路 |
CN110226362B (zh) * | 2017-01-26 | 2022-04-15 | 昕诺飞控股有限公司 | 被布置为经由无线控制器来控制的照明设备 |
US10516327B2 (en) * | 2017-07-19 | 2019-12-24 | Semiconductor Components Industries, Llc | System and method for controlling switching device in power converter |
US10292226B1 (en) | 2018-04-06 | 2019-05-14 | Dialog Semiconductor Inc. | Reducing jitter in a direct AC LED lighting device |
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TW201119489A (en) * | 2009-11-24 | 2011-06-01 | Darfon Electronics Corp | LED lighting system and power supply system thereof |
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US3323034A (en) * | 1963-06-05 | 1967-05-30 | Lambda Electronics Corp | Switching techniques in regulated d. c. power supplies |
DE3304759A1 (de) * | 1983-02-11 | 1984-08-16 | Siemens AG, 1000 Berlin und 8000 München | Verfahren und schaltungsanordnung zur transformatorlosen erzeugung kleiner gleichspannungen und deren verwendung |
KR100544189B1 (ko) | 2003-06-27 | 2006-01-23 | 삼성전자주식회사 | 고효율 전원 공급 장치 |
US8040070B2 (en) * | 2008-01-23 | 2011-10-18 | Cree, Inc. | Frequency converted dimming signal generation |
US8008898B2 (en) * | 2008-01-30 | 2011-08-30 | Cirrus Logic, Inc. | Switching regulator with boosted auxiliary winding supply |
GB2458699A (en) | 2008-03-28 | 2009-09-30 | Deepstream Technologies Ltd | Linear regulator with zero crossing coordination |
US8212493B2 (en) * | 2009-06-30 | 2012-07-03 | Cirrus Logic, Inc. | Low energy transfer mode for auxiliary power supply operation in a cascaded switching power converter |
US8638578B2 (en) * | 2009-08-14 | 2014-01-28 | Power System Technologies, Ltd. | Power converter including a charge pump employable in a power adapter |
US8466628B2 (en) * | 2009-10-07 | 2013-06-18 | Lutron Electronics Co., Inc. | Closed-loop load control circuit having a wide output range |
US7960922B2 (en) * | 2009-10-21 | 2011-06-14 | General Electric Company | High efficiency low power capacitor charged DC driver |
US8212485B2 (en) * | 2009-12-10 | 2012-07-03 | General Electric Company | Dimming bridge module |
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2013
- 2013-01-21 EP EP13705619.8A patent/EP2805576A1/en not_active Ceased
- 2013-01-21 US US14/372,401 patent/US9564828B2/en not_active Expired - Fee Related
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EP2805576A1 (en) | 2014-11-26 |
US9564828B2 (en) | 2017-02-07 |
US20150288293A1 (en) | 2015-10-08 |
CN104115558A (zh) | 2014-10-22 |
WO2013110038A1 (en) | 2013-07-25 |
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