CN104052180A - Multiple symmetrical winding magnetic flux switching motor and winding design method thereof - Google Patents

Multiple symmetrical winding magnetic flux switching motor and winding design method thereof Download PDF

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CN104052180A
CN104052180A CN201410326088.6A CN201410326088A CN104052180A CN 104052180 A CN104052180 A CN 104052180A CN 201410326088 A CN201410326088 A CN 201410326088A CN 104052180 A CN104052180 A CN 104052180A
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winding
coil
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symmetrical
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CN104052180B (en
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花为
邵凌云
程明
王宝安
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Southeast University
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Abstract

The invention discloses a multiple symmetrical winding magnetic flux switching motor and a winding design method thereof. The method is based on exertion of complementarity of windings of the magnetic flux switching motor with maximization of induced electric potential of each phase as the principle, and coil compositions of a phase winding, coil compositions of a set of symmetrical windings and coil connection types of all phase windings are obtained in sequence through optimizing the phase difference between two sets of adjacent symmetrical windings. The winding design method is clear in thinking and easy to operate. The multiple symmetrical winding magnetic flux switching motor has the advantages of being high in no-load induced electric potential sine degree and winding utilization rate, large in torque output and small in electromagnetic torque pulsation, and superior motor performance is embodied.

Description

A kind of multiple symmetric winding flux switch motor and Winding Design method thereof
Technical field
The invention belongs to motor winding construction design field, relate to a kind of multiple symmetric winding flux switch motor and Winding Design method thereof.
Background technology
Magneticflux-switching type magneto has the characteristics such as torque (power) density is high, efficiency is high, rotor structure is firm, is specially adapted to high-grade drives and high-speed applications field.Along with application scenario improving constantly performance requirements such as electric system power grade, fault-tolerant operation and reliabilities, heterogeneous Magneticflux-switching type magneto more and more becomes the emphasis problem of domestic and international Ge great colleges and universities and research institution, because it has not only retained the advantage of common three-phase Magneticflux-switching type magneto, also there is significant advantage aspect following four:
(1), in high-power applications occasion, the power grade that every phase winding distributes, in power device can tolerance range, can directly use calibration power module.
(2) reliability improves.For symmetrical m phase motor, the phase difference between adjacent two phasor1s is 2 π/m.In the time that certain phase winding breaks down, it is less that the power loss that fault phase causes accounts for population proportion, strengthened the fault freedom of motor; For overlapping the neutral point polyphase machine that independently the symmetrical winding of n forms by x, in the time that certain phase winding breaks down, the symmetrical winding of this cover n that directly cuts off this phase winding place, can make motor still can normally move in the situation that not changing control algolithm.
(3), along with the increase of the number of phases, the caused space harmonics magnetic field amplitude of armature winding electric current being provided by inverter reduces, thereby can torque ripple reduction.
(4) coordinate by specific rotor teeth groove, can effectively increase the frequency of location torque, and then reduce the amplitude of location torque, reduce motor torque ripple.
But, torque pulsation is inevitable problem in magneto, and the main cause that produces torque pulsation has: location torque, every mutually unloaded induced potential harmonic wave, d-axis, quadrature axis inductance change the reluctance torque and the armature supply wave distortion of loading etc. that cause.
The Winding Design method of existing flux switch motor only designs the connection of every phase armature winding coil according to the complementary principle of groove conductor electromotive force star graph and winding, and the most multiple symmetric winding is designed to the structure that full symmetric distributes.The method can reduce the harmonic component of induced potential to a certain extent, thereby improves the sinusoidal degree of every phase induced potential, but still has following problem: harmonic wave induced potential cannot be eliminated completely, and the torque pulsation therefore being caused by harmonic wave induced potential still exists; Even if harmonic wave induced potential is negligible, but still more serious by the caused torque pulsation of harmonic component of armature supply; Can not ensure that every mutually unloaded induced potential has higher winding factor, the amplitude and the motor that have affected every mutually unloaded induced potential fundametal compoment are exerted oneself.
Summary of the invention
Technical problem: the invention provides that the total percent harmonic distortion of the unloaded induced potential of a kind of every phase winding is less, electromagnetic torque mean value is higher and can effectively suppress the multiple symmetric winding flux switch motor by the electromagnetic torque pulsation that in unloaded induced potential or armature supply, odd harmonic component causes, a kind of Winding Design method of this motor is provided simultaneously.
Technical scheme: multiple symmetric winding flux switch motor Winding Design method of the present invention, design for the symmetrical winding of x cover n of heterogeneous flux switch motor, comprise the steps:
1) determine that according to motor winding number of phases m and coil number N the coil number of every phase is N/m, then two coils with winding complementarity are connected into a coil groups, the individual coil groups of the N/ of induced potential phase difference minimum (2m) is connected into a phase winding, thereby the coil that obtains first-phase winding forms, wherein armature winding coil number N is the even-multiple of number of phases m, be N=2km, k is positive integer;
2) according to the phase relation between each phase winding in the symmetrical winding of n, be that in the symmetrical winding of a set of n, the phase difference between adjacent two phase windings is 2 π/n, definite and described first-phase winding forms at the coil of other n-1 phase windings of same set of symmetric winding, thereby obtains the formation of the symmetrical winding of first set n;
3) determine the phase difference θ between the symmetrical winding of adjacent two cover n according to following formula set:
Wherein, x is the number of the symmetrical winding of n in multiple symmetric winding flux switch motor, and x, n are the integer that is greater than 1.
4) according to described step 3) in definite phase difference θ set, and phase relation (i-1) θ of other symmetric windings and first set symmetric winding set, determine that successively the coil of other x-1 cover symmetric windings forms, the sequence number that wherein i is symmetric winding, the sequence number of first set symmetric winding is got i=1, and the sequence number of other x-1 cover symmetric windings is i=2,3 ..., x.
In the inventive method, step 1) in, in the time that two coils with winding complementarity are connected into a coil groups, if the unloaded induced potential phase difference of two complementary coils is 180 °, differential concatenation; If the unloaded induced potential phase difference of two complementary coils is 0 °, forward series connection.
Multiple symmetric winding flux switch motor of the present invention, adopts the symmetrical winding of x cover n, the phase difference θ between the symmetrical winding of adjacent two cover n setfor:
Wherein, x is the number of the symmetrical winding of n in multiple symmetric winding flux switch motor, and x, n are the integer that is greater than 1, total number of phases m=xn of motor, and the even-multiple that coil number N is the number of phases, i.e. N=2km, k is positive integer.
In the multiple symmetric winding flux switch motor of the present invention, the symmetrical winding of n is connected into by the individual coil groups of N/ (2m) of induced potential phase difference minimum, and coil groups is formed by connecting by two coils with winding complementarity.
In the above-mentioned preferred version of the multiple symmetric winding flux switch motor of the present invention, if the unloaded induced potential phase difference of two complementary coils is 180 °, differential concatenation; If the unloaded induced potential phase difference of two complementary coils is 0 °, forward series connection.
The inventive method is for instructing the selection of phase difference between winding coil connection, every phase winding composition form and the symmetrical winding of x cover n, object is to increase unloaded induced potential first-harmonic winding factor as far as possible, harmonic reduction component, and the maximum flutter component of offsetting the symmetrical winding electric magnetic torque of every cover n, reduces the torque pulsation of heterogeneous Magneticflux-switching type magneto.When the present invention is intended to improve motor winding factor and unloaded induced potential sine, torque ripple reduction, is applicable to generator designs and motor designs, has both been suitable for pure permanent magnet excitation motor, is also applicable to pure electro-magnetic motor and mixed excitation electric machine.
Beneficial effect: compared with prior art, the present invention is considering, on the basis of groove conductor electromotive force star graph and winding complementarity, the design of polyphase windings to be converted into the design of multiple symmetric winding.In the present invention, the distribution of polyphase windings is no longer confined to full symmetric structure, but by the relation of the phase difference between derivation torque pulsation and adjacent two cover symmetric windings, to eliminate breakdown torque flutter component as object, obtain optimum phase difference, make motor realize following advantage:
1) adopt complementary connection, make the even-order harmonic component basic neutralisation of the unloaded induced potential of every phase winding, remaining odd harmonic component is less, makes total percent harmonic distortion of the unloaded induced potential of every phase winding less, the torque pulsation component that correspondingly harmonic reduction causes;
2) every phase winding is formed by connecting by the coil groups of induced potential phase difference minimum, thereby the first-harmonic winding factor of the unloaded induced potential of every phase winding is high, approach 1, the fundametal compoment amplitude of every mutually unloaded induced potential is effectively improved, thereby improve the mean value of motor electromagnetic torque;
3) phase difference between the symmetrical winding of adjacent two cover n is unique definite by number of phases n and the tricks x of symmetric winding, and computing formula is simple and clear, and Winding Design step is easy to operate;
4) by the phase difference between the symmetrical winding of the adjacent two cover n of appropriate design, the electromagnetic torque pulsation that the odd harmonic component in unloaded induced potential causes is further suppressed, and reduces the shake of motor, thereby improves the stability of motor operation;
5) by the phase difference between the symmetrical winding of the adjacent two cover n of appropriate design, the torque pulsation that in armature winding, the odd harmonic component of loading current causes is effectively suppressed.Because armature supply is supplied with armature winding by inverter, wherein unavoidably there is harmonic component, have a strong impact on the stability of motor torque output.Winding Design method of the present invention, the torque pulsation that can cause for the odd harmonic component in armature supply suppresses or eliminates, and has effectively improved motor torque quality, and reduces the requirement to inverter output characteristic, for the control of motor offers convenience.
Brief description of the drawings
Fig. 1 (a) is the horizontal sectional structure schematic diagram of a stator 24 groove rotor 22 utmost point Magneticflux-switching type magnetoes.
Fig. 1 (b) is the unloaded induced potential star graph of the groove conductor of a stator 24 groove rotor 22 utmost point Magneticflux-switching type magnetoes.Wherein, coil n ' is contrary with n polarity, and the potential vector phase difference of adjacent slot conductor is 150 ° (electrical degrees).
Fig. 2 (a) is the winding vector distribution that a stator 24 groove rotor 22 utmost point Magneticflux-switching type magnetoes two overlap 30 ° of three-phase symmetric winding mutual deviations.
Fig. 2 (b) is the winding vector distribution that a stator 24 groove rotor 22 utmost point Magneticflux-switching type magnetoes two overlap 60 ° of three-phase symmetric winding mutual deviations.
Fig. 3 is that a stator 24 groove rotor 22 utmost point Magneticflux-switching type magnetoes divide at two kinds of windings of Fig. 2 the torque characteristics planting.
Embodiment
Below in conjunction with embodiment and Figure of description, the present invention will be further described.
The multiple symmetric winding flux switch motor of one of the present invention, comprises stator 1, rotor 4 and rotating shaft 5, and rotor 4 is relative with stator 1, and gapped between rotor 4 and stator 1, and rotating shaft 5 is fixedly connected on rotor 4.Described stator 1 and rotor 4 are salient-pole structure.Stator 1 comprises stator core unit and centralized armature winding coil 2.Each stator core unit comprises two U-shaped stator cores 101 and a permanent magnet 3, and permanent magnet 3 is embedded between two U-shaped stator cores 101.Permanent magnet 3 cutting orientation magnetizings, and the magnetizing direction of two adjacent permanent magnets 3 is contrary.Between two adjacent stator core unit, form stator slot 102.Centralized armature winding coil 2, through the stator slot 102 that is positioned at both sides, stator core unit, is wrapped on stator core unit.The quantity of armature winding coil 2 equals the quantity of stator core unit.Stator and rotor iron core is made up of permeability magnetic material.Permanent magnet 3 is made up of permanent magnetic material, and preferably by neodymium iron boron, ferrite, or SmCo is made.
Further, the quantity N of described armature winding coil 2 is the even-multiple of number of phases m, i.e. N=2km, and k is positive integer.
Further, described rotor 4 can be positioned at the inside of stator 1, also can be positioned at the outside of stator 1.
Further, described multiple symmetric winding flux switch motor can be both pure permanent magnet excitation motor, can also be pure electro-magnetic motor, or mixed excitation electric machine, comprise and fill online demagnetization memory electrical machine, and, this motor both can have been made generator operation, can make again electric operation.
Different from traditional flux switch motor, the multiple symmetric winding flux switch motor that the present invention proposes, its armature winding can resolve into the symmetrical winding of x cover n, total number of phases m=xn of this motor, x, n are greater than 1 integer, therefore this motor claims again the symmetrical winding flux switch motor of the heavy n of x.
Innovation of the present invention is: the symmetrical winding of the heavy n of x of this flux switch motor adopts Winding Design method disclosed by the invention, and specific embodiment is as follows:
1) first determine that according to number of phases m and coil number N the coil number of every phase is N/m, every two coils connect into a coil groups conventionally, and the coil groups number of so every phase is N/ (2m).Based on groove conductor electromotive force star graph, by every two coils with winding complementarity be connected into a coil groups (if the unloaded induced potential phase difference of two complementary coils is 180 °, differential concatenation; If the unloaded induced potential phase difference of two complementary coils is 0 °, forward series connection), form altogether thus N/2 coil groups, the phase difference of two coil-induced electromotive forces in each coil groups is 0 ° or 180 °, therefore the spread factor of coil groups induced potential fundametal compoment is 1, and the even-order harmonic component in single coil induced potential disappears mutually, the harmonic content of the unloaded induced potential of coil groups is reduced; Then turn to principle with every phase winding induced potential maximum, the individual coil groups of N/ (2m) of coil groups induced potential phase difference minimum is connected into a phase winding, thereby obtain the coil formation of first-phase winding.
2) according to the phase relation between each phase winding in the symmetrical winding of n, be that in the symmetrical winding of a set of n, the phase difference between adjacent two phase windings is 2 π/n, definite and described first-phase winding forms at the coil of other n-1 phase windings of same set of symmetric winding, thereby obtains the formation of the symmetrical winding of first set n.
3) determine the phase difference between the symmetrical winding of adjacent two cover n.From the Formula of Electromagnetic of the symmetrical winding of x cover n, the phase difference between torque pulsation component and adjacent two cover symmetric windings is relevant.For simplifying derivation, only consider the torque pulsation that caused by induced potential or armature supply odd harmonic here, and ignore the flutter component that amplitude is very little.
The flutter component T of the symmetrical winding electric magnetic torque of n pulsecan be expressed as:
Wherein, T 2knfor the amplitude of 2kn torque pulsation component, θ is rotor-position electrical degree, for the starting phase angle of 2kn torque pulsation component.
The flutter component T of the total electromagnetic torque of the x cover symmetrical winding of n pulse_xcan be expressed as the stack of the symmetrical winding electric magnetic torque of x group n flutter component:
From above formula, the phase difference of 2kn flutter component of the symmetrical winding electric magnetic torque of adjacent two cover n is 2kn θ set.2kn torque pulsation component of x group cancelled out each other, 2kn θ setshould meet following relational expression:
For eliminating breakdown torque flutter component, i.e. 2n torque pulsation component when k=1, adjacent two overlap the preferred phase difference θ between symmetric windings setcan be obtained by above formula abbreviation:
Illustrate in the time that the phase angle difference between adjacent two cover symmetric windings meets (4), can offset the maximum flutter component of electromagnetic torque in the symmetrical winding of every cover n.
4) according to the phase difference calculating in (4), and phase relation (i-1) θ of other symmetric windings and first set symmetric winding set, determine that successively the coil of other x-1 cover symmetric windings forms, the sequence number that wherein i is symmetric winding, the sequence number of first set symmetric winding is got i=1, and the sequence number of other x-1 cover symmetric windings is i=2,3 ..., x.
According to the multiple symmetric winding of the heterogeneous flux switch motor of above-mentioned flow scheme design, both can ensure that motor obtained the mutually unloaded induced potential that sinusoidal degree is higher, can make again winding factor larger, improve the mean value of electromagnetic torque, can reduce the pulsation rate of electromagnetic torque, obtain the torque output of better quality simultaneously.
Taking dual three-phase symmetric winding flux switch permanent magnet motor as example, its common motor topology structure as shown in Fig. 1 (a), totally 24 centralized armature winding coils on stator, be respectively armature winding coil 201,202,203 ..., 224.These 24 coil design are become to 6 phase winding forms, and can be decomposed into two cover three-phase symmetric windings, i.e. m=6, x=2, n=3.Concrete Winding Design flow process is as follows:
1) determine that according to number of phases m=6 and coil number N=24 the coil number of every phase winding is 4, the coil groups number of every phase is 2.According to the groove conductor electromotive force star graph of stator 24 groove rotor 22 utmost point Magneticflux-switching type magnetoes, as shown in Fig. 1 (b), first judging and obtain the coil combination with winding complementarity, is respectively coil 201 (coil 213) and coil 207 (coil 219), coil 202 (coil 214) and coil 208 (coil 220), coil 203 (coil 215) and coil 209 (coil 221), coil 204 (coil 216) and coil 210 (coil 222), coil 205 (coil 217) and coil 211 (coil 223), coil 206 (coil 218) and coil 212 (coil 224), the unloaded induced potential phase difference of two coils in above-mentioned each coil combination is 180 °, pass through differential concatenation, two complementary coils are connected into a coil groups, the not reproducible combination of each coil, forming altogether 12 separate coil groups, is respectively coil 201 and coil 207, coil 202 and coil 208, coil 203 and coil 221, coil 204 and coil 222, coil 205 and coil 211, coil 206 and coil 212, coil 213 and coil 219, coil 214 and coil 220, coil 215 and coil 209, coil 216 and coil 210, coil 217 and coil 223, coil 218 and coil 224.For the spread factor that ensures phase winding induced potential fundametal compoment approaches 1 most, two coil groups of potential vector phase difference minimum are connected into a phase winding.Through observation shows that, coil groups 201+207 ' is 0 ° with the potential vector phase difference of coil groups 213+219 ', and the spread factor of the phase winding induced potential fundametal compoment that these two coil groups series connection form is 1, remembers that this phase winding is A1.
2) in three-phase symmetric winding, differ with A1 phase winding respectively+120 ° ,-120 ° electrical degrees of B1, C1 phase winding, thereby can obtain easily B1, C1 phase winding coil form, as shown in Fig. 2 (a).Thereby determine the coil connected mode of first set three-phase symmetric winding A1, B1, C1.For embodying the advantage of Winding Design method of the present invention, here listed the A1 phase winding type of attachment obtaining according to prior art, as shown in Fig. 2 (b), A1 is made up of coil groups 201+207 ' and coil groups 208+202 ', the potential vector phase difference of these two coil groups is 30 ° of electrical degrees, therefore the spread factor of A1 phase induced potential fundametal compoment is 0.966, and the A1 phase winding spread factor that beguine is designed according to the present invention is low.
3) determine the phase difference θ between two cover three-phase symmetric windings set.Below by theory analysis, the dual three-phase symmetric winding flux switch permanent magnet motor of Yi Yitai is example, and the optimum angle of deriving between its two covers three-phase symmetric winding is poor.
For three-phase symmetrical ac synchronous motor, its electromagnetic torque expression formula is as follows:
Wherein: T 0for the DC quantity of electromagnetic torque, i.e. average electromagnetic torque, T 6kfor the amplitude of 6k torque pulsation component, θ is rotor-position electrical degree, for the starting phase angle of 6k torque pulsation component.Visible, this electromagnetic torque is made up of the multiple subharmonic torque component of average torque component and 6.
For dual three-phase symmetric winding flux switch permanent magnet motor, its electromagnetic torque can be expressed as the electromagnetic torque stack of two three-phase symmetric winding motors:
(6) formula is adopted and poor eliminate indigestion formula, can obtain:
From (7) formula, as cos (3k θ set)=0 o'clock, 6k time torque pulsation component can be eliminated.Therefore, want farthest torque ripple reduction, can be to breakdown torque flutter component T 6offset, θ is easy to get set=30 °.Therefore, in dual three-phase symmetric winding flux switch permanent magnet motor, in the time that the phase difference between two cover three phase windings is 30 °, 6 flutter components of electromagnetic torque are eliminated completely, and now torque pulsation is taking 12 pulsation as main, and pulsation amplitude is very little.
4) phase difference between another set of three-phase symmetric winding A2, B2, C2 and first set three-phase symmetric winding A1, B1, C1 is 30 °, so 30 ° mutually of 30 ° mutually of A2 leading (or hysteresis) A1,30 ° mutually of B2 leading (or hysteresis) B1, C2 leading (or hysteresis) C1.Again according to groove conductor electromotive force star graph, just can determine easily that the coil of A2, B2, C2 phase winding forms, as shown in Fig. 2 (a).Thereby determine the armature winding type of attachment of whole dual three-phase symmetric winding flux switch permanent magnet motor.
Fig. 2 (a) is θ setthe asymmetric 6 phase windings distributions (Winding Design method of the present invention) of=30 °; Fig. 2 (b) is θ setthe symmetry 6 phase windings distributions (existing Winding Design method) of=60 °.For illustrating that Winding Design method of the present invention has advantage compared with existing Winding Design method, Fig. 3 has compared the electromagnetic torque waveform of dual three-phase symmetric winding flux switch motor under these two kinds of Winding Design methods.By more known, two cover three phase windings in the time of 60 ° of phase place mutual deviations, the ripple frequency of electromagnetic torque is fundamental frequency 6 times, pulsation amplitude is larger; In the time of 30 ° of two cover three phase winding phase place mutual deviations, the ripple frequency of electromagnetic torque is 12 times of fundamental frequency, pulsation amplitude is very little, exert oneself larger, thereby verified step 3) theoretical analysis result, embody multiple symmetric winding flux switch motor Winding Design method of the present invention and there is novelty and superiority.
Below be only the preferred embodiment of the present invention; be noted that for those skilled in the art; under the premise without departing from the principles of the invention; can also make the some improvement that can expect and be equal to replacement; these improve the claims in the present invention and are equal to the technical scheme after replacement, all fall into protection scope of the present invention.

Claims (5)

1. a Winding Design method for multiple symmetric winding flux switch motor, is characterized in that, the method designs for the symmetrical winding of x cover n of heterogeneous flux switch motor, comprises the following steps:
1) determine that according to motor winding number of phases m and coil number N the coil number of every phase is N/m, then two coils with winding complementarity are connected into a coil groups, the individual coil groups of the N/ of induced potential phase difference minimum (2m) is connected into a phase winding, thereby the coil that obtains first-phase winding forms, wherein armature winding coil number N is the even-multiple of number of phases m, be N=2km, k is positive integer;
2) according to the phase relation between each phase winding in the symmetrical winding of n, be that in the symmetrical winding of a set of n, the phase difference between adjacent two phase windings is 2 π/n, definite and described first-phase winding forms at the coil of other n-1 phase windings of same set of symmetric winding, thereby obtains the formation of the symmetrical winding of first set n;
3) determine the phase difference θ between the symmetrical winding of adjacent two cover n according to following formula set:
Wherein, x is the number of the symmetrical winding of n in multiple symmetric winding flux switch motor, and x, n are the integer that is greater than 1.
4) according to described step 3) in definite phase difference θ set, and phase relation (i-1) θ of other symmetric windings and first set symmetric winding set, determine that successively the coil of other x-1 cover symmetric windings forms, the sequence number that wherein i is symmetric winding, the sequence number of first set symmetric winding is got i=1, and the sequence number of other x-1 cover symmetric windings is i=2,3 ..., x.
2. Winding Design method according to claim 1, it is characterized in that described step 1) in, in the time that two coils with winding complementarity are connected into a coil groups, if the unloaded induced potential phase difference of two complementary coils is 180 °, differential concatenation; If the unloaded induced potential phase difference of two complementary coils is 0 °, forward series connection.
3. a multiple symmetric winding flux switch motor, is characterized in that, this motor adopts the symmetrical winding of x cover n, the phase difference θ between the symmetrical winding of adjacent two cover n setfor:
Wherein, x is the number of the symmetrical winding of n in multiple symmetric winding flux switch motor, and x, n are the integer that is greater than 1, total number of phases m=xn of motor, and the even-multiple that coil number N is the number of phases, i.e. N=2km, k is positive integer.
4. multiple symmetric winding flux switch motor according to claim 3, it is characterized in that, the symmetrical winding of described n is connected into by the individual coil groups of N/ (2m) of induced potential phase difference minimum, and described coil groups is formed by connecting by two coils with winding complementarity.
5. multiple symmetric winding flux switch motor according to claim 4, is characterized in that, if the unloaded induced potential phase difference of two complementary coils is 180 °, and differential concatenation; If the unloaded induced potential phase difference of two complementary coils is 0 °, forward series connection.
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CN102290883A (en) * 2011-08-26 2011-12-21 东南大学 Redundant excitation double-armature winding multiphase magnetic flux switching motor with fault-tolerant teeth
CN202206208U (en) * 2011-08-26 2012-04-25 东南大学 Redundant exciting double-armature winding multi-phase flux switching type motor
CN102868246A (en) * 2012-09-19 2013-01-09 武汉新能源接入装备与技术研究院有限公司 High-capacity low-speed permanent-magnet wind-driven generator
CN103280902A (en) * 2013-05-06 2013-09-04 东南大学 Twelve-phase stator permanent magnet type magnetic flux switching motor
CN103248158A (en) * 2013-05-10 2013-08-14 东南大学 Six-phase flux switching type permanent magnet motor

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CN104539127A (en) * 2015-01-04 2015-04-22 侯惜之 Magnet and iron-core coil integrated type electric generator
CN105471148A (en) * 2015-12-04 2016-04-06 重庆智仁发电设备有限责任公司 5KW 8-pole 48V intermediate-frequency dual-winding direct current electric generator
CN105743257A (en) * 2016-04-01 2016-07-06 东南大学 Magnetic flux switching brushless motor adopting single-layer stacked winding
CN105743257B (en) * 2016-04-01 2018-04-03 东南大学 A kind of individual layer lap winding magnetic flux switches brushless electric machine
CN108649768A (en) * 2018-06-11 2018-10-12 中国石油大学(华东) A kind of stator carries the mixed excited magnetic pass switch motor of pawl pole bypass structure
CN109038905A (en) * 2018-08-30 2018-12-18 哈尔滨电机厂有限责任公司 Symmetrical four branches wave winding connection method

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