CN102904458B - Control method and device for inverter - Google Patents
Control method and device for inverter Download PDFInfo
- Publication number
- CN102904458B CN102904458B CN201210444243.5A CN201210444243A CN102904458B CN 102904458 B CN102904458 B CN 102904458B CN 201210444243 A CN201210444243 A CN 201210444243A CN 102904458 B CN102904458 B CN 102904458B
- Authority
- CN
- China
- Prior art keywords
- voltage
- axle
- value
- control
- shaft
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Abstract
The embodiment of the invention discloses a voltage sag generation device and a control method and a control device for an inverter. The generation device comprises a modular multi-level rectifier and a modular multi-level inverter, wherein the modular multi-level rectifier is connected with the modular multi-level inverter in a back-to-back power transmission connection manner, and the structures of the modular multi-level rectifier and the modular multi-level inverter are the same; each of the modular multi-level rectifier and the modular multi-level inverter comprises three phase units which are connected in parallel with one another; each phase unit consists of two bridge arms which are connected in series with each other; any bridge arm consists of N sub modules SM and a valve reactor which are connected in series; and each SM consists of two insulated gate bipolar transistor (IGBT) switching devices and a direct current energy storage capacitor which are connected in parallel. The device can precisely control a voltage sag depth, lasting time, a phase and a sag type and can be easily expanded to high voltage and high power grade; requirements on high voltage and high power are met; a requirement on the switching devices is low, and the switching devices are easy to purchase; the price is low; an output waveform is relatively high in quality; and the number of filters on an alternating current side is reduced.
Description
Technical field
The present invention relates to mobile electrical network field, particularly relate to a kind of voltage sag generator, the control method of inverter and device.
Background technology
Wind power generation receives much concern as a kind of green regenerative energy sources.Constantly increase along with Wind turbines installed capacity accounts for electrical network proportion, wind generator system is by combining inverter and get access to grid, and when grid collapses causes Voltage Drop to a certain degree, will cause combining inverter and grid disconnection; Penetrate power with wind power generation constantly to increase, if a large amount of wind generator system is when electric network fault and grid disconnection, has a strong impact on causing the voltage of electrical network and frequency, even may aggravate fault degree, finally causing system unit all solutions to arrange.Therefore the serviceability of blower fan under grid fault conditions seems very important.The new operation of power networks criterion of China explicitly calls for grid type Wind turbines can not off-grid in certain hour under Voltage Drop, must possess certain low voltage ride-through capability (Low Voltage Ride Through, LVRT).
The LVRT of research wind generator system under electric network fault, first needs the grid voltage sags generating means that applicable wind power generation is studied.Voltage Drop is electric network fault type the most common, only have all kinds of accurate simulation Voltage Drop, namely, only having can the accurately control voltage type falling the degree of depth, duration, phase place and fall, random waveform voltage required for generation is to adapt to the demand of wind power system test under different faults condition, and research wind generator system low voltage crossing control strategy is just of practical significance.
And electric network fault or disturbance cause the Voltage Drop of wind farm grid-connected point to have uncontrollability, and in order to the low voltage ride-through capability of development& testing Wind turbines, special equipment must be had to simulate various types of Voltage Drop, this equipment is called voltage falling generator (Voltage Sag Generater, VSG).
The VSG based on two level voltage source converters is adopted in prior art.Converter adopts two level voltage sources, line voltage is powered to tested equipment through ac-dc-ac transform, rectifier control inputs power factor, maintenance DC-side Voltage Stabilization, by the control to inverter, can produce required various types of Voltage Drop waveforms.The voltage falling generator scheme that feasibility is strong will meet the requirement of three aspects: high-power grade, realize simple and cost is low.
In the VSG of prior art, when needs support that high-power exports, grade must be expanded, need to adopt a large amount of switching device directly to connect, the coherence request that the connected mode of this direct series connection turns on and off each device is very high, meanwhile, the stress also causing switching device to bear is larger.Therefore, this is also just harsh to the manufacturing technique requirent of switching device, and this switching device be suitable at present, its purchasing price is very expensive, and price, up to hundreds of thousands of dollars, causes the production cost of VSG very high.
Summary of the invention
In order to solve the problem, the object of the invention is the control method and the device that provide a kind of voltage sag generator, inverter, accurately control voltage the degree of depth can be fallen, duration, phase place and the type fallen, and very easyly high voltage and high-power grade can be expanded to, meet the demand of high-tension high-power, less demanding to switching device, easily buys, low price, and the waveform quality exported is more excellent, also reduces the filter of AC.
The invention provides a kind of voltage sag generator, comprising:
Modular multilevel rectifier and modular multilevel inverter;
Described modular multilevel rectifier is connected with connected mode of transmitting electricity back-to-back with described modular multilevel inverter, and described modular multilevel inverter is identical with the structure of described modular multilevel rectifier; Wherein,
Described modular multilevel rectifier comprises: the first brachium pontis connect with four bridge legs second-phase unit, the 5th brachium pontis of being formed of the first-phase unit, the 3rd brachium pontis that are formed of connecting with the second brachium pontis is connected with the 6th brachium pontis the third phase unit formed, three facies unit parallel connections;
Six brachium pontis, in series by a N number of submodule SM and valve reactor, N be more than or equal to 1 natural number;
Described SM comprises two IGBT derailing switches and a DC energy storage electric capacity, with a DC energy storage Capacitance parallel connection after described two IGBT derailing switches series connection.
A control method for inverter, controls the modular multilevel inverter in described device, comprising:
The three-phase actual current of detection module multi-electrical level inverter side ac bus, three-phase virtual voltage and three-phase reference voltage;
Described three-phase actual current, three-phase virtual voltage and three-phase reference voltage are carried out Coordinate Conversion respectively, obtains the d axle component of actual current and q axle component, the d axle component of virtual voltage and the d axle component of q axle component and reference voltage and q axle component;
Calculate the difference between the reference voltage of d axle and q axle component and virtual voltage respectively, and respectively voltage-regulation is carried out to described difference, obtain d shaft voltage regulated value and q shaft voltage regulated value;
Respectively Current adjustment is carried out to actual current q axle component and actual current d axle component, obtain the first modulation voltage and the second modulation voltage;
Calculate described d shaft voltage regulated value and the first modulation voltage and value, obtain d axle output voltage, calculate q shaft voltage regulated value and the second modulation voltage difference, obtain q axle output voltage;
Calculate voltage and the value of d axle and q axle output voltage and each self-dalay T/4 respectively, obtain d axle control voltage and q axle control voltage respectively, the angular frequency of T to be 2 π/w, w be predetermined current;
Coordinate Conversion is carried out to d axle control voltage and q axle control voltage, obtains α axle control voltage and β axle control voltage;
Trigger impulse generating process is carried out to described α axle control voltage and β axle control voltage, obtains the pulse signal controlling described modular multilevel inverter.
Preferably, the described difference calculated respectively between the reference voltage of d axle and q axle component and virtual voltage, and respectively voltage-regulation control is carried out to described difference, obtain d shaft voltage regulated value and q shaft voltage regulated value, comprising:
By PI proportional integral conditioning controller, according to formula: Vd=k1 (Udref-Ud)+k2 ∫ (Uref-Ud) dt calculates d shaft voltage regulated value, wherein, Vd is d shaft voltage regulated value, k1 and k2 is regulable control coefficient respectively, Udref is d axle reference voltage, and Ud is d axle virtual voltage; And
According to formula: Vq=k3 (Udref-Uq)+k4 ∫ (Uqref-Uq) dt, calculate q shaft voltage regulated value, wherein, Vq is q shaft voltage regulated value, k3 and k4 is regulable control coefficient respectively, and Uqref is q axle reference voltage respectively, and Uq is q axle virtual voltage.
Preferably, describedly respectively Current adjustment is carried out to the actual current value of q axle and the actual current value of d axle, obtains the first modulation voltage and the second modulation voltage, comprising:
According to formula: V1=ω Li
q, carry out Current adjustment to the actual current value of q axle, calculate the first modulation voltage, wherein V1 is the first modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
qit is q axle actual current value;
According to formula: V2=ω Li
d, carry out Current adjustment to the actual current value of d axle, calculate the second modulation voltage, wherein V2 is the second modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
dit is d axle actual current value.
Preferably, described calculating described d shaft voltage regulated value and the first modulation voltage and value, obtain d axle output voltage, calculates q shaft voltage regulated value and the second modulation voltage difference, obtain q axle output voltage, comprising:
According to formula: V1 (t)=k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt+ ω Li
q, calculate d axle output voltage, wherein, V1 (t) is d axle output voltage, and k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt is d shaft voltage regulated value, ω Li
qbe the first modulation voltage, k1 and k2 is regulable control coefficient respectively, Udref and Ud is reference voltage and the virtual voltage of d axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
qit is actual current q axle value;
According to formula: V2 (t)=k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt-ω Li
d, calculate q axle output voltage, wherein, V2 (t) is q axle output voltage, and k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt is q shaft voltage regulated value, ω Li
dbe the second modulation voltage, k3 and k4 is regulable control coefficient respectively, Uqref and Uq is reference voltage and the virtual voltage of q axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
dit is the d axle value of actual current.
Preferably, described voltage and the value calculating d axle and q axle output voltage and each self-dalay T/4 respectively, obtains d axle control voltage and q axle control voltage respectively, comprising:
According to formula: Vd (t)=V1 (t)+V1 (t-T/4), calculate described d axle output voltage and the voltage and the value that postpone T/4, obtain d axle control voltage, wherein, Vd (t) is d axle control voltage, V1 (t) is d axle output voltage, and V1 (t-T/4) is the voltage postponing T/4;
According to formula: Vq (t)=V2 (t)+V2 (t-T/4), calculate described q axle output voltage and the voltage and the value that postpone T/4, obtain q axle control voltage, wherein, Vq (t) is q axle control voltage, V2 (t) is q axle output voltage, and V2 (t-T/4) is the voltage postponing T/4.
Preferably, also comprise:
With the pulse signal of the described modular multilevel inverter of the control obtained, control opening or turning off of insulated gate bipolar transistor IGBT in each submodule of described modular multilevel inverter SM, produce the output voltage of described modular multilevel inverter AC.
A control device for inverter, controls the modular multilevel inverter in described device, comprising:
Detection module, for detecting the three-phase actual current of multi-electrical level inverter side ac bus, three-phase virtual voltage and three-phase with reference to phase voltage;
First coordinate transferring, for the three-phase actual current to detection, three-phase virtual voltage and three-phase with reference to phase voltage, carry out Coordinate Conversion respectively, obtain the d axle component of actual current and q axle component, the d axle component of virtual voltage and the d axle component of q axle component and reference voltage and q axle component;
First computing module, for calculating the difference between the reference voltage of d axle and q axle component and virtual voltage respectively, and carries out voltage-regulation control respectively to described difference, obtains d shaft voltage regulated value and q shaft voltage regulated value;
First adjustment module, for carrying out Current adjustment to the current value of q axle and the current value of d axle respectively, obtains the first modulation voltage and the second modulation voltage;
Second computing module, for calculating described d shaft voltage regulated value and the first regulation voltage and value, obtains d axle output voltage, calculates q shaft voltage regulated value and the second regulation voltage difference, obtains q axle output voltage;
Delay disposal module, for calculating voltage and the value of d axle and q axle output voltage and each self-dalay T/4 respectively, obtains d axle control voltage and q axle control voltage respectively;
Second coordinate transferring, for carrying out Coordinate Conversion to d axle control voltage and q axle control voltage, obtains α axle control voltage and β axle control voltage;
Pulse signal generation module, carries out trigger impulse generating process to described α axle control voltage and β axle control voltage, obtains the pulse signal of control inverter.
Preferably, described first computing module, comprising:
D shaft voltage regulates submodule, for passing through PI proportional integral conditioning controller, according to formula:
Vd＝k1(Udref-Ud)+k2∫(Uref-Ud)dt
Calculate d shaft voltage regulated value, wherein, Vd is d shaft voltage regulated value, k1 and k2 is regulable control coefficient respectively, and Udref is d axle reference voltage, and Ud is d axle virtual voltage; And
Q shaft voltage regulates submodule: for according to formula: Vq=k3 (Udref-Uq)+k4 ∫ (Uqref-Uq) dt, calculate q shaft voltage regulated value, wherein, Vq is q shaft voltage regulated value, k3 and k4 is regulable control coefficient respectively, Uqref is q axle reference voltage respectively, and Uq is q axle virtual voltage.
Preferably, described first adjustment module, comprising:
Q shaft current regulates submodule, for according to formula: V1=ω Li
q, carry out Current adjustment to the actual current value of q axle, calculate the first modulation voltage, wherein V1 is the first modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
qit is q axle actual current value;
D shaft current regulates submodule, for according to formula: V2=ω Li
d, carry out Current adjustment to the actual current value of d axle, calculate the second modulation voltage, wherein V2 is the second modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
dit is d axle actual current value.
Preferably, described second computing module, comprising:
D axle output voltage calculating sub module, for according to formula:
V1 (t)=k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt+ ω Li
q, calculate d axle output voltage, wherein, V1 (t) is d axle output voltage, and k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt is d shaft voltage regulated value, ω Li
qbe the first modulation voltage, k1 and k2 is regulable control coefficient respectively, Udref and Ud is reference voltage and the virtual voltage of d axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
qit is actual current q axle value;
Q axle output voltage calculating sub module, for according to formula:
V2 (t)=k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt-ω Li
d, calculate q axle output voltage, wherein, V2 (t) is q axle output voltage, and k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt is q shaft voltage regulated value, ω Li
dbe the second modulation voltage, k3 and k4 is regulable control coefficient respectively, Uqref and Uq is reference voltage and the virtual voltage of q axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
dit is the d axle value of actual current.
Preferably, described delay disposal module, comprising:
D axle postpones submodule, for according to formula: Vd (t)=V1 (t)+V1 (t-T/4), calculate described d axle output voltage and the voltage and the value that postpone T/4, obtain d axle control voltage, wherein, Vd (t) is d axle control voltage, and V1 (t) is d axle output voltage, and V1 (t-T/4) is the voltage postponing T/4;
Q axle postpones submodule, for according to formula: Vq (t)=V2 (t)+V2 (t-T/4), calculate described q axle output voltage and the voltage and the value that postpone T/4, obtain q axle control voltage, wherein, Vq (t) is q axle control voltage, and V2 (t) is q axle output voltage, and V2 (t-T/4) is the voltage postponing T/4.
Preferably, also comprise trigger impulse module,
Described trigger module, pulse signal for producing according to pulse signal generation module controls opening or turning off, producing the output voltage of described modular multilevel inverter AC of insulated gate bipolar transistor IGBT in each submodule of described modular multilevel inverter.
A kind of voltage sag generator provided by the present invention, the modular circuit structure adopted, can increase according to current demand or reduce the number of submodule SM, to support the voltage tester engineering demand of high-tension high-power, and the technological requirement reduced switching device, reduce the manufacturing cost of device and integrated difficulty, improve the performance of whole system, the control method provided controls the inverter in voltage sag generator, adopt the method for delay disposal, eliminate the alternating current component problem of two frequencys multiplication, produce control voltage more accurately, through trigger impulse generating process, obtain the pulse signal of control module multi-electrical level inverter, with this pulse signal, opening of the switching device in inverter Neutron module SM is controlled with closedown, thus realize the generation of various waveform voltage.
Accompanying drawing explanation
In order to be illustrated more clearly in the embodiment of the present invention or technical scheme of the prior art, be briefly described to the accompanying drawing used required in embodiment or description of the prior art below, apparently, accompanying drawing in the following describes is only some embodiments of the present invention, for those of ordinary skill in the art, under the prerequisite not paying creative work, other accompanying drawing can also be obtained according to these accompanying drawings.
Fig. 1 is a kind of voltage sag generator structural representation that the embodiment of the present invention one discloses;
Fig. 2 is the control method flow chart of a kind of inverter that the embodiment of the present invention two discloses;
Fig. 3 is the control method flow chart of the another kind of inverter that the embodiment of the present invention three discloses;
Fig. 4 is the control device structural representation of a kind of inverter that the embodiment of the present invention four discloses;
Fig. 5 is the control device structural representation of the another kind of inverter that the embodiment of the present invention five discloses.
Embodiment
For enabling above-mentioned purpose of the present invention, feature and advantage become apparent more, are described in detail the embodiment of the present invention below in conjunction with accompanying drawing.
Embodiment one
The invention provides a kind of voltage sag generator, here is that embodiment one is described for example, specifically refers to Fig. 1, and it is a kind of voltage sag generator structural representation that the embodiment of the present invention one discloses, and specifically comprises:
Modular multilevel rectifier and modular multilevel inverter;
Described modular multilevel rectifier is connected with connected mode of transmitting electricity back-to-back with described modular multilevel inverter, and described modular multilevel inverter is identical with the structure of described modular multilevel rectifier; Wherein,
Described modular multilevel rectifier comprises: the first brachium pontis connect with four bridge legs second-phase unit, the 5th brachium pontis of being formed of the first-phase unit, the 3rd brachium pontis that are formed of connecting with the second brachium pontis is connected with the 6th brachium pontis the third phase unit formed, three facies unit parallel connections;
Six brachium pontis, in series by a N number of submodule SM and valve reactor, N be more than or equal to 1 natural number;
Described SM comprises two IGBT derailing switches and a DC energy storage electric capacity, with a DC energy storage Capacitance parallel connection after described two IGBT derailing switches series connection.
Said apparatus, the modular circuit structure adopted, can increase according to current demand or reduce the number of submodule SM, to support the voltage tester engineering demand of high-tension high-power, and the technological requirement reduced switching device, reduce the manufacturing cost of device and integrated difficulty, improve the performance of whole system.
Embodiment two
For the device described in above-described embodiment, owing to there is static state, dynamic voltage balancing, electromagnetic interference and the problems such as too high switching loss can being brought due to too high switching frequency, therefore the Voltage Drop waveform quality of VSG output is not high, harmonic content is larger, particularly when the number of submodule is many, these problems can be more serious.Prior art is typically employed in AC and installs the method that a filter carries out filtering, eliminates the problems referred to above to a certain extent, avoids having an impact to the performance of whole VSG circuit.But when AC installing filter thoroughly eliminates the alternating current component of two frequencys multiplication, its filter effect is larger by frequency influence, frequency fluctuation can make performance of filter be deteriorated, cause delay to a certain degree, thus make the waveform quality of generation poor, cannot testing requirement be met.
For above-mentioned technical problem, the invention provides a kind of control method of inverter, modular multilevel inverter in said apparatus is controlled, thus the alternating current component problem solved for thoroughly eliminating two frequencys multiplication, also solve in the Cost Problems brought of AC case subfilter and technical problem simultaneously.
In order to the method that the present invention proposes better is described, be described for embodiment two below, specifically as Fig. 2 a kind of control method flow chart of inverter that discloses, specifically comprise the following steps:
Step 201: the three-phase actual current of detection module multi-electrical level inverter side ac bus, three-phase virtual voltage and three-phase reference voltage;
Step 202: described three-phase actual current, three-phase virtual voltage and three-phase reference voltage are carried out Coordinate Conversion respectively, obtains the d axle component of actual current and q axle component, the d axle component of virtual voltage and the d axle component of q axle component and reference voltage and q axle component;
Step 203: calculate the difference between the reference voltage of d axle and q axle component and virtual voltage respectively, and respectively voltage-regulation is carried out to described difference, obtain d shaft voltage regulated value and q shaft voltage regulated value;
Step 204: respectively Current adjustment is carried out to actual current q axle component and actual current d axle component, obtain the first modulation voltage and the second modulation voltage;
Step 205: calculate described d shaft voltage regulated value and the first modulation voltage and value, obtain d axle output voltage, calculates q shaft voltage regulated value and the second modulation voltage difference, obtains q axle output voltage;
Step 207: the voltage and the value that calculate d axle and q axle output voltage and each self-dalay T/4 respectively, obtain d axle control voltage and q axle control voltage respectively, the angular frequency of T to be 2 π/w, w be predetermined current;
Step 208: carry out Coordinate Conversion to d axle control voltage and q axle control voltage, obtains α axle control voltage and β axle control voltage;
Step 209: trigger impulse generating process is carried out to described α axle control voltage and β axle control voltage, obtains the pulse signal controlling described modular multilevel inverter.
By the method that above-described embodiment describes, the method of delay disposal can be adopted, eliminate the alternating current component problem of two frequencys multiplication, produce control voltage more accurately, through trigger impulse generating process, obtain the pulse signal of control module multi-electrical level inverter, with this pulse signal, opening of the switching device in inverter Neutron module SM is controlled with closedown, thus realize the generation of various waveform voltage.
Embodiment three
In order to the method proposed the present invention, more specifically describe, be described for embodiment three below, specifically refer to Fig. 3 propose another kind of inverter control method flow chart shown in, specifically comprise the following steps:
Step 301: the three-phase actual current of detection module multi-electrical level inverter side ac bus, three-phase virtual voltage and three-phase reference voltage;
Step 302: described three-phase actual current, three-phase virtual voltage and three-phase reference voltage are carried out Coordinate Conversion respectively, obtains the d axle component of actual current and q axle component, the d axle component of virtual voltage and the d axle component of q axle component and reference voltage and q axle component;
Step 303: calculate the difference between the reference voltage of d axle and q axle component and virtual voltage respectively, and respectively voltage-regulation is carried out to described difference, obtain d shaft voltage regulated value and q shaft voltage regulated value;
Above-mentioned steps 303, such as, can be specially: step 303A, by PI proportional integral conditioning controller,
According to formula: Vd=k1 (Udref-Ud)+k2 ∫ (Uref-Ud) dt, calculate d shaft voltage regulated value, wherein, Vd is d shaft voltage regulated value, k1 and k2 is regulable control coefficient respectively, and Udref is d axle reference voltage, and Ud is d axle virtual voltage; And
Step 303B, by PI proportional integral conditioning controller, according to formula: Vq=k3 (Udref-Uq)+k4 ∫ (Uqref-Uq) dt, calculate q shaft voltage regulated value, wherein, Vq is q shaft voltage regulated value, k3 and k4 is regulable control coefficient respectively, Uqref is q axle reference voltage respectively, and Uq is q axle virtual voltage.
Above-mentioned steps 303A and 303B does not have sequencing requirement, can any one step first carry out, and two steps can carry out simultaneously yet, is only wherein a kind of situation shown in Fig. 3.
Step 304: respectively Current adjustment is carried out to actual current q axle component and actual current d axle component, obtain the first modulation voltage and the second modulation voltage;
Above-mentioned steps 304, such as, can be specially: step 304A, according to formula: V1=ω Li
q, carry out Current adjustment to the actual current value of q axle, calculate the first modulation voltage, wherein V1 is the first modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
qit is q axle actual current value;
Step 304B is according to formula: V2=ω Li
d, carry out Current adjustment to the actual current value of d axle, calculate the second modulation voltage, wherein V2 is the second modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
dit is d axle actual current value.
Above-mentioned steps 304A and 304B does not have sequencing requirement, can any one step first carry out, and two steps can carry out simultaneously yet, is only wherein a kind of situation shown in Fig. 3.
Step 305: calculate described d shaft voltage regulated value and the first modulation voltage and value, obtain d axle output voltage, calculates q shaft voltage regulated value and the second modulation voltage difference, obtains q axle output voltage;
Above-mentioned steps 305, such as, can be specially: step 305A is according to formula: V1 (t)=k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt+ ω Li
q, calculate d axle output voltage, wherein, V1 (t) is d axle output voltage, and k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt is d shaft voltage regulated value, ω Li
qbe the first modulation voltage, k1 and k2 is regulable control coefficient respectively, Udref and Ud is reference voltage and the virtual voltage of d axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
qit is actual current q axle value;
Step 305B, according to formula: V2 (t)=k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt-ω Li
d, calculate q axle output voltage, wherein, V2 (t) is q axle output voltage, and k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt is q shaft voltage regulated value, ω Li
dbe the second modulation voltage, k3 and k4 is regulable control coefficient respectively, Uqref and Uq is reference voltage and the virtual voltage of q axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
dit is the d axle value of actual current.
Above-mentioned steps 305A and 305B does not have sequencing requirement, can any one step first carry out, and two steps can carry out simultaneously yet, is only wherein a kind of situation shown in Fig. 3.
Step 306: the voltage and the value that calculate d axle and q axle output voltage and each self-dalay T/4 respectively, obtain d axle control voltage and q axle control voltage respectively, the angular frequency of T to be 2 π/w, w be predetermined current;
Above-mentioned steps 306, such as can be specially: step 306A, according to formula: Vd (t)=V1 (t)+V1 (t-T/4), calculate described d axle output voltage and the voltage and the value that postpone T/4, obtain d axle control voltage, wherein, Vd (t) is d axle control voltage, V1 (t) is d axle output voltage, and V1 (t-T/4) is the voltage postponing T/4;
Step 306B, according to formula: Vq (t)=V2 (t)+V2 (t-T/4), calculate described q axle output voltage and the voltage and the value that postpone T/4, obtain q axle control voltage, wherein, Vq (t) is q axle control voltage, and V2 (t) is q axle output voltage, and V2 (t-T/4) is the voltage postponing T/4.
Above-mentioned steps 306A and 306B does not have sequencing requirement, can any one step first carry out, and two steps can carry out simultaneously yet, is only wherein a kind of situation shown in Fig. 3.
Step 307: carry out Coordinate Conversion to d axle control voltage and q axle control voltage, obtains α axle control voltage and β axle control voltage;
Step 308: trigger impulse generating process is carried out to described α axle control voltage and β axle control voltage, obtains the pulse signal controlling described modular multilevel inverter.
Said method, also comprise, step 309: with the pulse signal of the described modular multilevel inverter of the control obtained, control opening or turning off of insulated gate bipolar transistor IGBT in each submodule of described modular multilevel inverter SM, produce the output voltage of described modular multilevel inverter AC.
By the method that above-described embodiment describes, concrete calculating can be adopted to carry out regulable control to electric current and voltage, adopt the method for delay disposal, eliminate the alternating current component problem of two frequencys multiplication, produce control voltage more accurately, through trigger impulse generating process, obtain the pulse signal of control module multi-electrical level inverter, with this pulse signal, opening of the switching device in inverter Neutron module SM is controlled with closedown, thus realize the generation of various waveform voltage.
Embodiment four
Present invention also offers a kind of control device of inverter, modular multilevel inverter in device described in above-described embodiment 1 is controlled, is example to embodiment four below, is described, specifically refer to the control device structural representation of a kind of inverter shown in Fig. 4, specifically comprise:
Detection module 401, for detecting the three-phase actual current of multi-electrical level inverter side ac bus, three-phase virtual voltage and three-phase with reference to phase voltage;
First coordinate transferring 402, for the three-phase actual current to detection, three-phase virtual voltage and three-phase with reference to phase voltage, carry out Coordinate Conversion respectively, obtain the d axle component of actual current and q axle component, the d axle component of virtual voltage and the d axle component of q axle component and reference voltage and q axle component;
First computing module 403, for calculating the difference between the reference voltage of d axle and q axle component and virtual voltage respectively, and carries out voltage-regulation control respectively to described difference, obtains d shaft voltage regulated value and q shaft voltage regulated value;
First adjustment module 404, for carrying out Current adjustment to the current value of q axle and the current value of d axle respectively, obtains the first modulation voltage and the second modulation voltage;
Second computing module 405, for calculating described d shaft voltage regulated value and the first regulation voltage and value, obtains d axle output voltage, calculates q shaft voltage regulated value and the second regulation voltage difference, obtains q axle output voltage;
Delay disposal module 406, for calculating voltage and the value of d axle and q axle output voltage and each self-dalay T/4 respectively, obtains d axle control voltage and q axle control voltage respectively;
Second coordinate transferring 407, for carrying out Coordinate Conversion to d axle control voltage and q axle control voltage, obtains α axle control voltage and β axle control voltage;
Pulse signal generation module 408, carries out trigger impulse generating process to described α axle control voltage and β axle control voltage, obtains the pulse signal of control inverter.
Preferably, said apparatus, also comprise: trigger module, pulse signal for producing according to pulse signal generation module controls opening or turning off, producing the output voltage of described modular multilevel inverter AC of insulated gate bipolar transistor IGBT in each submodule of described modular multilevel inverter.
Pass through said apparatus, the delay disposal module adopted, the alternating current component problem of two frequencys multiplication can be eliminated, whole device can produce control voltage more accurately, through trigger impulse resume module, produce the pulse signal of control module multi-electrical level inverter, with this pulse signal, opening of the switching device in inverter Neutron module SM is controlled with closedown, thus realize the generation of various waveform voltage.
Embodiment five
With embodiment five specifically, control device provided by the invention is described below, specifically refers to the control device that Fig. 5 is the another kind of inverter that this aspect discloses, specifically comprise:
Detection module 501, for detecting the three-phase actual current of multi-electrical level inverter side ac bus, three-phase virtual voltage and three-phase with reference to phase voltage;
First coordinate transferring 502, for the three-phase actual current to detection, three-phase virtual voltage and three-phase with reference to phase voltage, carry out Coordinate Conversion respectively, obtain the d axle component of actual current and q axle component, the d axle component of virtual voltage and the d axle component of q axle component and reference voltage and q axle component;
First computing module 503, for calculating the difference between the reference voltage of d axle and q axle component and virtual voltage respectively, and carries out voltage-regulation control respectively to described difference, obtains d shaft voltage regulated value and q shaft voltage regulated value;
Preferably, above-mentioned first computing module 503, comprise: d shaft voltage regulates submodule 503A and q shaft voltage to regulate submodule 503B, wherein, d shaft voltage regulates submodule 503A, for by PI proportional integral conditioning controller, according to formula: Vd=k1 (Udref-Ud)+k2 ∫ (Uref-Ud) dt
Calculate d shaft voltage regulated value, wherein, Vd is d shaft voltage regulated value, k1 and k2 is regulable control coefficient respectively, and Udref is d axle reference voltage, and Ud is d axle virtual voltage; And
Q shaft voltage regulates submodule 503B: for according to formula: Vq=k3 (Udref-Uq)+k4 ∫ (Uqref-Uq) dt, calculate q shaft voltage regulated value, wherein, Vq is q shaft voltage regulated value, k3 and k4 is regulable control coefficient respectively, Uqref is q axle reference voltage respectively, and Uq is q axle virtual voltage.
First adjustment module 504, for carrying out Current adjustment to the current value of q axle and the current value of d axle respectively, obtains the first modulation voltage and the second modulation voltage;
Preferably, above-mentioned first adjustment module 504, comprising: q shaft current regulates submodule 504A and d shaft current to regulate submodule 504B, wherein,
Q shaft current regulates submodule 504A, for according to formula: V1=ω Li
q, carry out Current adjustment to the actual current value of q axle, calculate the first modulation voltage, wherein V1 is the first modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
qit is q axle actual current value;
D shaft current regulates submodule 504B, for according to formula: V2=ω Li
d, carry out Current adjustment to the actual current value of d axle, calculate the second modulation voltage, wherein V2 is the second modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
dit is d axle actual current value.
Second computing module 505, for calculating described d shaft voltage regulated value and the first regulation voltage and value, obtains d axle output voltage, calculates q shaft voltage regulated value and the second regulation voltage difference, obtains q axle output voltage;
Preferably, above-mentioned second computing module 505, comprising: d axle output voltage calculating sub module 505A and q axle output voltage calculating sub module 505B, wherein,
D axle output voltage calculating sub module 505A, for according to formula:
V1 (t)=k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt+ ω Li
q, calculate d axle output voltage, wherein, V1 (t) is d axle output voltage, and k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt is d shaft voltage regulated value, ω Li
qbe the first modulation voltage, k1 and k2 is regulable control coefficient respectively, Udref and Ud is reference voltage and the virtual voltage of d axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
qit is actual current q axle value;
Q axle output voltage calculating sub module 505B, for according to formula: V2 (t)=k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt-ω Li
d, calculate q axle output voltage, wherein, V2 (t) is q axle output voltage, and k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt is q shaft voltage regulated value, ω Li
dbe the second modulation voltage, k3 and k4 is regulable control coefficient respectively, Uqref and Uq is reference voltage and the virtual voltage of q axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
dit is the d axle value of actual current.
Delay disposal module 506, for calculating voltage and the value of d axle and q axle output voltage and each self-dalay T/4 respectively, obtains d axle control voltage and q axle control voltage respectively;
Preferably, above-mentioned delay disposal module 506, comprising: d axle postpones submodule 506A and q axle postpones submodule 506B,
D axle postpones submodule 506A, for according to formula: Vd (t)=V1 (t)+V1 (t-T/4), calculate described d axle output voltage and the voltage and the value that postpone T/4, obtain d axle control voltage, wherein, Vd (t) is d axle control voltage, and V1 (t) is d axle output voltage, and V1 (t-T/4) is the voltage postponing T/4;
Q axle postpones submodule 506B, for according to formula: Vq (t)=V2 (t)+V2 (t-T/4), calculate described q axle output voltage and the voltage and the value that postpone T/4, obtain q axle control voltage, wherein, Vq (t) is q axle control voltage, and V2 (t) is q axle output voltage, and V2 (t-T/4) is the voltage postponing T/4.
Second coordinate transferring 507, for carrying out Coordinate Conversion to d axle control voltage and q axle control voltage, obtains α axle control voltage and β axle control voltage;
Pulse signal generation module 508, carries out trigger impulse generating process to described α axle control voltage and β axle control voltage, obtains the pulse signal of control inverter.
Preferably, said apparatus, also comprise: trigger module 509, pulse signal for producing according to pulse signal generation module controls opening or turning off, producing the output voltage of described modular multilevel inverter AC of insulated gate bipolar transistor IGBT in each submodule of described modular multilevel inverter.
Above to control method and the device of a kind of voltage sag generator provided by the present invention, inverter, be described in detail, apply specific embodiment herein to set forth principle of the present invention and execution mode, the explanation of above embodiment just understands method of the present invention and core concept thereof for helping; Meanwhile, for one of ordinary skill in the art, according to thought of the present invention, all will change in specific embodiments and applications, in sum, this description should not be construed as limitation of the present invention.
Claims (12)
1. a control method for inverter, is characterized in that, controls the modular multilevel inverter in voltage sag generator, and this voltage sag generator comprises modular multilevel rectifier and modular multilevel inverter; Described modular multilevel rectifier is connected with connected mode of transmitting electricity back-to-back with described modular multilevel inverter, and described modular multilevel inverter is identical with the structure of described modular multilevel rectifier; Wherein, described modular multilevel rectifier comprises: the first brachium pontis connect with four bridge legs second-phase unit, the 5th brachium pontis of being formed of the first-phase unit, the 3rd brachium pontis that are formed of connecting with the second brachium pontis is connected with the 6th brachium pontis the third phase unit formed, three facies unit parallel connections; Six brachium pontis, in series by a N number of submodule SM and valve reactor, N be more than or equal to 1 natural number; Described SM comprises two IGBT derailing switches and a DC energy storage electric capacity, and with a DC energy storage Capacitance parallel connection after described two IGBT derailing switches series connection, described method comprises:
The three-phase actual current of detection module multi-electrical level inverter side ac bus, three-phase virtual voltage and three-phase reference voltage;
Described three-phase actual current, three-phase virtual voltage and three-phase reference voltage are carried out Coordinate Conversion respectively, obtains the d axle component of actual current and q axle component, the d axle component of virtual voltage and the d axle component of q axle component and reference voltage and q axle component;
Calculate the difference between the reference voltage of d axle and q axle component and virtual voltage respectively, and respectively voltage-regulation is carried out to described difference, obtain d shaft voltage regulated value and q shaft voltage regulated value;
Respectively Current adjustment is carried out to actual current q axle component and actual current d axle component, obtain the first modulation voltage and the second modulation voltage;
Calculate described d shaft voltage regulated value and the first modulation voltage and value, obtain d axle output voltage, calculate q shaft voltage regulated value and the second modulation voltage difference, obtain q axle output voltage;
Calculate voltage and the value of d axle and q axle output voltage and each self-dalay T/4 respectively, obtain d axle control voltage and q axle control voltage respectively, the angular frequency of T to be 2 π/w, w be predetermined current;
Coordinate Conversion is carried out to d axle control voltage and q axle control voltage, obtains α axle control voltage and β axle control voltage;
Trigger impulse generating process is carried out to described α axle control voltage and β axle control voltage, obtains the pulse signal controlling described modular multilevel inverter.
2. method according to claim 1, it is characterized in that, the described difference calculated respectively between the reference voltage of d axle and q axle component and virtual voltage, and respectively voltage-regulation control is carried out to described difference, obtain d shaft voltage regulated value and q shaft voltage regulated value, comprising:
By PI proportional integral conditioning controller, according to formula:
Vd=k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt, calculate d shaft voltage regulated value, wherein, Vd is d shaft voltage regulated value, k1 and k2 is regulable control coefficient respectively, and Udref is d axle reference voltage, and Ud is d axle virtual voltage; And
According to formula: Vq=k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt, calculate q shaft voltage regulated value, wherein, Vq is q shaft voltage regulated value, k3 and k4 is regulable control coefficient respectively, and Uqref is q axle reference voltage respectively, and Uq is q axle virtual voltage.
3. method according to claim 1, is characterized in that, describedly carries out Current adjustment to the actual current value of q axle and the actual current value of d axle respectively, obtains the first modulation voltage and the second modulation voltage, comprising:
According to formula: V1=ω Li
q, carry out Current adjustment to the actual current value of q axle, calculate the first modulation voltage, wherein V1 is the first modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
qit is q axle actual current value;
According to formula: V2=ω Li
d, carry out Current adjustment to the actual current value of d axle, calculate the second modulation voltage, wherein V2 is the second modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
dit is d axle actual current value.
4. method according to claim 1, is characterized in that, described calculating described d shaft voltage regulated value and the first modulation voltage and value, obtain d axle output voltage, calculate q shaft voltage regulated value and the second modulation voltage difference, obtain q axle output voltage, comprising:
According to formula: V1 (t)=k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt+ ω Li
q, calculate d axle output voltage, wherein, V1 (t) is d axle output voltage, and k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt is d shaft voltage regulated value, ω Li
qbe the first modulation voltage, k1 and k2 is regulable control coefficient respectively, Udref and Ud is reference voltage and the virtual voltage of d axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
qit is actual current q axle value;
According to formula: V2 (t)=k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt-ω Li
d, calculate q axle output voltage, wherein, V2 (t) is q axle output voltage, and k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt is q shaft voltage regulated value, ω Li
dbe the second modulation voltage, k3 and k4 is regulable control coefficient respectively, Uqref and Uq is reference voltage and the virtual voltage of q axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
dit is the d axle value of actual current.
5. method according to claim 1, is characterized in that, described voltage and the value calculating d axle and q axle output voltage and each self-dalay T/4 respectively, obtains d axle control voltage and q axle control voltage respectively, comprising:
According to formula: Vd (t)=V1 (t)+V1 (t-T/4), calculate described d axle output voltage and the voltage and the value that postpone T/4, obtain d axle control voltage, wherein, Vd (t) is d axle control voltage, V1 (t) is d axle output voltage, and V1 (t-T/4) is the voltage postponing T/4;
According to formula: Vq (t)=V2 (t)+V2 (t-T/4), calculate described q axle output voltage and the voltage and the value that postpone T/4, obtain q axle control voltage, wherein, Vq (t) is q axle control voltage, V2 (t) is q axle output voltage, and V2 (t-T/4) is the voltage postponing T/4.
6. method according to claim 1, is characterized in that, also comprises:
With the pulse signal of the described modular multilevel inverter of the control obtained, control opening or turning off of insulated gate bipolar transistor IGBT in each submodule of described modular multilevel inverter SM, produce the output voltage of described modular multilevel inverter AC.
7. a control device for inverter, is characterized in that, controls, comprising the modular multilevel inverter in voltage sag generator:
Detection module, for detecting the three-phase actual current of multi-electrical level inverter side ac bus, three-phase virtual voltage and three-phase with reference to phase voltage;
First coordinate transferring, for the three-phase actual current to detection, three-phase virtual voltage and three-phase with reference to phase voltage, carry out Coordinate Conversion respectively, obtain the d axle component of actual current and q axle component, the d axle component of virtual voltage and the d axle component of q axle component and reference voltage and q axle component;
First computing module, for calculating the difference between the reference voltage of d axle and q axle component and virtual voltage respectively, and carries out voltage-regulation control respectively to described difference, obtains d shaft voltage regulated value and q shaft voltage regulated value;
First adjustment module, for carrying out Current adjustment to the current value of q axle and the current value of d axle respectively, obtains the first modulation voltage and the second modulation voltage;
Second computing module, for calculating described d shaft voltage regulated value and the first regulation voltage and value, obtains d axle output voltage, calculates q shaft voltage regulated value and the second regulation voltage difference, obtains q axle output voltage;
Delay disposal module, for calculating voltage and the value of d axle and q axle output voltage and each self-dalay T/4 respectively, obtains d axle control voltage and q axle control voltage respectively;
Second coordinate transferring, for carrying out Coordinate Conversion to d axle control voltage and q axle control voltage, obtains α axle control voltage and β axle control voltage;
Pulse signal generation module, carries out trigger impulse generating process to described α axle control voltage and β axle control voltage, obtains the pulse signal of control inverter.
8. device according to claim 7, is characterized in that, described first computing module, comprising:
D shaft voltage regulates submodule, for passing through PI proportional integral conditioning controller, according to formula: Vd=k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt calculates d shaft voltage regulated value, wherein, Vd is d shaft voltage regulated value, k1 and k2 is regulable control coefficient respectively, and Udref is d axle reference voltage, and Ud is d axle virtual voltage;
Q shaft voltage regulates submodule, for according to formula: Vq=k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt, calculate q shaft voltage regulated value, wherein, Vq is q shaft voltage regulated value, k3 and k4 is regulable control coefficient respectively, and Uqref is q axle reference voltage respectively, and Uq is q axle virtual voltage.
9. device according to claim 7, is characterized in that, described first adjustment module, comprising:
Q shaft current regulates submodule, for according to formula: V1=ω Li
q, carry out Current adjustment to the actual current value of q axle, calculate the first modulation voltage, wherein V1 is the first modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
qit is q axle actual current value;
D shaft current regulates submodule, for according to formula: V2=ω Li
d, carry out Current adjustment to the actual current value of d axle, calculate the second modulation voltage, wherein V2 is the second modulation voltage, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value in described modular multilevel inverter, i
dit is d axle actual current value.
10. device according to claim 7, is characterized in that, described second computing module, comprising:
D axle output voltage calculating sub module, for according to formula: V1 (t)=k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt+ ω Li
q, calculate d axle output voltage, wherein, V1 (t) is d axle output voltage, and k1 (Udref-Ud)+k2 ∫ (Udref-Ud) dt is d shaft voltage regulated value, ω Li
qbe the first modulation voltage, k1 and k2 is regulable control coefficient respectively, Udref and Ud is reference voltage and the virtual voltage of d axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
qit is actual current q axle value;
Q axle output voltage calculating sub module, for according to formula: V2 (t)=k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt-ω Li
d, calculate q axle output voltage, wherein, V2 (t) is q axle output voltage, and k3 (Uqref-Uq)+k4 ∫ (Uqref-Uq) dt is q shaft voltage regulated value, ω Li
dbe the second modulation voltage, k3 and k4 is regulable control coefficient respectively, Uqref and Uq is reference voltage and the virtual voltage of q axle respectively, and ω is default electric current angular frequency, and L is the half of single brachium pontis series reactance value, i
dit is the d axle value of actual current.
11. devices according to claim 7, is characterized in that, described delay disposal module, comprising:
D axle postpones submodule, for according to formula: Vd (t)=V1 (t)+V1 (t-T/4), calculate described d axle output voltage and the voltage and the value that postpone T/4, obtain d axle control voltage, wherein, Vd (t) is d axle control voltage, and V1 (t) is d axle output voltage, and V1 (t-T/4) is the voltage postponing T/4;
Q axle postpones submodule, for according to formula: Vq (t)=V2 (t)+V2 (t-T/4), calculate described q axle output voltage and the voltage and the value that postpone T/4, obtain q axle control voltage, wherein, Vq (t) is q axle control voltage, and V2 (t) is q axle output voltage, and V2 (t-T/4) is the voltage postponing T/4.
12. devices according to claim 7, is characterized in that, also comprise trigger impulse module,
Described trigger module, pulse signal for producing according to pulse signal generation module controls opening or turning off, producing the output voltage of described modular multilevel inverter AC of insulated gate bipolar transistor IGBT in each submodule of described modular multilevel inverter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201210444243.5A CN102904458B (en) | 2012-11-08 | 2012-11-08 | Control method and device for inverter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201210444243.5A CN102904458B (en) | 2012-11-08 | 2012-11-08 | Control method and device for inverter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN102904458A CN102904458A (en) | 2013-01-30 |
| CN102904458B true CN102904458B (en) | 2015-01-28 |
Family
ID=47576547
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201210444243.5A Active CN102904458B (en) | 2012-11-08 | 2012-11-08 | Control method and device for inverter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN102904458B (en) |
Families Citing this family (12)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103178546B (en) * | 2013-03-27 | 2014-12-03 | 许继电气股份有限公司 | Low voltage generator used for low voltage ride through testing and voltage control method of low voltage generator |
| CN103731059B (en) * | 2013-06-13 | 2016-04-06 | 华北电力大学 | A kind of two clamped sub-module structure circuit of modularization multi-level converter |
| CN104237838B (en) * | 2014-10-27 | 2017-10-10 | 宁波三星智能电气有限公司 | A kind of meter operating voltage falls automatically testing platform and Voltage Drop mode |
| CN105811751B (en) * | 2014-12-29 | 2018-08-14 | 国家电网公司 | A kind of unlock startup control method of flexible direct-current transmission converter |
| CN104793090A (en) * | 2015-05-11 | 2015-07-22 | 上海凌世电子有限公司 | Separate voltage drop simulator |
| CN104993711B (en) * | 2015-05-22 | 2018-01-30 | 国网河南省电力公司电力科学研究院 | A kind of voltage dip transient process analogue means and method |
| CN105226712B (en) * | 2015-10-19 | 2017-12-22 | 阳光电源股份有限公司 | A kind of control method and system for adjusting inversion system output voltage |
| CN105699809A (en) * | 2016-02-16 | 2016-06-22 | 烽火通信科技股份有限公司 | Direct current voltage drop generator |
| CN106712100A (en) * | 2017-03-02 | 2017-05-24 | 江苏大学 | Perturbation observation-based control method for virtual grid-connected synchronous inverter and control system |
| CN106998074B (en) * | 2017-03-15 | 2021-08-27 | 全球能源互联网研究院 | Control method and system for modular multi-level flexible direct current converter station |
| CN108152619B (en) * | 2017-12-16 | 2021-02-05 | 西安翌飞核能装备股份有限公司 | Power grid fault simulation device and control method thereof |
| CN110518624A (en) * | 2018-05-21 | 2019-11-29 | 南京理工大学 | A kind of low voltage traversing control method based on photovoltaic combining inverter |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101119074A (en) * | 2007-09-25 | 2008-02-06 | 中国科学院电工研究所 | Electric network electric voltage drop generator |
| CN101887074A (en) * | 2010-05-24 | 2010-11-17 | 华北电力大学（保定） | Three-phase voltage sag generator |
| CN202034907U (en) * | 2011-03-15 | 2011-11-09 | 荣信电力电子股份有限公司 | H bridge serial connection multilevel voltage sag generator based on IGBT |
| CN102761135A (en) * | 2012-07-19 | 2012-10-31 | 河海大学 | Low voltage ride through method for single-stage photovoltaic grid-connected inverter |
-
2012
- 2012-11-08 CN CN201210444243.5A patent/CN102904458B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101119074A (en) * | 2007-09-25 | 2008-02-06 | 中国科学院电工研究所 | Electric network electric voltage drop generator |
| CN101887074A (en) * | 2010-05-24 | 2010-11-17 | 华北电力大学（保定） | Three-phase voltage sag generator |
| CN202034907U (en) * | 2011-03-15 | 2011-11-09 | 荣信电力电子股份有限公司 | H bridge serial connection multilevel voltage sag generator based on IGBT |
| CN102761135A (en) * | 2012-07-19 | 2012-10-31 | 河海大学 | Low voltage ride through method for single-stage photovoltaic grid-connected inverter |
Non-Patent Citations (1)
| Title |
|---|
| Performance evaluation of half-bridge cascaded multilevel converters operated with multicarrier sinusoidal PWM techniques;Georgios S.Konstantinou et al.;《IEEE Industrial Electronics and Applications Conference》;20090527(第4期);第3399-3404页 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN102904458A (en) | 2013-01-30 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN102904458B (en) | Control method and device for inverter | |
| CN103078316B (en) | Network voltage disturbance generating device and control method thereof | |
| CN103197241B (en) | Flexible DC power transmission MMC converter valve operating test device and test method | |
| CN108280271B (en) | Unified power flow controller equivalent modeling method based on switching period average principle | |
| CN103117556B (en) | PCS electric voltage frequency control system and control method | |
| CN103427425B (en) | Coordinated control device and method for MMC (modular multilevel converter) type unified power quality conditioner | |
| CN101534015A (en) | Three-phase photovoltaic grid-connected inverting control method and device thereof | |
| CN101951178A (en) | Method used for balancing three phases of direct current side voltages of chain power regulating device | |
| CN103616584B (en) | The adjustment method of a kind of frequency converter test platform and frequency converter test platform | |
| CN106950512B (en) | Energy storage converter grid-connected and grid-disconnected characteristic integrated detection system and method | |
| CN102520218A (en) | Programmable trouble power simulator | |
| CN103825478A (en) | Control method of modular multilevel converter based on power frequency fixed switching frequency | |
| CN105226720A (en) | Magneto alternator networking side converter improves droop control method | |
| CN103986174A (en) | Energy storage converter parallel operation optimizing control method in three-phase imbalance system | |
| CN103954866A (en) | Testing circuit of half-bridge-structure voltage source current converter and modulation method thereof | |
| CN104065279A (en) | Voltage disturbance generation device and method for simulating power grid disturbance | |
| CN106787878A (en) | A kind of single-phase MMC loop current suppressions device and suppressing method based on virtual Circulation Components | |
| CN103366053B (en) | A kind of improvement of Voltage-oriented control strategy and Mathematical Modeling Methods | |
| Gangui et al. | Research on modular multilevel converter suitable for direct-drive wind power system | |
| Yuan et al. | Control scheme to improve DPFC performance during series converter failures | |
| CN109450316B (en) | Method and system for simplifying direct-drive fan based on PWM | |
| CN103606965A (en) | Networking control method of energy storage inverters based on quasi real-time synchronous signals | |
| CN109361235A (en) | The alternate Power balance control method of three-phase cascaded H-bridges photovoltaic DC-to-AC converter | |
| CN111952995B (en) | Direct-current capacitor voltage balance control method under single-phase fault of power grid | |
| CN203911496U (en) | Full energy feedback type power grid simulator |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant |