CN102540106B - DC (direct current) side EMI noise measuring device for new energy inversion system and measuring and calibrating method - Google Patents
DC (direct current) side EMI noise measuring device for new energy inversion system and measuring and calibrating method Download PDFInfo
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- CN102540106B CN102540106B CN201210020645.2A CN201210020645A CN102540106B CN 102540106 B CN102540106 B CN 102540106B CN 201210020645 A CN201210020645 A CN 201210020645A CN 102540106 B CN102540106 B CN 102540106B
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Abstract
The invention discloses a DC side EMI noise measuring device for a new energy inversion system and a measuring and calibrating method. The new energy inversion system includes a new energy module, an inversion control and power quality adjusting module, a load or a connected grid, wherein a DC-LISN is connected onto a conducting wire between the new energy module and the inversion control and power quality adjusting module, and then is connected with an EMI receiver. The method is based on the common formula for measuring the DC side conduction EMI internal impedance of the new energy inversion system through S parameters, adopts the S parameter method to model and measure the internal impedance at the new energy end, the DC-LISN end, and the inversion control and power quality adjusting end, provides sufficient theoretic reference for realizing the final measurement result compensation through combing the wave reflection theory to derive the direct current conduction EMI calibration compensation formula, and provides a reliable reference for the design of a DC side conduction EMI filter at the same time.
Description
Technical field
The invention belongs to technical field of electromagnetic compatibility, specifically a kind of new forms of energy inversion system DC conduction EMI noise measurement mechanism, and measure and compensation calibration method, the method adopts S parameter to analyze the internal impedance of new forms of energy end (DC power supply terminal), DC-LISN end, inversion control and quality of power supply adjustable side, have studied the metrophia compensation of DC conduction EMI based on reflection wave theory.
Background technology
Along with the increasing of environmental pollution and the day by day in short supply of traditional energy, improve energy structure and the renewable new forms of energy of development, the quality improving electric energy has become the strategic measure of China's energy development.In recent years along with the progress of Power Electronic Technique and the support of national policy, solar electrical energy generation is with the extensive concern of its aboundresources, advantage the causes people such as pollution-free, the construction period is short.Owing to employing a large amount of power electronic devices in solar grid-connected system, the emc issue of system is highlighted, become the focus of engineering and scientific research personnel's concern, the impact along with grid-connected system increases its compatibility and becomes more important.
The research that the research of traditional conducted EMI noise is mainly limited to inversion system AC noise, does not have the generation root that deep structure research Conducted EMI is possible.Inversion system often comprises direct current buck link, although DC link is different to exchange and controls and quality of power supply governing loop, but the Conducted EMI of high frequency is present among the circuit of DC link equally, how to measure the Conducted EMI of DC link efficiently and accurately, have very important vital role for the impact eliminating Conducted EMI direct or potential.
Summary of the invention
Technical matters to be solved by this invention is to provide a kind of new forms of energy inversion system DC side conducted EMI noise measurement mechanism and measurement, calibration steps, the impedance information that this device and method is measured for S parameter, in conjunction with reflection wave theory, calculate the size recording EMI wave reflection, finally realize the metrophia compensation of DC conduction EMI.
A kind of new forms of energy inversion system DC side conducted EMI noise measurement mechanism of the present invention, this new forms of energy inversion system comprises new forms of energy module, inversion control and quality of power supply adjustment module and load or grid-connected, new forms of energy module provides direct supply and outputs to inversion control and quality of power supply adjustment module, obtain alternating voltage by inversion control and quality of power supply adjustment module and resupply load or grid-connected, DC-LISN is connected with on the wire between inversion control and quality of power supply adjustment module in new forms of energy module, DC-LISN is connected with EMI receiver or vector network analyzer again.
Present invention also offers a kind of new forms of energy inversion system DC side conducted EMI noise to measure and calibration steps, it comprises the following steps:
1) on above-mentioned measurement mechanism basis, the internal impedance of DC-LISN, new forms of energy module, inversion control and quality of power supply adjustment module is first tried to achieve based on S parameter measurement, if the impedance of new forms of energy module is Z
x1, DC-LISN internal impedance is Z
x2, inversion control and quality of power supply adjustment module internal impedance be Z
x3;
2) carry out compensation for calibrating errors in conjunction with reflection wave theory, the new forms of energy module impedance according to recording is Z
x1, DC-LISN internal impedance is Z
x2, inversion control and quality of power supply adjustment module internal impedance be Z
x3, obtain voltage reflection coefficient
;
（3-1）
According to the reflection coefficient that formula (3-1) is tried to achieve, then try to achieve:
Virtual voltage V
n=V
+ n/
, reflected voltage V
- nF=
* V
n,
Wherein, V
+ nfor the magnitude of voltage of EMI receiver actual measurement, V
+ nFreflected voltage, is also the voltage needing to compensate, V
nfor in esse Conducted EMI voltage.
Above-mentioned steps 1) the measuring and calculating process of each module impedance is:
Use two current probes, one is connected to the output terminal of vector network analyzer as injection probe; Another is connected to the input end of vector network analyzer as detection probe, and two probes access DC-LISN to be measured, new forms of energy module, inversion control and quality of power supply adjustment module respectively through coupling capacitance C, record the noise source internal impedance Z of each module
x, being the impedance of new forms of energy module is Z
x1, DC-LISN internal impedance is Z
x2, inversion control and quality of power supply adjustment module internal impedance be Z
x3;
Internal impedance measure equation based on scattering parameter method is:
（3-16）
In formula
for the internal impedance in loop,
for the coefficient of measuring circuit,
s 11for input reflection coefficient,
s 21for forward transmission coefficient.
Use short-circuit conductors and measuring resistance respectively
r standardreplace
z xcan obtain
（3-17）
（3-18）
Simultaneous above formula can be calculated k with
z setup, therefore measure noise source to be measured
z xscattering parameter, noise source internal impedance can be calculated
z x
（3-19）
In above-mentioned formula,
for the internal impedance in loop,
for the coefficient of measuring circuit,
s 11for input reflection coefficient,
s 21for forward transmission coefficient.
Above-mentioned steps 2) when consideration 2 secondary reflection coefficient time, known input voltage is reflected voltage V
- nF, can try to achieve 2 secondary reflection coefficients is:
（3-3）
In formula,
for voltage reflection coefficient, Z
x2for DC-LISN internal impedance, Z
x3for new forms of energy module internal impedance, known V
+ nfor the magnitude of voltage of EMI receiver actual measurement, V
+ nFreflected voltage, V
nfor in esse Conducted EMI voltage; There is formula:
（3-4）
Then according to the reflection coefficient that formula (3-3) is tried to achieve, try to achieve virtual voltage V
2 n=V
2+ n/
, reflected voltage V
2- nF=
* V
2 n, in formula, V
2 n=V
- nF.The terminal voltage Vr of known final EMI receiver is: Vr=V
+ n+ V
2- nF=V
n* (1-
)+V
n*
*
, can voltage transmission coefficient be obtained
:
（3-5）
Rectification building-out voltage is:
(3-6)
In like manner for the measurement of electric current, current transmission coefficient can be obtained
:
（3-7）
Rectification building-out electric current is:
(3-8)
The present invention, from the schematic diagram of new forms of energy inversion system, analyzes the root that new forms of energy inversion system DC side conducted EMI noise produces.Define DC side Conducted EMI, analyze the insertion loss characteristic of DC-LISN, obtain corresponding measure equation.Derive and measured the general formulae of new forms of energy inversion systems DC side Conducted EMI internal impedance based on S parameter, adopted the internal impedance modeling of S parameter method to new forms of energy end (DC power supply terminal), DC-LISN end, inversion control and quality of power supply adjustable side to measure.In conjunction with reflection wave theory, DC conduction EMI compensation for calibrating errors formula of having derived, has put forward sufficient confession theoretical foundation for finally realizing measurement result compensation.Simultaneously for the design of DC side Conducted EMI wave filter provides reliable reference.
Accompanying drawing explanation
Fig. 1 new energy resources system Conducted EMI test philosophy figure;
Fig. 2 DC side Conducted EMI defines;
Fig. 3 two-port network S parameter schematic diagram;
Fig. 4 is based on the internal impedance measuring principle figure of S parameter;
Fig. 5 is based on the noise source internal impedance modelled equivalent circuit diagram of S parameter method;
The Ideal Transmission Line analytical model of Fig. 6 signal reflex;
Fig. 7 filter insertion loss figure, wherein Fig. 7 is a) before wave filter access, Fig. 7 b) be after wave filter access;
Fig. 8 holds internal impedance to measure based on the DC-LISN of S parameter;
Fig. 9 measures based on the new forms of energy end internal impedance of S parameter;
Figure 10 measures based on the inversion control of S parameter and quality of power supply adjustable side internal impedance;
Figure 11 reflection parameters model;
Figure 12 secondary reflection parameter model.
Embodiment
the brief introduction of new forms of energy inversion system DC side Conducted EMI test macro
New forms of energy inversion system and DC side Conducted EMI test macro comprise several main part: new forms of energy module (wind energy, sun power, fuel cell etc.), inversion control and quality of power supply adjustment module, load (grid-connected), DC-LISN and EMI receiver.
System provides direct supply by new forms of energy module, outputs to inversion control and quality of power supply adjustment module, finally obtains alternating voltage supply load or grid-connected.Conducted EMI is present in the modules of system, in order to researching DC side Conducted EMI is on the impact of system, have selected the measuring element of DC-LISN as DC conduction EMI.Source due to DC conduction EMI may be inversion control side, also may be new forms of energy module side.To measure respectively the noise of different port when our actual measurement.If Fig. 1, DC-LISN are single wire input/output, when measurement, (turning the line of DC-LISN when measurement) measurement to A, B side Conducted EMI when DC-LSIN is connected on A, B port time, can be realized respectively.When DC-LSIN is connected on C, D port time, (turning the line of DC-LISN when measurement) measurement to C, D side Conducted EMI can be realized respectively.Have employed two EMI receivers inside the measuring principle figure of Fig. 1, in actual measurement, only an EMI receiver need be used just to measure the Conducted EMI of DC side two wires.
new forms of energy inversion test macro and DC side Conducted EMI side noise reason and impact analysis
The conducted EMI noise of DC side has two sources, and one comes from new forms of energy module side, and another comes from inversion control and quality of power supply adjustment module side.New forms of energy module side, owing to there is the effect of motor, switching device etc., can produce the Conducted EMI of high frequency, and because the power port exported does not load effective filtering measures, Conducted EMI enters DC side easily via power supply short-term.Inversion control and quality of power supply adjustment module side are the major source that Conducted EMI produces, and because inverter side exists a large amount of switching device, simultaneously due to problems such as control strategies, may produce the conducted EMI noise of different frequency range, be transferred to DC side.Traditional electromagnetic compatibility research often ignores the impact of high frequency noise in DC side, as long as think that the final output terminal of inversion can load the impact that filtering measures just finally can eliminate Conducted EMI.But, facts have proved, as long as Conducted EMI exists, side device will be regulated to produce direct or potential impact on new forms of energy module side and inverter control and the quality of power supply.
In the DC side of inversion system owing to only there are two wires, there is no so-called ground wire, so only there is a kind of noise of situation.For the Conducted EMI between two lines, we can do a simply definition, as shown in Figure 2.Two lines are defined: L, N at new forms of energy module side and inverter control and quality of power supply adjustment module side.We suppose the transmission path of Conducted EMI as shown in FIG., then the Conducted EMI on L line is defined as L line Conducted EMI, and the Conducted EMI on N line is defined as the Conducted EMI of N line.
the definition of parameter and test philosophy
the ultimate principle of 3.1 S parameter
S parameter (scattering parameter) is a kind of radio frequency vector parameters, comprises amplitude and phase information simultaneously, can more comprehensively describe network port characteristic.Relation between S parameter reflection port incident wave and reflection wave.
For Two-port netwerk, tell about ultimate principle.The parameter of normal Two-port netwerk as shown in Figure 3.S parameter is for representing the relation between incident wave a and reflection wave b, and any network all can characterize its port identity by multiple S parameter.N-terminal-pair network needs n
2individual S parameter, wherein, represents the S parameter S of certain Single port themselves incident ripple and reflection wave relation
iibe called reflection coefficient, the incident wave between expression different port and the S parameter S of reflection wave relation
ijbe called transmission coefficient.For the physical significance of two-port network S parameter, shown in (3-1), the scattering parameter of this two-port network comprises reflection coefficient S
11and S
22, and transmission coefficient S
12and S
21, the scattering parameter equation of this network can be expressed as:
（3-1）
In formula, the physical significance of S parameter is respectively:
: when representing port 2 impedance matching, the reflection coefficient of port one;
: when representing port one impedance matching, the reflection coefficient of port 2;
: when representing port 2 impedance matching, by the transmission coefficient of port one to port 2;
: when representing port one impedance matching, by the transmission coefficient of port 2 to port one.
For multiport network, if port number is n, incident wave and the reflection wave of each port are respectively a
nand b
n, its scattering parameter matrix equation can be expressed as:
（3-2）
The scattering parameter of multiport network has following character:
(1) S when network is symmetrical
ii=S
jj;
(2) S during network reciprocity
ij=S
ji.
(3) matched load is used for absorbed power, during port i use matched load, and this port no reflection events.
based on the realization that the internal impedance of S parameter is measured
Scattering parameter method is utilization two current probes, and one is connected to the output terminal of vector network analyzer as injection probe; Another is connected to the input end of vector network analyzer as detection probe, and as shown in Figure 4, wherein C is coupling capacitance, Z
xfor noise source internal impedance.
Current probe is equivalent to current transformer, can be therefore Fig. 5, wherein L, L by Fig. 4 circuit equivalent
1, L
2be respectively circuit equivalent self-induction, injection probe self-induction, detection probe self-induction; M
1, M
2be respectively injection/equivalent mutual inductance between detection probe and circuit; V
1, V
2be respectively the output signal of vector network analyzer and the Received signal strength of vector network analyzer.Can obtain according to Kirchhoff's second law
（3-3）
（3-4）
（3-5）
Cancellation
i 1,
i 2after can obtain
（3-6）
In order to simplified operation, be defined as follows:
（3-7）
Then formula (3-6) can be written as
（3-8）
Order
can obtain
（3-9）
Electric current
ican be recorded by measurement current probe, can obtain according to current probe use principle
（3-10）
In formula,
u p2for vowing the voltage signal that net instrument input end records,
z t2 for measuring the transport property impedance of current probe.
On the other hand, due to
（3-11）
Can obtain
（3-12）
Can obtain according to scattering parameter analytical approach
s 11for input reflection coefficient,
s 12for reverse transfer coefficient,
s 21for forward transmission coefficient,
s 22for output reflection coefficient, with wave parameter, there is following relation:
（3-13）
Have again
（3-14）
For the input end of vowing net instrument and output terminal, characteristic impedance is equal and be
, i.e. Z
c1=Z
c2=
, therefore have
（3-15）
Formula (3-12) can be written as
（3-16）
Use short-circuit conductors and measuring resistance respectively
r standardreplace
z xcan obtain
（3-17）
（3-18）
Simultaneous above formula can be calculated k with
z setup, therefore measure noise source to be measured
z xscattering parameter, can noise source be calculated
z x
（3-19）
In measuring process, reflection parameters and transformation parameter all comprise phase information, and therefore noise source internal impedance also comprises amplitude and phase information, thus avoid phase place disappearance, and effectively solve the resistance matching problem between noise source and electromagnetic interface filter.Relative to the noise source internal impedance modeling method based on double-current probe method, this method does not need to consider measuring resistance
approximate condition, improve measuring accuracy.
reflection wave theory
In signal transmits on high-speed digital circuit, when impedance discontinuity on transmission line, at this moment transmission line there will be the situation of signal reflex.Circuit diagram as shown in Figure 6.Suppose that transmission line L is driven by the digital signal drive source Vs that internal impedance is R0, the characteristic impedance of transmission line is Z0, and loaded impedance is
r l.Three kinds of situation discussion can be divided:
1) ideally R0=Z0=is worked as
r ltime, the impedance of transmission line is continuous print, and any reflection can not occur, and energy has half consumption in load internal resistance
r lon, load absorbs the energy of arrival completely, returns source without any signal reflex, and this situation is called critical damping.
2) if loaded impedance is greater than the characteristic impedance of transmission line, the energy that so load end is unnecessary will be reflected back source, because load end does not absorb whole energy, therefore claims this situation to be underdamping.
3) if loaded impedance is less than the characteristic impedance of transmission line, so load is wanted to consume the more energy of the energy provided than current source, and therefore notify that source carries more energy by reflection, this situation is called overdamping.
For underdamping and overdamping, they can cause reciprocal propagation waveform, in some cases transmission line can form standing wave.Critical damping is a kind of state can avoiding reflecting completely.But critical damping situation is difficult to realize, and will adopt slight overdamping mode in general reality.
Load end impedance is not mated can return source (A point) at load end (B) antireflection part signal in transmission line impedance, and reflected voltage signal amplitude is by load reflection coefficient
determine, namely
（4-1）
In formula (4-1),
lfor load voltage reflection coefficient, be actually the ratio of reflected voltage and incident voltage;
r lloaded impedance; Z
0for the characteristic impedance of transmission line.
Known by formula above ,-1
l + 1, and work as
r l=Z
0time,
l=0, at this moment can not there is reflex.Visible, as long as carry out terminal coupling according to the characteristic impedance of transmission line, just can reflection be eliminated.
When the voltage be reflected back from load end arrives source, again will be reflected back load end again, form secondary counter ejected wave, the amplitude of reflected voltage is at this moment by source reflection coefficient
sdetermine, namely
（4-2）
Signal after secondary reflection, acts on very faint.Can no longer do deep consideration.
The present invention is directed to during DC conduction EMI noise is measured the signal reflection problem that may exist, adopt S parameter method, full frequency band measurement noises source internal impedance, experimental configuration is relatively simple, and reliability is high.In conjunction with the wave impedance recorded, reflection wave theory is adopted to compensate calculating.Compensated by corresponding theory calculate, make the result of test more close to actual value, also for squelch provides impedance information the most accurately.
Embodiment
1. based on the insert loss of the DC-LISN of A parameter
Electromagnetic interface filter is to the rejection ability insertion loss IL(Insertion Loss of interference noise) weigh.Insertion loss is defined as: when not having wave filter to access, and after the power P 1 being transferred to load from noise source and access wave filter, noise source is transferred to the ratio of the power P 2 of load, with dB(decibel) represent.Circuit before and after wave filter access as shown in Figure 7.
(1-1)
(1-2)
(1-3)
So
(1-4)
Can be obtained by Fig. 7 (a)
(1-5)
The Internet Transmission equation of Fig. 7 (b) is
(1-6)
(1-7)
Simultaneously
(1-8)
(1-9)
Formula (1-6) ~ (1-9) simultaneous can solve V
2for
(1-10)
Then (1-10), (1-5) are updated in (1-4), try to achieve
(1-11)
For Fig. 7 (b), we adopt A Parametric Representation FL-network, and A parameter matrix is
2. the DC-LISN based on S parameter holds, the internal impedance of new forms of energy (DC power supply terminal), inversion control and quality of power supply adjustable side is measured.
2.1 measure based on the internal impedance of the DC-LISN of S parameter
In the technical scheme of the invention, draw the formula (see formula (3-16)) based on S parameter measurement impedance, in formula, had COEFFICIENT K and source internal impedance Z
setuptwo unknown numbers, so in order to measure unknown impedance, also need twice measurement (see formula (3-17), formula (3-18)) carrying out short circuit and adjunction normal impedance.
（2-1）
Z in formula
xfor impedance to be asked, K is related coefficient, Z
setupsource internal impedance, S
3 21, S
3 11for the S parameter that frequency spectrograph is measured
（2-2）
In formula, K is related coefficient, Z
setupsource internal impedance, S
1 21, S
1 11for the S parameter that frequency spectrograph is measured
（2-3）
R in formula
standardfor normal impedance, K is related coefficient, Z
setupsource internal impedance, S
2 21, S
2 11for the S parameter that frequency spectrograph is measured
The computing of through type (2-2), formula (2-3) can solve COEFFICIENT K and source impedance Z
setuptwo unknown numbers.Then substitute in formula (2-1), the impedance Z of getting required by just obtaining
x.Test is arranged as shown in Figure 8, and acquired results is the internal impedance of DC-LISN.
2.2 measure based on new forms of energy (DC power supply terminal) internal impedance of S parameter
The internal impedance of DC power supply terminal is asked for identical with DC-LISN principle, through type (2-1), (2-2), formula can obtain new forms of energy end internal impedance in (2-3), test is arranged as shown in Figure 9.
2.3 measure based on the inversion control of S parameter and quality of power supply adjustable side internal impedance
The internal impedance of inversion control and quality of power supply adjustable side is asked for identical with DC-LISN principle, and in through type (2-1), (2-2), (2-3), formula can obtain inversion control and quality of power supply adjustable side internal impedance, and test is arranged as shown in Figure 10.
3. the compensation for calibrating errors of wave reflection
By 2.1,2.2,2.3 solve.We obtain new forms of energy (DC power supply terminal), DC-LISN end, inversion control and the impedance of three, quality of power supply adjustable side, if new forms of energy (DC power supply terminal) impedance is Z
x1, DC-LISN internal impedance is Z
x2, inversion control and quality of power supply adjustable side internal impedance be Z
x3.In conjunction with the reflection wave theory inside summary of the invention, we know.Conducted EMI is when DC terminal is transmitted.Certainly exist wave reflection, when we adjunction DC-LISN carries out Conducted EMI measurement time, owing to not considering wave reflection, may there is deviation in actual measurement, in order to obtain Conducted EMI information the most accurately, we can carry out compensation for calibrating errors in conjunction with reflection wave theory.As Figure 11, when we overlap the Conducted EMI of good preparation measurement inversion control and quality of power supply adjustable side.Consider that there is V inversion control and quality of power supply adjustable side
nconducted EMI when outputting to DC-LISN end, due to not mating of impedance, there is wave reflection, in conjunction with our DC-LISN end of side, inversion control and the impedance of quality of power supply adjustable side, can voltage reflection coefficient be obtained.
（3-1）
In formula,
for voltage reflection coefficient, Z
x2for DC-LISN holds internal impedance, Z
x3for new forms of energy end (DC power supply terminal) internal impedance.According to test connection Figure 11, known V
+ nfor the magnitude of voltage of EMI receiver actual measurement, V
+ nFreflected voltage, V
nfor in esse Conducted EMI voltage, there is formula:
（3-2）
According to the reflection coefficient that formula (3-1) is tried to achieve, can in the hope of virtual voltage V
n=V
+ n/
, reflected voltage V
- nF=
* V
n, so, when measurement, V
- nFbe the voltage needing to compensate, the measured value of EMI receiver can be converted into by corresponding conversion.
Fig. 7, when consideration 2 secondary reflection coefficient time, known input voltage is reflected voltage V
- nF, can try to achieve 2 secondary reflection coefficients is:
（3-3）
In formula,
for voltage reflection coefficient, Z
x2for DC-LISN holds internal impedance, Z
x3for new forms of energy end (DC power supply terminal) internal impedance.According to test connection Figure 12, known V
+ nfor the magnitude of voltage of EMI receiver actual measurement, V
+ nFreflected voltage, V
nfor in esse Conducted EMI voltage.There is formula:
（3-4）
Then according to the reflection coefficient that formula (3-3) is tried to achieve, can in the hope of virtual voltage V
2 n=V
2+ n/
, reflected voltage V
2- nF=
* V
2 n, in formula, V
2 n=V
- nF.The terminal voltage (being set to Vr) of known final EMI receiver is: Vr=V
+ n+ V
2- nF=V
n* (1-
)+V
n*
*
, voltage transmission coefficient can be obtained and (be set to
):
（3-5）
Rectification building-out voltage is:
(3-6)
In like manner for the measurement of electric current, current transmission coefficient can be obtained and (be set to
):
（3-7）
Rectification building-out electric current is:
(3-8)
The above is only the preferred embodiment of the present invention, it should be pointed out that for those skilled in the art, under the premise without departing from the principles of the invention, can also make some improvement, and these improvement also should be considered as protection scope of the present invention.
Claims (1)
1. a new forms of energy inversion system DC side conducted EMI noise is measured and calibration steps, described new forms of energy inversion system comprises new forms of energy module, inversion control and quality of power supply adjustment module and load or grid-connected, new forms of energy module provides direct supply and outputs to inversion control and quality of power supply adjustment module, obtain alternating voltage by inversion control and quality of power supply adjustment module and resupply load or grid-connected, DC-LISN is connected with on the wire between inversion control and quality of power supply adjustment module in new forms of energy module, DC-LISN is connected with vector network analyzer or EMI receiver again,
It is characterized in that, the method comprises following step:
1) internal impedance of DC-LISN, new forms of energy module, inversion control and quality of power supply adjustment module is first tried to achieve based on multiport circuit, if new forms of energy module internal impedance is Z
x1, DC-LISN internal impedance is Z
x2, inversion control and quality of power supply adjustment module internal impedance be Z
x3;
The measuring and calculating process of each module internal impedance is:
Use two current probes, one is connected to the output terminal of vector network analyzer as injection probe; Another is connected to the input end of vector network analyzer as detection probe, and two probes access DC-LISN to be measured, new forms of energy module, inversion control and quality of power supply adjustment module respectively through coupling capacitance C, record the noise source internal impedance Z of each module
x, being new forms of energy module internal impedance is Z
x1, DC-LISN internal impedance is Z
x2, inversion control and quality of power supply adjustment module internal impedance be Z
x3; Internal impedance measure equation based on scattering parameter method is:
Z in formula
setup=Z
m1+ Z
m2+ Z
mfor the internal impedance in loop, k=(-j ω MZ
t2/ (Z
sig+ jwL
p)) be the coefficient of measuring circuit, S
11for input reflection coefficient, S
21for forward transmission coefficient;
Use short-circuit conductors and measuring resistance R respectively
standardreplace Z
xcan obtain
Simultaneous above formula can be calculated k and Z
setup, therefore measure noise source Z to be measured
xscattering parameter, noise source internal impedance Z can be calculated according to formula (3-16)
x;
2) carry out compensation for calibrating errors in conjunction with reflection wave theory, the new forms of energy module internal impedance according to recording is Z
x1, DC-LISN internal impedance is Z
x2, inversion control and quality of power supply adjustment module internal impedance be Z
x3, obtain voltage reflection coefficient;
ρ in formula
vfor voltage reflection coefficient;
According to the voltage reflection coefficient that formula (3-1) is tried to achieve, then try to achieve:
Virtual voltage V
n=V
+ n/ ρ
v, reflected voltage V
- nF=ρ
v* V
n,
Wherein, V
+ nfor the magnitude of voltage of EMI receiver actual measurement, V
- nFfor reflected voltage, be also the voltage needing to compensate, V
nfor in esse Conducted EMI voltage.
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