CN102082547A - Power conversion device - Google Patents
Power conversion device Download PDFInfo
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- CN102082547A CN102082547A CN2010102640752A CN201010264075A CN102082547A CN 102082547 A CN102082547 A CN 102082547A CN 2010102640752 A CN2010102640752 A CN 2010102640752A CN 201010264075 A CN201010264075 A CN 201010264075A CN 102082547 A CN102082547 A CN 102082547A
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Abstract
The invention provides a power conversion device, wherein the peak value of the common mode current is reduced when a PWM rectifier (3) and an inverter (4) is controlled in a two-phase modulation mode.According to the PWM rectifier (3) and the inverter (4) driven in a two-phase modulation mode, the carrier of each triangular wave is synchronized and the phase difference thereof becomes zero.When the switch and the timing of the voltage mode of each two-phase modulation mode is focused on, the switch of the voltage mode of the PWM rectifier (3) and the inverter (4) successively occurs in a short time.The switch and the timing of the voltage mode is corrected by prolonging the time period of one of the PWM rectifier (3) and the inverter (4), so that the switch of the voltage mode of the PWM rectifier (3) and the inverter (4) is prevented from successively occuring in a short time.
Description
Technical field
The present invention relates to a kind of power-converting device (Electricity force conversion system), the reduction method of the common mode current when especially relating to a kind of PWM rectifier and inverter and all adopting the bi-phase modulated mode to control.
Background technology
Control mode as the inverter of power-converting device generally adopts the three-phase modulations mode, but in order to reduce the switch number of times of each switch element, to reduce switching loss, also adopts the bi-phase modulated mode sometimes.
For example, the scheme of bi-phase modulated mode as the PWM control method of three-phase voltage-type inverter that adopt disclosed in patent documentation 1.In addition, in patent documentation 2 disclosed compressor control methods, compressing apparatus of refrigerant and aircondition and control method thereof, put down in writing the method that a kind of PWM rectifier and inverter all adopt the bi-phase modulated mode to control, and put down in writing at inverter side and increase the iron loss of motor to be used for the overheated mode of cold-producing medium.
In addition, in patent documentation 3 disclosed power-converting devices, though not to having adopted the bi-phase modulated mode or having adopted the three-phase modulations mode to make an explanation, it has put down in writing the method that reduces Zero-phase current (common mode current) by the triangular wave carrier signal Synchronization that makes PWM rectifier and inverter.Wherein, so-called common mode current is meant the electric current that flows by ground connection.
Have again, the control method of a kind of pair of converter converting means is disclosed in patent documentation 4, this method is not the method at common mode current, it makes it possible to use withstand voltage low components and parts in order to reduce surge voltage, make the regularly later instruction delay regular hour, avoid connection (ON)/disconnection (OFF) instruction of switch in PWM rectifier and inverter in official hour, to take place simultaneously with this.
Patent documentation 1: the flat 1-274669 communique of Japan's open patent
Patent documentation 2: the open patent 2006-38432 of Japan communique
Patent documentation 3: the open patent 2004-80855 of Japan communique
Patent documentation 4: the open patent 2009-60708 of Japan communique
In the bi-phase modulated mode of patent documentation 1, when carrying out the switching of voltage mode, voltage between lines can not change, but has bigger voltage to overlap on the phase voltage of each phase as the component of voltage of zero phase.Therefore, especially when carrying out the switching of voltage mode, can produce bigger common mode current, thereby cause high-frequency noise to take place.
In addition, shown in patent documentation 2, when all adopting the bi-phase modulated mode in PWM rectifier and inverter, zero phase voltage takes place respectively independently, and these zero phase voltages that take place independently are overlapping and in the inflow common-mode circuit (circuit that comprises earth connection).For this reason, under certain timing, following situation may occur: voltage mode switches simultaneously in PWM rectifier and these two devices of inverter, and the common mode current that takes place respectively in these two devices overlaps, thereby produces the big common mode current of peak value.When the big common mode current of above-mentioned peak value has taken place after, this common mode current flow in the equipment of periphery by earth connection, so, existence for example can cause residual current circuit breaker misoperation to occur or make playback equipment produce noise etc., thereby brings the problem of adverse effect to peripheral equipment.
In the converting means that adopts patent documentation 1 or patent documentation 2 disclosed bi-phase modulated modes, common mode current is not made consideration, and the solution of this common mode current is not made an explanation yet.
The patent documentation 3 disclosed synchronous methods of triangular wave carrier that make PWM rectifier and inverter are very effective to reducing common mode current in the three-phase modulations mode.In the bi-phase modulated mode, synchronous by the triangular wave carrier that makes PWM rectifier and inverter, have the effect that can reduce common mode current to a certain extent.But in the bi-phase modulated mode, the switching of voltage mode can cause common mode current to take place, and this phenomenon does not then exist in the three-phase modulations mode.At this, the common mode current that is caused by the switched voltage pattern can be reduced synchronously and to a certain extent by making triangular wave carrier.But, when adopting the bi-phase modulated mode to control PWM rectifier and inverter, because the switching of voltage mode is respectively so that independently the cycle carries out, so exist the synchronization that switches in of both voltage modes to carry out, make common mode current takes place respectively in PWM rectifier and inverter, these common mode currents are overlapping and produce big this problem of common mode current of peak value, and the triangular wave carrier of PWM rectifier and inverter can't be addressed this problem synchronously.
The scheme of patent documentation 4 is at common mode current, and in the scheme of patent documentation 4, because the instruction itself that makes switch connection/disconnections is postponed processing, thus may cause normally exporting required voltage, make output current distort.In addition, because the paired pulses command value itself postpones to handle, so also there is the circuit that causes postponing to handle very complicated this problem that becomes itself.
Summary of the invention
The object of the present invention is to provide a kind of power-converting device, this power-converting device can reduce the peak value of common mode current when adopting the bi-phase modulated mode to control PWM rectifier and inverter.
Other problems beyond the above-mentioned problem are elaborated by this specification whole content and accompanying drawing.
In power-converting device of the present invention, as the method that solves above-mentioned problem, so that the phase difference of the triangular wave carrier separately of PWM rectifier that employing bi-phase modulated mode drives and inverter becomes zero mode, make the triangular wave carrier of PWM rectifier and inverter synchronous, and be conceived to the switching timing of the voltage mode of bi-phase modulated mode separately, when the switching of the voltage mode of PWM rectifier and inverter will take place at short notice in succession, by prolonging wherein the time period of a side voltage mode the switching timing of voltage mode is revised, thereby made the switching of voltage mode of PWM rectifier and inverter can not take place in succession at short notice.
As formation of the present invention, for example can adopt following structure.
(1) provides a kind of power-converting device, has the PWM rectifier, inverter, and the controller of controlling described PWM rectifier and described inverter by the bi-phase modulated mode, in power-converting device, described controller makes phase difference become zero mode so that each triangular wave carrier that uses in the control computing of described PWM rectifier and described inverter is synchronous described PWM rectifier and described inverter is driven, and, when the switching timing of the switching timing of the voltage mode of the bi-phase modulated mode of described PWM rectifier and the voltage mode of the bi-phase modulated mode of described inverter will closely take place mutually with the interval shorter than official hour section, revise the switching timing of the voltage mode of bi-phase modulated mode by prolonging wherein the time period of the voltage mode of a side bi-phase modulated mode, thereby make the switching timing of switching timing and the voltage mode of the bi-phase modulated mode of described inverter of voltage mode of bi-phase modulated mode of described PWM rectifier separate the above interval generation of described official hour section each other.
(2) according to (1) described power-converting device, the phase angle that the extended range of the time period of the voltage mode of preferred described bi-phase modulated mode is preferably voltage instruction value is the following scopes of 30 degree.
(3) according to (1) or (2) described power-converting device, preferably when the time period of the voltage mode that prolongs described bi-phase modulated mode, preferably prolong time period of voltage mode of the lower side's of output frequency in described PWM rectifier and the described inverter described bi-phase modulated mode.
(4) according to each the described power-converting device in (1) to (3), preferably have common mode choke (common mode choke) and a plurality of capacitor, described common mode choke is connected between power supply and the described PWM rectifier, described a plurality of capacitor is corresponding with each of described power supply respectively, the one end is connected in the corresponding wiring mutually between described common mode choke and the described PWM rectifier, other end ground connection.
(5) according to each the described power-converting device in (1) to (4), described controller preferably generates the described triangular wave carrier separately of described PWM rectifier and described inverter by the same arithmetic processing apparatus that is connected with single quartz-crystal resonator, so that described PWM rectifier and described inverter are controlled.
Said structure is an example of the present invention, and the present invention can carry out suitable change in the scope that does not break away from technological thought.Structure example of the present invention beyond the said structure will be described in detail by this specification whole content and accompanying drawing.
According to the present invention, can reduce the peak value of common mode current, thereby can suppress adverse effect surrounding devices.In addition, the small-sized and lightweight of the common mode choke that protection against noise is used.
Other effects of the present invention will be described in detail by the whole content of this specification.
Description of drawings
Fig. 1 is the structure chart of expression embodiments of the invention.
Fig. 2 is the key diagram of the voltage mode of bi-phase modulated mode.
Fig. 3 is the key diagram of the voltage instruction value of bi-phase modulated mode.
Type of attachment when Fig. 4 represents to be provided with common mode choke and direct-to-ground capacitance device in the embodiments of the invention.
The equivalent electric circuit of the zero phase when Fig. 5 represents to adopt structure shown in Figure 4.
Fig. 6 represents the analysis result of the common mode current under the various carrier phase difference of the prior art.
Fig. 7 is that carrier phase difference of the prior art is 0 the enlarged drawing of analysis result of common mode current when spending.
Fig. 8 is the schematic diagram of common-mode voltage of the prior art.
Fig. 9 is the flow chart of the control and treatment in the embodiments of the invention.
Figure 10 is the schematic diagram of the common-mode voltage in the embodiments of the invention.
Figure 11 is the analysis result of the common mode current in the embodiments of the invention.
Figure 12 is prior art constructions figure.
Among the figure:
The 1-power supply
2-boosts and uses reactor
The 3-PWM rectifier
The 4-inverter
The 5-motor
The 6-controller
The 7-common mode choke
8-direct-to-ground capacitance device
Embodiment
Followingly embodiments of the invention are described with reference to accompanying drawing.In each figure, identical or similarly component part adopt identical symbolic representation, and omit its explanation.
Fig. 1 is the structure chart of expression embodiments of the invention.Fig. 1 (a) is the structure chart of an example of the power-converting device of expression embodiments of the invention, the switching timing of the voltage mode of Fig. 1 (b) expression bi-phase modulated mode of the present invention.In Fig. 1 (b), transverse axis express time t, the upper portion of figure represent to adopt the voltage mode of the PWM rectifier 3 of bi-phase modulated mode, and lower portion represents to adopt the voltage mode of the inverter 4 of bi-phase modulated mode.Shown in Fig. 1 (a), power-converting device of the present invention is made of with reactor 2, the inverter 4 that is connected with PWM rectifier 3 with the PWM rectifier 3 that is connected with reactor 2 of boosting, by smmothing capacitor and to the controller 6 that the control signal that drives PWM rectifier 3 and inverter 4 is carried out computing boosting of being connected with power supply 1.
The AC voltage conversion of the commercial frequency that PWM rectifier 3 will be supplied with by power supply 1 with reactor 2 by boosting is a direct voltage.Inverter 4 is a variable frequency with dc voltage conversion, to drive the motor 5 that is connected with the outlet side of inverter 4.In controller 6, computing makes the switch element that constitutes PWM rectifier 3 connect the signal of (ON)/disconnection (OFF), and the switch element of PWM rectifier 3 controlled, make the electric current of the AC side that flows to PWM rectifier 3 and the direct voltage and instruction value of DC side be consistent.And, in controller 6, computing makes the switch element that constitutes inverter 4 connect (ON)/disconnect the signal of (OFF), and the switch element of inverter 4 is controlled, and makes the electric current of the outlet side that flows to inverter 4 and the rotary speed and instruction value of motor 5 be consistent.
In the present invention, PWM rectifier 3 and inverter 4 are driven in bi-phase modulated mode described later by controller 6.And, in controller 6, when computing is used to drive the ON/OFF signal of PWM rectifier 3 and inverter 4, adopt the mode that compares with general triangular wave carrier signal, make each triangular wave carrier signal so that phase difference becomes zero and synchronous mode drives PWM rectifier 3 and inverter 4.
Fig. 2 is the key diagram of the voltage mode of bi-phase modulated mode.The condition of the voltage mode of Fig. 2 (a) expression bi-phase modulated mode, Fig. 2 (b) represents the 1st voltage instruction value, the waveform of the 2nd voltage instruction value and the corresponding relation between the voltage mode.With inverter 4 is example, when the command value of computing inverter 4, at first, in the arithmetic processing apparatus of the microprocessor in being installed in controller 6 etc., by the torque instruction value of speed control system calculating motor output torque, make that the difference between speed value that is used for drive motor 5 and the speed detected value that obtains by the not shown speed detector that is installed in motor 5 is zero.After this, generate the 1st voltage instruction value by current control system, make that the difference between the torque current component of the current detector that obtains with the proportional current value of torque instruction value with by the not shown current detector that the output with inverter 4 is connected is zero, and the difference between the field supply component of the command value of the feasible magnetic-field component that gives motor 5 and the current detection value that obtains by described current detector is zero.
Wherein, as shown in Figure 2, will be made as corresponding to described the 1st voltage instruction value of each output phase of inverter 4 vu*, vv*, during vw*}, be used for the 2nd voltage instruction value that the triangular wave carrier signal with the bi-phase modulated mode compares vw} satisfies for vu, vv:
vu＝vu*+Vo ...(1)
vv＝vv*+Vo ...(2)
vw＝vw*+Vo ...(3)
Wherein, the Vo in the formula exists
Mid{vu*, vv*, vw*} 〉=0 o'clock,
Be Vo=-min{vu*, vv*, vw*} ... (4)
At mid{vu*, vv*, vw*}＜0 o'clock,
Be Vo=DC potential (peak value of triangular wave carrier)-max{vu*, vv*, vw*}... (5)
In following formula, max{vu*, vv*, vw*}, mid{vu*, vv*, vw*} and min{vu*, vv*, vw*} represent the 1st voltage instruction value { vu*, vv*, the maximum among the vw*}, median and minimum value respectively.At this moment, shown in Fig. 2 (b), ({ vu, vv vw}) become distorted waveform to the 2nd voltage instruction value to the command voltage of each phase, but because Vo is suitable with zero phase voltage, so voltage between lines is sinusoidal wave, therefore, can be subjected to obstacle ground motor 5 is driven.
In the bi-phase modulated mode, as shown in Figure 2, can divide into 12 voltage modes according to the order of the magnitude of voltage of each phase voltage and the order of median.And, when adopting the bi-phase modulated mode, in each voltage mode, the command voltage of each phase (the 2nd voltage instruction value { vu, vv, vw}) command voltage in is kept the voltage that equates with the minimum value of the maximum of triangular wave carrier or triangular wave carrier shown in Fig. 2 (b).In this zone, because corresponding switch element is in the state of ON or OFF all the time, so can not produce switching loss.Therefore, be that the situation that unit carries out the three-phase modulations mode of ON/OFF is compared all with whole switch elements with cycle of triangular wave carrier, have the effect that can reduce the wastage significantly.
But, can know from Fig. 2 (b), in the switching between switching between switching between switching between switching between switching between pattern 1 and pattern 2, mode 3 and the pattern 4, pattern 5 and the pattern 6, mode 7 and the pattern 8, pattern 9 and the pattern 10, pattern 11 and the pattern 12, the voltage of zero phase component produces big variation.The peakedness ratio of the common mode current of this moment other the time big, may cause residual current circuit breaker to produce misoperation and bring adverse influence to surrounding devices.
Fig. 3 is the key diagram of the voltage instruction value of bi-phase modulated mode, Fig. 3 (a) is the 1st voltage instruction value { vu*, the 2nd voltage instruction value { vu, vv when vv*, the amplitude of vw*} are big, the example of vw}, Fig. 3 (b) is the 1st voltage instruction value { vu*, vv*, the amplitude of vw*} the 2nd voltage instruction value { vu hour, vv, the example of vw}.Can know that from Fig. 3 shown in Fig. 3 (b), { amplitude of vw*} is more little for vu*, vv*, and the change in voltage of zero phase component is big more for the 1st voltage instruction value.At this moment, the peakedness ratio of common mode current other the time big.
In PWM rectifier 3, because the value of output voltage is near the magnitude of voltage of power supply 1, so in general the amplitude of voltage instruction value can increase.On the other hand, in inverter 4, because output gives the voltage of the variable motor of speed 5, so when load was identical, along with the increase of rotary speed, the amplitude of voltage instruction value increased.That is to say that during with low speed rotation, shown in Fig. 3 (b), the change in voltage of the zero phase voltage of inverter 4 increases at motor 5.
Below the occurring principle of common mode current is described.In general, partly and between the grounded part (ground connection) there is stray capacitance (stray capacity) in the internal wiring at feed line and motor 5.Especially in motor 5, because its inner stationary part is provided with internal wiring to high-density, so there is bigger stray capacitance between the motor field frame of this winding and ground connection.Because the variation of the voltage (common-mode voltage) of the zero phase component of PWM rectifier 3 or inverter 4, common mode current flows to grounded part by wiring (playing the effect of inductance) and described stray capacitance.Because this common mode current leaks towards mains side, may cause residual current circuit breaker generation misoperation, bring adverse influence perhaps for the equipment that is connected on the same power supply.
Type of attachment when Fig. 4 represents to be provided with common mode choke and direct-to-ground capacitance device (ground condenser) in an embodiment of the present invention.As shown in Figure 4, the AC side with PWM rectifier 3 be connected boost with reactor 2 and power supply 1 between be connected with common mode choke 7.In addition, to be connected with each corresponding mode of power supply 1, an end of each direct-to-ground capacitance device 8 connects with corresponding wiring mutually between common mode choke 7 and PWM rectifier 3 direct-to-ground capacitance device 8 respectively, and the other end of direct-to-ground capacitance device 8 is connected with earth connection (ground connection).In this structure, common mode current circulates in low-impedance direct-to-ground capacitance device 8, so can reduce the discharge of the common mode current that flows to power supply 1 side that is connected with high impedance common mode choke 7.This form power supply 1 with boost with reactor 2 between use long the connection under the situation that electric wire connects up too.At this moment, the inductive component that connects electric wire is suitable with common mode choke 7, and the stray capacitance that connects between electric wire and the ground connection is suitable with direct-to-ground capacitance device 8.
The equivalent electric circuit of the zero phase when Fig. 5 represents to adopt structure shown in Figure 4.In Fig. 5, Lm, Cm and Rm represent respectively between the winding-housing of inductive component, motor 5 of the AC side wiring of inverter 4 the stray capacitance component and with the zero corresponding resistive component of phase component.And Lf, Cg represent respectively to boost with zero phase component and the direct-to-ground capacitance device 8 of reactor 2, Lc, Ls and Rs represent respectively zero phase inductance component that the connecting line of common mode choke 7, mains side etc. produces and with the zero corresponding resistive component of phase component.In addition, the common-mode voltage Vc among Fig. 5 is:
Common-mode voltage Vc=(component of voltage of zero phase that produces by inverter 4)-(by the component of voltage of the zero phase of PWM rectifier 3 generations) ... (6)
The common mode current Ic that flows in circuit is corresponding with the difference component of the component of voltage of the zero phase that is produced by PWM rectifier 3 and inverter 4.
The analysis result of the common mode current that has flowed at mains side when below explanation has been used model shown in Figure 5 in prior art and embodiments of the invention.
Figure 12 represents prior art constructions figure.Figure 12 (a) is corresponding with Fig. 1 (a), and Figure 12 (b) is corresponding with Fig. 1 (b).Figure 12 (a) is with the difference of Fig. 1 (a), in Figure 12 (a), is provided with the controller 63 of control PWM rectifier 3 usefulness and the controller 64 of control inverter 4 usefulness respectively independently and replaces controller 6.In addition, in Figure 12 (a), the triangular wave carrier of the triangular wave carrier of PWM rectifier 3 and inverter 4 is asynchronous.In addition, the difference of Figure 12 (b) and Fig. 1 (b) is, shown in the part that surrounds by dotted line of Figure 12 (b), and the timing that in PWM rectifier 3 and inverter 4, exists the voltage mode of bi-phase modulated mode to switch simultaneously.Have, in Figure 12 (b), transverse axis express time t, the upper portion of figure represent to adopt the voltage mode of the PWM rectifier 3 of bi-phase modulated mode again, and lower portion represents to adopt the voltage mode of the inverter 4 of bi-phase modulated mode.
As shown in figure 12, in the general power converter that adopts prior art, each triangular wave carrier that PWM rectifier 3 and inverter 4 use when generating command value is asynchronous.This be because, in the ordinary course of things, PWM rectifier 3 carries out calculation process with inverter 4 by different microprocessors, even the frequency of triangular wave carrier is identical, its phase state is also uncertain.In addition, even phase difference is zero under the accidental state in the early stage, but because there is small error in the quartz-crystal resonator that is arranged in each microprocessor, so under extremely low frequency, phase state can change.
The analysis result of the common mode current when Fig. 6 represents to make in the prior art phase difference of triangular wave carrier (same frequency) to change, Fig. 6 (a) expression carrier phase difference is 0 analysis result when spending, and Fig. 6 (b) expression carrier phase difference is 180 analysis results when spending.In addition, at Fig. 6 (a) with (b), except the phase difference difference of triangular wave carrier, other condition is all identical.In Fig. 6, transverse axis express time (s), the longitudinal axis are represented the size (A) of common mode current.
Can know from Fig. 6 (a) with (b), be that the situation of 0 degree is compared with carrier phase difference, and carrier phase difference is 180 when spending, and the peak value of common mode current (and effective value) is bigger.As mentioned above, in prior art shown in Figure 12, because there is error in quartz-crystal resonator, so between the state shown in the state shown in Fig. 6 (a) and Fig. 6 (b), change repeatedly with extremely low frequency.For this reason, even under the bigger state of the amplitude shown in Fig. 6 (b),, also need to be provided with big common mode choke 7 for fear of producing magnetic saturation.
Below explanation is fixed on the carrier phase difference between PWM rectifier 3 and the inverter 40 situation when spending in the prior art of Figure 12.In recent years, along with the function raising apace of arithmetic processing apparatus such as microprocessor, thus can be by realizing above-mentioned condition with same microprocessor driven PWM rectifier 3 and inverter 4.The waveform of the common mode current of this moment is shown in Fig. 6 (a).At this, can know from Fig. 6 (a), though the peak value of common mode current has reached 0.45A, but common mode current is not to remain on this big peak value, in most of the cases, common mode current is suppressed to the little common mode current about 0.1A, can produce big peak value in intermittence ground once in a while.
Therefore; shown in Fig. 6 (a); be fixed as 0 degree by carrier phase difference with PWM rectifier 3 and inverter 4; though can dwindle common mode current to a certain extent; even but carrier phase difference has been fixed on 0 degree; common mode current also the time regular meeting big peak value appears, thereby exist may to around equipment bring problems such as adverse effect.As mentioned above, only, can not suppress common mode current fully, below its reason be inquired into by the carrier phase difference between PWM rectifier 3 and the inverter 4 being fixed as 0 degree.
Fig. 7 is the waveform of the common-mode voltage of near the enlarged drawing of the part peak value of common mode current of Fig. 6 (a) and this part.In Fig. 7, upper portion is represented the waveform of common-mode voltage, and lower portion is represented the waveform of common mode current.Can know that from Fig. 7 in the big part of the peak value of common mode current, the fluctuation of common-mode voltage is also big.
Following is that the schematic diagram of the common-mode voltage of prior art describes the fluctuation of this common-mode voltage with reference to Fig. 8.Fig. 8 (a) is the schematic diagram of the voltage of the command value, pwm pulse of PWM rectifier side and zero phase component, is the example of voltage mode when intermediate point changes of bi-phase modulated mode.Shown in Fig. 8 (a), in the triangular wave manner of comparison, at the command value (vr of each phase, vs, vt) in the part greater than triangular wave carrier, the drive signal of the switch element of each phase is pwm pulse (vr_p, vs_p, vt_p) be ON, and at command value (vr, the vs of each phase, vt) in the part less than triangular wave carrier, (vr_p, vs_p vt_p) are OFF to this pwm pulse.In Fig. 8 (a), because signal is the signal of controlling by the bi-phase modulated mode, so in first half, command value vr is all the time greater than triangular wave carrier, pwm pulse vr_p is always ON.And in latter half, command value vt is all the time less than triangular wave carrier, and pwm pulse vt_p is always OFF.Under the situation of Fig. 8 (a), will the output voltage of each phase (with the drive signal of switch element be that pwm pulse (vr_p, vs_p, vt_p) voltage of output correspondingly) is made as vr_out respectively, vs_out, during vt_out,
The voltage Vc3 of the zero phase component of PWM rectifier side satisfies:
The voltage Vc3=(vr_out+vs_out+vt_out)/3 of the zero phase component of PWM rectifier side
∝(vr_p+vs_p+vt_p)/3 ...(7)
In the formula, ∝ is expressed as ratio.That is to say that the mean value of the voltage Vc3 of the zero phase component of PWM rectifier side and pwm pulse (vr_p+vs_p+vt_p) is proportional.
Fig. 8 (b) is the schematic diagram of voltage of command value, pwm pulse, zero phase component of inverter side, is the example of the little situation (with the suitable situation of Fig. 3 (b)) of the amplitude of instruction voltage.Command value (vu in each phase, vv, vw) in the part greater than triangular wave carrier, the drive signal of the switch element of each phase is pwm pulse (vu_p, vv_p, vw_p) be, and at command value (vu, the vv of each phase, vw) in the part less than triangular wave carrier, (vu_p, vv_p vw_p) are OFF to pwm pulse.In this example, the voltage mode of bi-phase modulated mode also is to change at intermediate point, and in first half, command value vw is all the time less than triangular wave carrier, and pwm pulse vw_p is in the OFF state all the time.And in latter half, command value vv is all the time greater than triangular wave carrier, and pwm pulse vv_p is in the OFF state all the time.In addition, with the output voltage of each phase (with the drive signal of switch element be that when being made as vu_out, vv_out, vw_out respectively, the voltage Vc4 of zero phase component of inverter side is satisfied for pwm pulse (vu_p, vv_p, vw_p) voltage of output accordingly):
The voltage Vc4=(vu_out+vv_out+vw_out)/3 of the zero phase component of inverter side
∝(vu_p+vv_p+vw_p)/3 ...(8)
That is to say that (mean value vw_p) is proportional for vu_p, vv_p for the voltage Vc4 of the zero phase component of inverter side and pwm pulse.
Fig. 8 (c) is the schematic diagram of the common-mode voltage of the circuit integral body that obtains of through type (6).Can know from formula (6), because the common-mode voltage Vc=Vc3+Vc4 of circuit integral body, so big in the fluctuation of the dotted portion common-mode voltage of Fig. 8 (c).
Can know from above-mentioned analysis result, when variation has taken place in voltage mode in PWM rectifier side and inverter side bi-phase modulated mode simultaneously, because the variation of each zero phase voltage is overlapping, so can cause common mode current generation Fig. 6 (a) and big peak value shown in Figure 7.In the prior art, because computing is carried out in the processing (processing of formula (1)～formula (5)) of the bi-phase modulated mode of PWM rectifier 3 and inverter 4 respectively independently, so shown in Figure 12 (b), the timing that the voltage mode of bi-phase modulated mode switches simultaneously can take place in PWM rectifier 3 and inverter 4 aperiodically, at this moment, big fluctuation shown in Figure 7 can take place in common-mode voltage and common mode current.
For this reason, in the present invention, when as Figure 12 (b) when the switching of the voltage mode of bi-phase modulated mode takes place at short notice in succession in the PWM rectifier 3 that is shown in and the inverter 4, shown in Fig. 1 (b), implement to make the control that time period of a side voltage mode wherein prolongs.Be specifically, when the switching timing of the switching timing of the voltage mode of the bi-phase modulated mode of PWM rectifier 3 and the voltage mode of the bi-phase modulated mode of inverter 4 will closely take place mutually with the interval shorter than official hour section, by prolonging the wherein time period of the voltage mode of a side bi-phase modulated mode, switching timing to the voltage mode of bi-phase modulated mode is revised, and makes the switching timing of voltage mode of bi-phase modulated mode of the switching timing of voltage mode of bi-phase modulated mode of PWM rectifier 3 and inverter 4 separate the above interval of described official hour section each other and takes place.For example, by control, the time period of the pattern 1 in the voltage mode of bi-phase modulated mode of inverter 4 sides of dotted portion of Fig. 1 (b) is prolonged, the time period of pattern 2 is shortened, voltage mode with the bi-phase modulated mode of PWM rectifier 3 sides staggers from the timing that pattern 5 switches to pattern 6 thus, thereby avoids the voltage mode of PWM rectifier 3 and inverter 4 to switch simultaneously.In addition, in Fig. 1 (b), with time period of the voltage mode of the bi-phase modulated mode that prolongs inverter 4 sides be that example is described, but also can prolong time period of voltage mode of the bi-phase modulated mode of PWM rectifier 3 sides.
Fig. 9 is the flow chart of the control and treatment of embodiments of the invention.At first, in square 9, carry out the computing of current control system, and computing the 1st voltage instruction value (vu*, vv*, vw*).After this, select two the judgment model shielding marks whether to be 1 in the square 10.Wherein, when the switching timing of the switching timing of the voltage mode of the bi-phase modulated mode of PWM rectifier 3 and the voltage mode of the bi-phase modulated mode of inverter 4 will take place close to each other with the interval shorter than official hour section (comprise simultaneously and taking place), this pattern shielding mark becomes 1.Select two that to be judged as pattern shielding mark in the square 10 be at 1 o'clock, in square 11, from memory, read the previous value of voltage mode of the bi-phase modulated mode of PWM rectifier 3, the control computing of implementing the bi-phase modulated mode of PWM rectifier 3 in square 12 (is replaced into vr with the processing of formula (1)～formula (5), vs, vp carries out).Then, in square 13, from memory, read the previous value of voltage mode of the bi-phase modulated mode of inverter 4, and in square 14, implement the control computing (processing of formula (1)～formula (5)) of the bi-phase modulated mode of inverter 4.In addition, the described official hour section of time period of decision pattern shielding mark for example is set at the multiple of the duty cycle of the control computing of implementing PWM rectifier 3 and inverter 4.For example, square 20 as described later, shown in 28, the number of times of this task is set at N time, and setting is called as the variable that shields timer and stores, shown in square 15, with the duty cycle is that unit carries out subtraction, up to becoming till 0, so, then can in described official hour section, keep the voltage mode of bi-phase modulated mode.In square 15, implement successively decreasing of shielding timer, select two that to be judged as the shielding timer in the square 16 be not 0 o'clock end process, be 0 o'clock being judged as the shielding timer, in square 17 pattern being shielded flag settings is 0 back end process.
After this, select two that to be judged as pattern shielding mark in the square 10 be not at 1 o'clock, in square 18, (but be replaced into vr according to the condition identical with Fig. 2, vs, vt) (vr, vs select the voltage mode of bi-phase modulated mode in vt) from the voltage instruction value of PWM rectifier 3.And it is identical at the voltage mode of two voltage modes of selecting the bi-phase modulated mode of judging PWM rectifier 3 in the square 19 during whether with previous operation.In the operation values of the voltage mode of bi-phase modulated mode and previous operation value not simultaneously, variation has taken place in the voltage mode of expression PWM rectifier 3, is 1 so in square 20 pattern is shielded flag settings, is N with the specification of variables of shielding timer.After this, the voltage mode with the bi-phase modulated mode of PWM rectifier 3 in square 21 is stored in the memory, and implements the later processing of square 12.Select the operation values of voltage mode of the bi-phase modulated mode that is judged as PWM rectifier 3 in the square 19 when identical two with the previous operation value, because the voltage mode of the bi-phase modulated mode of expression PWM rectifier 3 does not change, so the voltage mode with the bi-phase modulated mode of PWM rectifier 3 in square 22 is stored in the memory, the control computing of implementing the bi-phase modulated mode of PWM rectifier 3 in square 23 (is replaced into vr with the processing of formula (1)～formula (5), vs, vp carries out).
After this, in square 24 according to the condition of Fig. 2 voltage instruction value (vu* from inverter 4, vv* selects the voltage mode of bi-phase modulated mode in vw*), and is identical at the voltage mode of two voltage modes of selecting the bi-phase modulated mode of judging inverter 4 in the square 25 during whether with previous operation.When the operation values of the voltage mode of bi-phase modulated mode is identical with the previous operation value, because the voltage mode of inverter 4 does not change, so the voltage mode with the bi-phase modulated mode of inverter 4 in square 26 is stored in the memory, in square 27, implement control computing (processing of formula (1)～formula (5)) the back end process of the bi-phase modulated mode of inverter 4.Select the operation values of the voltage mode that is judged as the bi-phase modulated mode in the square 25 and previous operation value not simultaneously two, variation has taken place in the voltage mode of expression inverter 4, therefore in square 28 pattern being shielded flag settings is 1, is N with the specification of variables that shields timer.After this, the bi-phase modulated voltage mode with inverter 4 in square 29 is stored in the memory, implements the control computing (processing of formula (1) formula～formula (5)) of the bi-phase modulated mode of inverter 4 in square 30.After this, in square 31, implement successively decreasing of shielding timer, and end process.
The control and treatment of the time period of the voltage mode of prolongation bi-phase modulated mode shown in Figure 9 can not make the ON/OFF of common switch postpone, so voltage between lines can not change, can not produce voltage distortion yet.But (for example, duty cycle * N) upper limit is arranged must be in the time period of next voltage mode so prolong owing to the time period that can prolong.That is to say, in Fig. 2, the scope that the time period of the pattern 1 of voltage mode can increase equals the time period of the pattern 2 of voltage mode, when satisfying when voltage mode 1 carries out the transition to the condition of voltage mode 3, because vv will be greater than as the fixing vu of maximum, thereby might cause voltage distortion to take place.Can know that from Fig. 2 the phase angle in a week is 360 degree because 12 voltage modes circulate,, therefore be necessary the phase angle of described higher limit is controlled at below 30 degree so the phase angle of a voltage mode equals 30 degree.
From the absolute time of each voltage mode, frequency low more (cycle is long more), then the time of voltage mode is long more.It is identical with the frequency of power supply that the frequency of the output voltage of PWM rectifier 3 is fixed to, and the frequency of inverter 4 is owing to proportional with the rotation number of motor, so the frequency of this inverter 4 can change.Wherein, when the voltage mode of the bi-phase modulated mode of PWM rectifier 3 and inverter 4 will switch simultaneously, the time period of the voltage mode by prolonging the lower side of frequency, has the effect of the higher limit (just can increase N) that can increase in the time.In addition, when (just with N fixedly time) under the situation about counting with the time during identical, can dwindle error, so have the effect of the balance of the shutdown switch time that can improve switch element with respect to the phase angle.
Figure 10 is the schematic diagram of the common-mode voltage in the embodiments of the invention.Figure 10 (a) has the identical pulse with Fig. 8 (a), and Figure 10 (b) expression prolongs the situation of voltage mode with the switching of delay voltage pattern by the processing of Fig. 9.According to this processing, the common-mode voltage Vc that can make the circuit integral body shown in Figure 10 (c) is in the situation of the fluctuation of the utmost point in the short time less than Fig. 8 (c), and its result has the effect of the peak value that can reduce common mode current.
Figure 11 is the analysis result of the common mode current of embodiments of the invention.Figure 11 is illustrated under the condition identical with Fig. 6 (a) processing of implementing Fig. 9, for fear of the switching of the voltage mode of the bi-phase modulated mode of PWM rectifier 3 and inverter 4 result when having prolonged the wherein time period of a side pattern takes place in succession at short notice.Can know that from this result the peak value of common mode current is 0.39A, compare, can reduce peak value more than 10% with the prior art constructions of Fig. 6 (a).In addition, the peak value of this common mode current because of the voltage mode of bi-phase modulated mode time expand section and the variation of the amplitude condition of PWM rectifier 3 and inverter 4 change, and can further dwindle.Thus, has the effect that can prevent residual current circuit breaker generation misoperation and reduce adverse effect that surrounding devices is brought etc.Small-sized and the light-weighted effect that perhaps has common mode choke 7 grades that can realize that protection against noise is used.
In addition, the controller 6 preferably same arithmetic processing apparatus by being connected with single quartz-crystal resonator (for example microprocessor etc.) generates the triangular wave carrier separately of PWM rectifier 3 and inverter 4, so that PWM rectifier 3 and inverter 4 are controlled.The simultaneous bias that can suppress thus, the phase place of 2 triangular wave carriers that the deviation owing to 2 quartz-crystal resonators produces.
Power-converting device of the present invention for example can be applied in drive unit of elevator etc.
Abovely describe the present invention with reference to embodiment, but illustrated structure is an example in above-mentioned each embodiment, the present invention can carry out suitable change in the scope that does not break away from technological thought.
Claims (5)
1. power-converting device has PWM rectifier, inverter and controls the controller of described PWM rectifier and described inverter by the bi-phase modulated mode, it is characterized in that,
Described controller makes each triangular wave carrier that uses in the control computing of described PWM rectifier and described inverter become zero mode with phase difference and drives synchronously, and, when the switching timing of the switching timing of the voltage mode of the bi-phase modulated mode of described PWM rectifier and the voltage mode of the bi-phase modulated mode of described inverter will closely take place mutually with the interval shorter than official hour section, revise the switching timing of the voltage mode of bi-phase modulated mode by prolonging wherein the time period of the voltage mode of a side bi-phase modulated mode, thereby make the switching timing of switching timing and the voltage mode of the bi-phase modulated mode of described inverter of voltage mode of bi-phase modulated mode of described PWM rectifier separate the above interval generation of described official hour section each other.
2. power-converting device according to claim 1 is characterized in that,
The extended range of the time period of the voltage mode of described bi-phase modulated mode is the scope of phase angle below 30 degree of voltage instruction value.
3. power-converting device according to claim 1 is characterized in that,
When the time period of the voltage mode that prolongs described bi-phase modulated mode, prolong time period of voltage mode of the side's that output frequency is lower in described PWM rectifier and the described inverter described bi-phase modulated mode.
4. power-converting device according to claim 1 is characterized in that,
Have common mode choke and a plurality of capacitor, described common mode choke is connected between power supply and the described PWM rectifier, described a plurality of capacitor is corresponding with each of described power supply respectively, the one end is connected in the corresponding wiring mutually between described common mode choke and the described PWM rectifier, other end ground connection.
5. according to each the described power-converting device in the claim 1 to 4, it is characterized in that,
Described controller generates the described triangular wave carrier separately of described PWM rectifier and described inverter by the same arithmetic processing apparatus that is connected with single quartz-crystal resonator, so that described PWM rectifier and described inverter are controlled.
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| JP2009270969A JP5241692B2 (en) | 2009-11-30 | 2009-11-30 | Power converter |
| JP2009-270969 | 2009-11-30 |
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| JP (1) | JP5241692B2 (en) |
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| CN103051281A (en) * | 2013-01-30 | 2013-04-17 | 秦皇岛国能石油装备有限公司 | High-performance four-quadrant frequency converter |
| CN103062023A (en) * | 2013-01-30 | 2013-04-24 | 秦皇岛国能石油装备有限公司 | Intelligent linear-motor oil production system |
| CN103401588A (en) * | 2013-08-02 | 2013-11-20 | 成都博高科技有限责任公司 | Low-voltage power line carrier three-phase coupling circuit |
| CN104300815A (en) * | 2013-07-18 | 2015-01-21 | 株式会社日立制作所 | Power conversion device and elevator |
| CN108596060A (en) * | 2018-04-12 | 2018-09-28 | 上海思立微电子科技有限公司 | Fingerprint image processing method, fingerprint identification device and electronic equipment |
| CN110380636A (en) * | 2018-04-12 | 2019-10-25 | 株式会社东芝 | The control method of power-converting device and power-converting device |
| CN113302831A (en) * | 2019-01-28 | 2021-08-24 | 三菱电机株式会社 | Power conversion device |
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| JP5676990B2 (en) * | 2010-09-17 | 2015-02-25 | 株式会社東芝 | Switching method for power converter |
| CA2868700C (en) | 2012-03-30 | 2016-10-11 | Toshiba Mitsubishi-Electric Industrial Systems Corporation | Power supply apparatus |
| JP6221815B2 (en) * | 2014-02-20 | 2017-11-01 | 株式会社明電舎 | Inverter control method and inverter |
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| DE112021007968T5 (en) * | 2021-07-14 | 2024-04-25 | Mitsubishi Electric Corporation | POWER CONVERTER DEVICE |
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Also Published As
| Publication number | Publication date |
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| CN102082547B (en) | 2013-04-10 |
| HK1153053A1 (en) | 2012-03-16 |
| JP5241692B2 (en) | 2013-07-17 |
| JP2011114991A (en) | 2011-06-09 |
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