CN101010730A - Scalable decoding device and signal loss compensation method - Google Patents
Scalable decoding device and signal loss compensation method Download PDFInfo
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Abstract
There is provided a scalable decoding device capable of improving resistance against a transmission error. In the device, a narrow band LSP decoding unit (108) decodes narrow band LSP encoded information corresponding to a core layer of the current encoded information. A storage unit (126) stores a wide band quantized LSP corresponding to an extended layer of the past encoded information as a stored wide band LSP. When the wide band LSP encoded information is lost from the current encoded information, a compensation unit formed by a combination of a frame loss compensation unit (124) and a switching unit (128) generates a compensated wide band LSP by weighted addition of the band conversion LSP of the narrow band quantized LSP and the stored wide band LSP, thereby compensating the decoding signal of the lost wide band LSP encoded information by the compensated wide band LSP.
Description
Technical field
The present invention relates to scalable decoder with and the lossing signal compensation method, this scalable decoder is decoded to the coded message that has extensibility in bandwidth (being the frequency axis direction).
Background technology
In general, in the coding of voice signal, be extensive use of LSP (line spectrum pair) parameter as the parameter that shows spectrum envelope information effectively.In addition, LSP is also referred to as LSF (line spectral frequencies).
The coding of LSP parameter (being designated hereinafter simply as " LSP "), it is one of essential basic technology in the speech coding technology of encoding speech signal efficiently, voice signal is hierarchically being encoded, but and generate accordingly in the frequency band extended voice coding of narrow band signal and broadband signal with core layer and extension layer respectively, also be important basic technology.
But as the method in the past that the coding LSP that obtains with frequency band extended voice coding is decoded, the method that for example has patent documentation 1 to be put down in writing.Scalable decoding method disclosed herein is: decoding LSP takes advantage of 0.5 times with the arrowband of core layer, and with component addition in the extension layer decoding, obtain wideband decoded LSP thus.
On the other hand, when above-mentioned coding LSP is transmitted, might on the warp of transmission road, lose its part.When the part of LSP does not arrive decoding end, need handle information with compensating missing in decoding end.Like this, when carrying out voice communication under the system environments that might make mistakes in information transmission, on the meaning of the fault-tolerant ability of improving the audio coding/decoding mode, the use that loss compensation is handled can be described as very important necessary basic technology.For example, the loss compensation that patent documentation 2 is put down in writing is treated to: be divided into and, when 7 LSP no show decoding end of high order, 7 LSP of high order that reuse last normal decoder are as decode value for 3 times of low order for 7 times of high order and among 10 LSP being transmitted.
[patent documentation 1] spy opens flat 11-30997 communique
[patent documentation 2] spy opens flat 9-172413 communique
Summary of the invention
The problem that the present invention need solve
Yet, in above-mentioned scalable decoding method in the past, following problem is arranged, that is, because the coding of the part of being lost among the coding LSP that is transmitted LSP is not compensated processing, so can't improve the fault-tolerance of the transmission error that may occur for system environments.
Purpose of the present invention is for providing the scalable decoder and the signal loss compensation method that can improve the fault-tolerance of transmission error.
The scheme of dealing with problems
The structure that scalable decoder of the present invention adopted comprises: decoding unit, the narrow band spectrum parameter corresponding with the core layer of the first hierarchical coding signal decoded; Storage unit is stored the broader frequency spectrum parameter corresponding with the extension layer of the second hierarchical coding signal, and this second hierarchical coding signal is different with the first hierarchical coding signal; And compensating unit, when losing the broader frequency spectrum parameter of the second hierarchical coding signal, frequency band transformation signal by the narrow band spectrum parameter of will be decoded generates the loss compensation signal with the broader frequency spectrum parameter weighting addition of being stored, and compensates the decoded signal of the broader frequency spectrum parameter of being lost with the loss compensation signal.
Signal loss compensation method of the present invention is: when having lost the corresponding broader frequency spectrum parameter of extension layer with current hierarchical coding signal, will be corresponding to the frequency band transformation signal of the core layer of current hierarchical coding signal and the narrow band spectrum parameter of being decoded, with broader frequency spectrum parameter weighting addition corresponding to the extension layer of former hierarchical coding signal, thereby generate the loss compensation signal, and compensate the decoded signal of the broader frequency spectrum parameter of being lost with the loss compensation signal.
Effect of the present invention
According to the present invention, can improve fault-tolerance to transmission error.
Description of drawings
Fig. 1 is the block scheme of structure of the scalable decoder of expression embodiment of the present invention 1.
Fig. 2 is the block scheme of structure of the wide-band LSP decoding unit of expression embodiment of the present invention 1.
Fig. 3 is the block scheme of structure of the LOF compensating unit of expression embodiment of the present invention 1.
Fig. 4 A is the figure of the quantification LSP of expression embodiment of the present invention 1.
Fig. 4 B is the figure of the frequency band transformation LSP of expression embodiment of the present invention 1.
Fig. 4 C is the figure of the wide-band LSP of expression embodiment of the present invention 1.
Fig. 4 D is the figure of the compensating wide band LSP of expression embodiment of the present invention 1.
Fig. 5 is the block scheme of structure of the scalable decoder of expression embodiment of the present invention 2.
Fig. 6 is the block scheme of structure of the wide-band LSP decoding unit of expression embodiment of the present invention 2.
Fig. 7 is the block scheme of structure of the LOF compensating unit of expression embodiment of the present invention 2.
Embodiment
Below, use accompanying drawing to explain embodiments of the present invention.
(embodiment 1)
Fig. 1 is the block scheme of major part of structure of the scalable decoder of expression embodiment of the present invention 1.The scalable decoder 100 of Fig. 1 comprises: multiplexing separative element 102, sound source decoding unit 104,106, arrowband LSP decoding unit 108, wide-band LSP decoding unit 110, phonetic synthesis unit 112,114, up-sampling unit 116 and adder unit 118.Fig. 2 is the block scheme of the inner structure of expression wide-band LSP decoding unit 110, and wide-band LSP decoding unit 110 comprises: unit 122, LOF compensating unit 124, storage unit 126 and switch unit 128 are carried out in converter unit 120, decoding.Storage unit 126 comprises buffer 129.Fig. 3 is the block scheme of the inner structure of expression LOF compensating unit 124, and LOF compensating unit 124 comprises weighted units 130,132 and adder unit 134.
Multiplexing separative element 102 is accepted coded message.Wherein, the coded message of being accepted by multiplexing separative element 102 is, by the signal of voice signal hierarchically being decoded and generating at not shown scalable encoding apparatus.In the voice coding of scalable encoding apparatus, generate the coded message that constitutes by arrowband sound source coded message, broadband sound source coded message, arrowband LSP coded message and wide-band LSP coded message.Arrowband sound source coded message is corresponding with core layer and signal that generate with arrowband LSP coded message, and broadband sound source coded message and wide-band LSP coded message are corresponding with extension layer and signal that generate.
Multiplexing separative element 10 is separated into the coded message of being accepted the coded message of each parameter.Arrowband sound source coded message after will separating respectively then outputs to sound source decoding unit 106, arrowband LSP coded message after separating is outputed to arrowband LSP decoding unit 108, broadband sound source coded message after separating is outputed to sound source decoding unit 104, the wide-band LSP coded message after separating is outputed to wide-band LSP decoding unit 110.
106 pairs of arrowband sound source coded messages from multiplexing separative element 102 inputs of sound source decoding unit are decoded, and quantize sound-source signal thereby obtain the arrowband.The arrowband quantizes sound-source signal and is output to phonetic synthesis unit 112.
Up-sampling unit 116 carries out the up-sampling of the arrowband decodeing speech signal of 112 inputs from the phonetic synthesis unit to be handled.The arrowband decodeing speech signal that has carried out the up-sampling processing is output to adder unit 118.
104 pairs of broadband sound source coded messages from multiplexing separative element 102 inputs of sound source decoding unit are decoded, and obtain the wide band quantized sound-source signal.The wide band quantized sound-source signal that is obtained is output to phonetic synthesis unit 114.
Wide-band LSP decoding unit 110 is based on the LOF information described later of illustrated LOF information generating unit input never, wide-band LSP coded message by the arrowband from 108 inputs of arrowband LSP decoding unit quantizes LSP and imports from multiplexing separative element 102 obtains wide band quantized LSP.The wide band quantized LSP that is obtained is output to phonetic synthesis unit 114.
Here, be described more specifically the inner structure of wide-band LSP decoding unit 110 with reference to Fig. 2.
In addition, converter unit 120 also can adopt the processing disposal route in addition that multiply by conversion coefficient to carry out conversion process.For example, can utilize the nonlinear transformation of mapping table, also can comprise LSP is transformed to coefficient of autocorrelation, in the zone of coefficient of autocorrelation, carry out up-sampling and handle.
In addition, the decoding structure of carrying out unit 122 is not limited to said structure.For example, the decoding carry out unit 122 within it portion can possess code book.At this moment, unit 122 is carried out in decoding will be decoded into index information from the wide-band LSP coded message of multiplexing separative element 102 inputs, and use the LSP vector of determining with this index information to obtain wide-band LSP.Can also be following structure in addition, that is, and the wide band quantized LSP that was decoded before using, the former wide-band LSP coded message of importing or in the past from the frequency band transformation LSP of converter unit 120 inputs etc., with the structure of wide band quantized LSP decoding.
Employed stored wide band LSP when storage unit 126 will generate compensating wide band LSP by LOF compensating unit 124 is stored in the buffer 129 of the portion of setting within it in advance, and this stored wide band LSP is outputed to LOF compensating unit 124 and switch unit 128.In addition, upgrade the stored wide band LSP of being stored the buffer 129 with wide band quantized LSP from switch unit 1 28 inputs.
Thus, come the updated stored wide-band LSP with wide band quantized LSP from switch unit 128 inputs.Therefore, when losing follow-up coded message, especially when the wide-band LSP coded message of the next coded message of losing current coded message, the wide-band LSP coded message of coded message that can correspondence is the current and wide band quantized LSP that generates uses as stored wide band LSP, thus compensating wide band LSP generated corresponding to the wide-band LSP coded message of follow-up coded message.
Switch unit 128 switches the information that is output to phonetic synthesis unit 114 as wide band quantized LSP based on the LOF information of being imported.
More particularly, when the LOF information representation of being imported " has normally received all arrowband LSP coded message and wide-band LSP coded message that coded message comprised ", switch unit 128 will directly output to phonetic synthesis unit 114 and storage unit 126 from the wide band quantized LSP that decoding is carried out importing unit 122.In addition, when the LOF information representation " in the arrowband LSP coded message and wide-band LSP coded message that coded message comprised; normally received arrowband LSP coded message; lost at least a portion in the wide-band LSP coded message " of input, switch unit 128 will output to phonetic synthesis unit 114 and storage unit 126 as wide band quantized LSP from the compensating wide band LSP of LOF compensating unit 124 inputs.Have again, when the LOF information representation of input " has been lost arrowband LSP coded message that coded message comprised and at least a portion of wide-band LSP coded message both sides ", switch unit 128 will output to phonetic synthesis unit 114 and storage unit 126 as wide band quantized LSP from the stored wide band LSP of storage unit 126 inputs.
That is to say, LOF compensating unit 124 and switch unit 128 constitute compensating unit, when the wide-band LSP coded message of this compensating unit in the coded message that is input to multiplexing separative element 102 lost, by quantizing LSP frequency band transformation LSP that obtains and the stored wide band LSP weighting summation that is stored in buffer 129 in advance from the arrowband of being decoded, thereby generate the loss compensation signal, and the wide band quantized LSP of the broadband signal of being lost with the loss compensation signal compensation.
Here, be described more specifically the inner structure of LOF compensating unit 124 with reference to Fig. 3.Weighted units 130 will multiply by weighting coefficient w1 from the frequency band transformation LSP of converter unit 120 inputs.Be output to adder unit 134 by the LSP vector that this multiplying obtained.Weighted units 132 will multiply by weighting coefficient w2 from the stored wide band LSP of storage unit 126 inputs.Be output to adder unit 134 by the LSP vector that this multiplying obtained.Adder unit 134 will be respectively from weighted units 130 and the 132 LSP addition of vectors of importing.Generate compensating wide band LSP by this addition.
Referring again to Fig. 1.Phonetic synthesis unit 114 will be transformed to linear predictor coefficient from the quantification wide-band LSP of wide-band LSP decoding unit 110 inputs, and use the linear predictor coefficient that is obtained to construct linear prediction synthesis filter.And, drive this linear prediction synthesis filter with wide band quantized sound-source signal from 104 inputs of sound source decoding unit, thus synthetic decodeing speech signal.This decodeing speech signal is output to adder unit 118.
Then, to the action of the scalable decoder 100 that comprises said structure, weighting summation is handled being illustrated especially.
Here, suppose that the arrowband frequency domain corresponding with core layer is 0～4kHz, the broadband frequency domain corresponding with extension layer is 0～8kHz, converter unit 120 employed conversion coefficients be " 0.5 " situation as an example, and use Fig. 4 A～Fig. 4 D to describe.In Fig. 4 A, sample frequency is 8kHz, and nyquist frequency is 4kHz, and in Fig. 4 B～Fig. 4 D, sample frequency is 16kHz, and nyquist frequency is 8kHz.
At converter unit 120, each time LSP that quantizes LSP by the current arrowband that will be imported takes advantage of 0.5 times, for example the quantification LSP of the 4kHz frequency band shown in Fig. 4 A is transformed to the quantification LSP of 8kHz frequency band, thereby generates for example frequency band transformation LSP shown in Fig. 4 B.In addition, at converter unit 120, can use with above-mentioned diverse ways and come conversion bandwidth (sample frequency).In addition, the number of times of supposing wide band quantized LSP here is 16 times, and is defined as lower frequency region with 1～8 time respectively, is defined as high-frequency domain with 9～16 times.
Frequency band transformation LSP is imported into weighted units 130.To multiply each other with following formula (1) and (2) weighting coefficient w1 (i) that sets and the frequency band transformation LSP that imports from converter unit 120 in weighted units 130.In addition, the frequency band transformation LSP that is imported derives from the current coded message that is obtained by multiplexing separative element 120.In addition, i represents number of times.
W1 (i)=(9-i)/8 (i=1～8) ... formula (1)
W1 (i)=0 (i=9～16) ... formula (2)
On the other hand, for example the stored wide band LSP shown in Fig. 4 C is imported into weighted units 132.In weighted units 132, will multiply each other with following formula (3) and (4) weighting coefficient w2 (i) that sets and the stored wide band LSP of importing from storage unit 126.In addition, the stored wide band LSP of being imported derives from coded message, and this coded message is to be obtained before in the current coded message previous frame of present coded message (for example) by multiplexing separative element 102.
W2 (i)=(i-1)/8 (i=1～8) ... formula (3)
W2 (i)=1 (i=9～16) ... formula (4)
That is to say that weighting coefficient w1 (i) and weighting coefficient w2 (i) are set to and make w1 (i)+w2 (i)=1.0.In addition, more little value when weighting coefficient w1 (i) is set at approaching more high territory between 0～1 is set at 0 in high territory.On the other hand, with weighting coefficient w2 (i) be set between 0～1 more near high-frequency domain the time big more value, be set to 1 at high-frequency domain.
Then at adder unit 134, ask by the LSP that multiplying the obtained vector of weighted units 130 with by the LSP vector that multiplying obtained of weighted units 132 and vector.Like this, by ask described LSP vector and the vector, can obtain for example compensating wide band LSP shown in Fig. 4 D.
It is desirable to, the wide band quantized LSP that decodes when which of " the conversion arrowband quantizes the frequency band transformation LSP that LSP obtains " and " as the stored wide band LSP of the wide band quantized LSP of former decoding " more to be bordering on zero defect according to sets weighting coefficient w1 (i) and w2 (i) adaptively.Just, preferably be set at: make weighting coefficient w1 (i) bigger during wide band quantized LSP when frequency band transformation LSP more is bordering on zero defect, during wide band quantized LSP when stored wide band LSP more is bordering on zero defect, make weighting coefficient w2 (i) bigger.Therefore wide band quantized LSP in the time of can't learning zero defect when LOF takes place is difficult to carry out the setting of desirable weighting coefficient but in fact.Yet, when the scalable coding that carries out as above-mentioned 4kHz band signal and 8kHz band signal, following tendency is arranged: the frequency band more than 4kHz, the situation of wide band quantized LSP when stored wide band LSP more is bordering on zero defect (with zero defect time wide band quantized LSP error little) is more, frequency band below 4kHz, more near 0Hz, the situation of the wide band quantized LSP when frequency band transformation LSP more is bordering on zero defect (with zero defect time wide band quantized LSP error little) is more.Therefore, described formula (1)～(4) are the functions that is similar to the characteristic that comprises described error prone.So, by using weighting coefficient w1 (i) and the w2 (i) that defines with formula (1)～(4), can consider by the combination of the frequency band in the frequency band of arrowband and broadband and definite error characteristics, promptly, error prone between the wide band quantized LSP of frequency band transformation LSP and zero defect is handled and be weighted addition.And, can be to decide weighting coefficient w1 (i) and w2 (i) suc as formula the such simple formula in (1)～(4), therefore do not need weighting coefficient w1 (i) and w2 (i) are stored in ROM (Read Only Memory) etc., can realize effective weighting summation with simple structure.
In addition, in present embodiment, there to be error change tendency, promptly the high more time error of frequency or the number of times situation that becomes big more tendency describes as an example, but error change tendency is different because of imposing a condition of the frequency domain of each layer etc.For example, frequency domain in the arrowband is that the frequency domain in 300Hz～3.4kHz, broadband is when being 50Hz～7kHz, because the lower frequency limit difference, the error that might take place with the zone below 300Hz is compared, and the error that the zone more than 300Hz takes place is littler or be same degree.In this case, for example can make weighting coefficient w2 (1) be and the identical value of weighting coefficient w2 (2), or be value greater than weighting coefficient w2 (2).
That is to say that the condition that requires is as follows when setting weighting coefficient w1 (i) and w2 (i).The coefficient corresponding with overlapping bands is defined as first coefficient, and described overlapping bands is the frequency domain of arrowband and the overlapped zone of frequency domain in broadband.In addition, the coefficient corresponding with non-overlapped frequency band is defined as second coefficient, frequency domain that described non-overlapped frequency band is the arrowband and the mutual nonoverlapping zone of the frequency domain in broadband.First coefficient is a parameter, based on the frequency in the overlapping bands or corresponding to the edge frequency of the number of times of this frequency and overlapping bands and non-overlapped frequency band or corresponding to the difference of the number of times of this edge frequency and determine.Second coefficient is constant in non-overlapped frequency band.
Moreover, for first coefficient, do not set described difference hour more little value more accordingly with frequency band transformation LSP is individual, set described difference hour big more value more individually accordingly with stored wide band LSP.Specifically, can be to represent first coefficient suc as formula the formula of (1) and (3) represented linearity, also can will use speech database etc. to use as first coefficient by the value that study obtains.When obtaining first coefficient by study, determine weighting coefficient as follows, that is, and the speech data all to database, the error of wide band quantized LSP when compensating wide band LSP that calculating obtains as the result of weighting summation and zero defect, and the decision weighting coefficient is so that its summation be a minimum.
Like this, according to present embodiment, when having lost the wide-band LSP coded message of current coded message, the wide band quantized LSP weighting summation of frequency band transformation LSP by the arrowband of this coded signal being quantized LSP and former coded message generates compensating wide band LSP, and compensates the wide band quantized LSP of the wideband encoding information of being lost with compensating wide band LSP.Just, the wide band quantized LSP weighting summation by with the frequency band transformation LSP of current coded message and former coded message generates compensating wide band LSP, and it is used to compensate the wide band quantized LSP of the wideband encoding information of being lost.Therefore, compare with the wide band quantized LSP of coded message or the arrowband of the current coded message situation that quantizes the wide band quantized LSP of the wide-band LSP coded message that LSP lost with compensation before only using, can make the wide band quantized LSP of the wide-band LSP coded message after the compensation approach the state of zero defect, can improve fault-tolerance thus transmission error.And, the frequency band transformation LSP of current coded message successfully can be connected with the wide band quantized LSP of former coded message, thereby can keep continuity between the frame of the compensating wide band LSP that generated.
(embodiment 2)
Fig. 5 is the block scheme of major part of structure of the scalable decoder of expression embodiment of the present invention 2.In addition, the scalable decoder 200 of Fig. 5 comprise with in the identical basic structure of the scalable decoder 100 of embodiment 1 explanation.Therefore, to give identically with reference to label at the identical structural element of embodiment 1 explanation, and omit its detailed description.
Wide-band LSP decoding unit 202 and wide-band LSP decoding unit 110 similarly based on LOF information, by from the arrowband quantification LSP of arrowband LSP decoding unit 108 inputs and the wide-band LSP coded message of importing from multiplexing separative element 102, obtain wide band quantized LSP.
In wide-band LSP decoding unit 202, the frequency band transformation LSP that variation computing unit 206 is accepted by converter unit 120 acquisitions.Calculate the interframe variation of frequency band transformation LSP then.Variation computing unit 206 will output to the weighting coefficient control module 208 of LOF compensating unit 204 according to the control signal of the interframe variation that calculates.
LOF compensating unit 204 will be from the frequency band transformation LSP and the stored wide band LSP weighting summation that is stored in buffer 129 of converter unit 120 inputs with the method identical with LOF compensating unit 124.Generate compensating wide band LSP thus.
In addition, weighting summation at embodiment 1, directly using the weighting coefficient w1 and the w2 that determine in unique mode based on number of times i or corresponding frequency, but with respect to this, is to control and use weighting coefficient w1 and w2 adaptively at the weighting summation of present embodiment.
In LOF compensating unit 204, weighting coefficient control module 208 is according to the control signal from 206 inputs of variation computing unit, and among the weighting coefficient w1 (i) of whole frequency band and the w2 (i) corresponding with overlapping bands (promptly being defined as " first coefficient " at embodiment 1) weighting coefficient w1 (i) and w2 (i) are changed adaptively.
More particularly, when the interframe variation of calculating is big more, make weighting coefficient w1 (i) big more and correspondingly make the more little setting of weighting coefficient w2 (i).And in the interframe variation of calculating more hour, make weighting coefficient w2 (i) big more and correspondingly make the more little setting of weighting coefficient w1 (i).
As an example of described control method, can lift following control method: with the interframe variation that calculates and specific threshold ratio,, switch the weighting coefficient group that comprises weighting coefficient w1 (i) and weighting coefficient w2 (i) according to this comparative result.When adopting this control method, weighting coefficient group WS1 that weighting coefficient control module 208 storage in advance is corresponding with the interframe variation more than the threshold value and the weighting coefficient group WS2 corresponding with the interframe variation that is lower than threshold value.The weighting coefficient w1 (i) that is comprised among the weighting coefficient group WS1 is set at value greater than the weighting coefficient w1 (i) that is comprised among the weighting coefficient group WS2, the weighting coefficient w2 (i) that is comprised among the weighting coefficient group WS1 is set at value less than the weighting coefficient w2 (i) that is comprised among the weighting coefficient group WS2.
Then, result relatively, in the interframe variation of calculating is that threshold value is when above, 208 pairs of weighted units 130 of weighting coefficient control module are controlled, so that weighted units 130 is used the weighting coefficient w1 (i) of weighting coefficient group WS1, simultaneously weighted units 132 is controlled, so that weighted units 132 is used the weighting coefficient w2 (i) of weighting coefficient group WS1.On the other hand, result relatively, when the interframe variation of calculating is lower than threshold value, 208 pairs of weighted units 130 of weighting coefficient control module are controlled, so that weighted units 130 is used the weighting coefficient w1 (i) of weighting coefficient group WS2, simultaneously weighted units 132 is controlled, so that weighted units 132 is used the weighting coefficient w2 (i) of weighting coefficient group WS2.
Like this, according to present embodiment, because when the interframe variation is big more, make weighting coefficient w1 (i) big more and correspondingly make the more little setting of weighting coefficient w2 (i), on the other hand, in the interframe variation of calculating more hour, make weighting coefficient w2 (i) big more and correspondingly make the more little setting of weighting coefficient w1 (i), that is to say, because the weighting coefficient w1 (i) and the w2 (i) that use at weighting summation are changed adaptively based on the interframe variation, so can according to the information of normal reception through the time change and control weighting coefficient w1 (i) and w2 (i) adaptively, can further improve the compensation precision of wide band quantized LSP.
In addition, the variation computing unit 206 of present embodiment is arranged on the back level of converter unit 120, calculates the interframe variation of frequency band transformation LSP.But the configuration of mapping computation cell 206 and structure are not limited to above-mentioned configuration and structure.For example, also variation computing unit 206 can be set in the prime of converter unit 120.At this moment, variation computing unit 206 calculates the interframe variation that the arrowband that is obtained by arrowband LSP decoding unit 108 quantizes LSP.Also can realize action effect same as described above this moment.
In addition, earthquake amount computing unit 206 also can individually carry out the calculating of interframe variation to each number of times of frequency band transformation LSP (or the arrowband quantizes LSP).At this moment, by weighting coefficient control module 208 each number of times is weighted the control of coefficient w1 (i) and w2 (i).Can further improve the precision of the compensation of wide band quantized LSP thus.
In addition, each functional block that is used for the explanation of above-mentioned embodiment can be embodied as LSI usually, and it is a kind of integrated circuit.These pieces both each piece be integrated into a chip respectively, perhaps can be that a part or all pieces are integrated into a chip.
Though be called LSI herein,, also can be called as IC, system LSI, super LSI (Super LSI) or especially big LSI (Ultra LSI) according to degree of integration.
In addition, realize that the method for integrated circuit is not limited only to LSI, also can use special circuit or general processor to realize it.After LSI makes, programmable FPGA (Field Programmable GateArray) be can utilize, the connection of circuit unit of restructural LSI inside and the reconfigurable processor of setting perhaps can be used.
Moreover, along with semi-conductive technical progress or the appearance of other technology of derivation thereupon,, can utilize new technology to carry out the integrated of functional block certainly if the new technology of LSI integrated circuit can occur substituting.Exist the possibility that is suitable for biotechnology etc.
This instructions is the Japanese patent application 2004-258925 according to application on September 6th, 2004.Its content all is contained in this.
Industrial applicibility
Scalable decoder of the present invention and signal loss compensation method, applicable in the mobile communication system With the device of communicating by letter in the packet communication system that uses Internet protocol etc.
Claims (7)
1. scalable decoder comprises:
Decoding unit is decoded to the narrow band spectrum parameter corresponding with the core layer of the first hierarchical coding signal;
Storage unit, the corresponding broader frequency spectrum parameter of extension layer of storing the second hierarchical coding signal different with the first hierarchical coding signal; And
Compensating unit, when losing the corresponding broader frequency spectrum parameter of extension layer with the second hierarchical coding signal, frequency band transformation signal by the narrow band spectrum parameter of will be decoded generates the loss compensation signal with the broader frequency spectrum parameter weighting addition of being stored, and comes the decoded signal of the broader frequency spectrum parameter of compensating missing with the loss compensation signal.
2. scalable decoder as claimed in claim 1, wherein,
The narrow band spectrum parameter of the first hierarchical coding signal has first frequency band, and the broader frequency spectrum parameter of the second hierarchical coding signal has second frequency band than first bandwidth;
Also comprise: converter unit, with the narrow band spectrum parameter of being decoded from first frequency band transformation to second frequency band, thereby generate the frequency band transformation signal;
Described compensating unit uses the weighting coefficient of setting based on first frequency band and second frequency band to be weighted addition.
3. scalable decoder as claimed in claim 2, wherein,
Described compensating unit uses the weighting coefficient that is provided by function to be weighted addition, and this function is the function of frequency, and is similar to the error between the broader frequency spectrum parameter of frequency band transformation signal and zero defect.
4. scalable decoder as claimed in claim 2, wherein,
Described compensating unit uses first weighting coefficient and second weighting coefficient to be weighted addition, and this first weighting coefficient is corresponding with the overlapping bands of first frequency band and second frequency band, and this second weighting coefficient is corresponding with the non-overlapped frequency band of first frequency band and second frequency band;
First weighting coefficient is a parameter, determines that according to the difference of the edge frequency of the frequency in the overlapping bands and overlapping bands and non-overlapped frequency band second weighting coefficient is a constant in non-overlapped frequency band.
5. scalable decoder as claimed in claim 2, wherein,
Described compensating unit uses weighting coefficient to be weighted addition, this weighting coefficient is to frequency band transformation signal and broader frequency spectrum parameter individual settings, and determines according to the difference of the edge frequency of frequency in the overlapping bands of first frequency band and second band overlapping and overlapping bands;
The weighting coefficient that the frequency band transformation signal is set hour is got more little value more in described difference, and the weighting coefficient that the broader frequency spectrum parameter is set hour is got big more value more in described difference.
6. scalable decoder as claimed in claim 2, wherein,
Described compensating unit makes the weighting coefficient for frequency band transformation signal and broader frequency spectrum parameter individual settings, according to the interframe variation variation of the narrow band spectrum parameter of being decoded.
7. signal loss compensation method, when having lost the corresponding broader frequency spectrum parameter of extension layer with current hierarchical coding signal, will be corresponding to the frequency band transformation signal of the core layer of current hierarchical coding signal and the narrow band spectrum parameter of being decoded and broader frequency spectrum parameter weighting addition corresponding to the extension layer of former hierarchical coding signal, generate the loss compensation signal thus, and compensate the decoded signal of the broader frequency spectrum parameter of being lost with the loss compensation signal.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2004258925 | 2004-09-06 | ||
| JP258925/2004 | 2004-09-06 | ||
| PCT/JP2005/016098 WO2006028009A1 (en) | 2004-09-06 | 2005-09-02 | Scalable decoding device and signal loss compensation method |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101010730A true CN101010730A (en) | 2007-08-01 |
| CN101010730B CN101010730B (en) | 2011-07-27 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2005800294184A Expired - Fee Related CN101010730B (en) | 2004-09-06 | 2005-09-02 | Scalable decoding device and signal loss compensation method |
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| Country | Link |
|---|---|
| US (1) | US7895035B2 (en) |
| EP (1) | EP1788556B1 (en) |
| JP (1) | JP4989971B2 (en) |
| CN (1) | CN101010730B (en) |
| WO (1) | WO2006028009A1 (en) |
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| CN111200485A (en) * | 2018-11-16 | 2020-05-26 | 中兴通讯股份有限公司 | Method and device for extracting broadband error calibration parameters and computer readable storage medium |
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- 2005-09-02 US US11/574,631 patent/US7895035B2/en not_active Expired - Fee Related
- 2005-09-02 CN CN2005800294184A patent/CN101010730B/en not_active Expired - Fee Related
- 2005-09-02 JP JP2006535718A patent/JP4989971B2/en not_active Expired - Fee Related
- 2005-09-02 WO PCT/JP2005/016098 patent/WO2006028009A1/en active Application Filing
- 2005-09-02 EP EP05777024.0A patent/EP1788556B1/en not_active Not-in-force
Cited By (3)
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| CN101308660B (en) * | 2008-07-07 | 2011-07-20 | 浙江大学 | Decoding terminal error recovery method of audio compression stream |
| CN111200485A (en) * | 2018-11-16 | 2020-05-26 | 中兴通讯股份有限公司 | Method and device for extracting broadband error calibration parameters and computer readable storage medium |
| CN111200485B (en) * | 2018-11-16 | 2022-08-02 | 中兴通讯股份有限公司 | Method and device for extracting broadband error calibration parameters and computer readable storage medium |
Also Published As
| Publication number | Publication date |
|---|---|
| EP1788556A4 (en) | 2008-09-17 |
| CN101010730B (en) | 2011-07-27 |
| JP4989971B2 (en) | 2012-08-01 |
| EP1788556B1 (en) | 2014-06-04 |
| JPWO2006028009A1 (en) | 2008-05-08 |
| US20070265837A1 (en) | 2007-11-15 |
| US7895035B2 (en) | 2011-02-22 |
| WO2006028009A1 (en) | 2006-03-16 |
| EP1788556A1 (en) | 2007-05-23 |
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